How is the 741 op-amp output protected when shorted to V+?
I think I finally managed to unravel the mystery of the 741 sink (low-side) limiter... I will expose my guesses in the form of an imaginary story of how they were thinking when designing the circuit.

Original asymmetrical circuit solution

Sensing and limiting through the previous stage. In the initial 741 internal circuit diagram (Fig. 1), the Widlar's trick is applied only to the push transistor Q14 by Q15 and R9. For some reason (I will consider it below), it was unacceptable for it to be also applied to the pull transistor Q20. That is why they assigned the previous stage (the intermediate voltage amplifier Q16,Q17 and limiting transistor Q22) both to sense and limit the overcurrent.



Fig. 1. In the initial 741 op-amp circuit solution, the previous stage both senses and limits the overcurrent

"Moving" the overload to the previous stage. The sensing is based on the properties of the BJT emitter follower. Let me clarify what this is about. In an emitter follower, the base-emitter junction makes a direct connection between the input and output. It is a one-way "diode" connection (from input to output). Under normal operating conditions, the transistor "lifts" its emitter voltage almost to the input base voltage level so that this direct connection does not work... and the base current is low (bootstrapping). When the output is grounded (short circuit), this phenomenon ceases to operate and the input is also grounded through the base-emitter junction... i.e., the overload is also applied to it. It would be not the case if the follower had been implemented with FET (source follower); so it is only valid for BJT.

No sensing the overload (ideal transistor). OK, the low load resistance is applied (through the Q20 base-emitter junction and 50 ohms R10) to the Q17 collector. And now the riddle comes into the picture, "How is it possible the load to change the Q17 collector current while its base voltage is kept constant? Q17, like any BJT, behaves as a constant current source (sink here); so its collector current cannot be changed from the side of the collector... the voltage drop across R11 cannot be changed as well.

(Practically, we have implemented this experiment as follows. In the beginning, we have set some constant input voltage so that Q17 base voltage is constant. Then we connect a variable load resistor (rheostat) between the output and V+. There is some (small) Q20 base current that, together with Q13 quiescent collector current, enters Q17 collector. Both they flow through R11 and create a voltage drop that is unsufficient to turn on Q22. Then we begin decreasing RL up to zero (short to V+). Q20 base current increases... but Q17 (behaving as a current sink) should not let it do that. So the voltage drop should not change.)

And this would indeed be the case if Q17 was an "ideal" transistor (without any Early effect) having an almost horizontal output IV curve - Fig. 2. When the resistance applied to the collector changes from RL + R10  to only R10, the load line rotates clockwise... the intersection (operating) point moves from 1 to 2 position... but the collector current does not change - I1 = I2, dI = 0. So the voltage drop across R11 does not change as well... and Q22 does not sense the overload.



Fig. 2. Graphical solution of the circuit in the case of an "ideal" transistor (without Early effect)

There is even something else "harmful" here - the resistor R11 in the Q17 emitter introduces a negative feedback that tries to keep the current constant (emitter degeneration)... but, for the purposes of the overcurrent sensing, we want just the opposite...

Sensing the overload (real transistor). But Q17 is a real transistor with Early effect and its output IV curve has some slope - Fig. 3. So when the operating point moves from 1 to 2 position, the collector current will (slightly) change from I1 to I2... the voltage drop across R11 will also (slightly) change... and Q22 should sense this change.



Fig. 3. Graphical solution of the circuit in the case of a real transistor (with some Early effect)

The paradox of this idea is that, in order for this circuit to work well, the transistor Q17 should be poor... the poorer it is, the better Q22 will sense the overload. If Q17 is too perfect, Q22 may not sense it...

Never implemented symmetrical solution

However, the idea of a symmetrical current limiter in both output parts remains attractive. It can be found, for example, in the output stages of powerful amplifiers implemented by discrete elements - Fig. 4.



Fig. 4. Power amplifier with identical current limiters in both push and pull part

So why did not Widlar and designers at Fairchild do it in 741 op-amp? One possible explanation is that it cannot be done as @Jonk has said in the related question:


  A symmetrically equivalent low-side isn't possible...


I made a lot of effort to figure out what the problem with this circuit was that it did not work. I turned my imagination into top gear (Fig. 5)... I even dug up old books from my student years... and still I have not found the reason... maybe simply because there was no principal reason for it not to work...



Fig. 5. Can the symmetrical current limiter work?

Apparently the circuit can work properly... but it works poorly... So I am more inclined to rely on @EinarA explanation above about the low performance of p-n-p transistors...

Improved symmetrical circuit solution

Maybe that was the reason that, in the next 741 version, the Widlar's followers from Fairchild separated the two functions so that the pull output stage senses while the previous stage limits the overcurrent (Fig. 6).



Fig. 6. In the improved 741 op-amp, functions are separated - the pull output stage senses while the previous stage limits the overcurrent

It is done in the typical Widlar manner by connecting the low-side sensing circuit (Q21, R7) with the limiting transistor Q22 via a current mirror (Q22,Q24)... as though Q21 is moved at the place of Q22. The current mirror serves as a kind of "current transmission" connecting Q21 and Q22.

What is the benefit of all this? I think that thanks to the higher gain of the n-p-n Q22 and Q18, the current protection is triggered more sharply... and thus it is more efficient...

Is there a paradox here? No, now the transistor Q17 can be perfect as much as we want...