dexed subcarriers. This operation is reversed at the receiver using the function -1(.). The other blocks are self-explanatory. Let the quantity sm.in = Thus, it follows from (3.9) that (3.10) the imaginary part of the cross correlation between the basis functions [26]. The signal received at the SISO-FBMC receiver is 3 FBMC: A Waveform Candidate for Beyond 5G Transmit Antenna Receive Antenna ejoon e-j4o, D(Co.n) -j2zk e-john D(C1,n) ejon-1.1 dN-1,n bn-1.n YN-1,n P(CN-1,n -(-1.n) Fig. 3.2 Discrete-time equivalent baseband model for FBMC: (a) transmitter and (b) receiver y[k]=(s[k]*h[k])+n[k], (3.11) where h[k] denotes impulse response of an Lh-tap channel. The scaler quantity n[k] is an additive white Gaussian noise (AWGN) with mean zero and variance on At the receive, the FBMC signal is demodulated at frequency index m and symbol instant n by matching it with the basis function Xm,n[k] as [15] (3.12) k=-00 By substituting s[k], Xm,[k] and y[k] from (3.7), (3.8) and (3.11), respectively, in the above expression, , is expanded as Nm,N, (3.13) the demodulated noise which obeys Gaussian distribution with mean k=-00 P. Singh and E. Sharma The covariance between Nm,n and Nm,n is computed as (3.14) The noise at FT index (m, n) is thus correlated. This correlation, however, is negligible because of the associated sharp prototype filters for pulse shaping in FBMC [24]. The duration of the prototype pulse p[k] in FBMC is typically chosen as an integer multiple of the symbol time T. Thus, the pulse duration is significantly larger than the channel delay spread, i.e. Lp = koN >> Lh. For example, references [24, 26] set ko to be 4. This implies that the bandwidth of the pulse- shaping filter p[k] is significantly lower than the channel coherence bandwidth. As a result, the impulse response p[k] of prototype filter in time has negligible variations over the channel delay spread. Therefore, as described in [24, 26] p[k-1- - nN/2] 2 p[k - nN/2], for l E [0, Lh]. (3.15) Upon employing the above result, the expression for y[k] in 