In response to programmer input of a trigger token, a program editor creates a pair of boundary tokens encapsulating an embedded lexical context and positions an insertion point within the embedded lexical context. The operations on the embedded lexical context are preferably performed using an embeddable sub-editor specialized to the task at hand. Since boundary tokens are generated in pairs, stability of lexical boundaries is enforced. Accordingly, stable implementations of certain desirable behaviors, including language-oriented advanced program typography that is robust to user edits, are facilitated using the invented techniques.

1. Field of the Invention
The present invention relates generally to interactive software engineering tools including editors for source code such as a programming or mark-up language, and more particularly to a language-based editing architecture with support for embedded lexical contexts.
2. Description of the Related Art
Source code plays a major role in most software engineering environments, yet it has always been difficult for software engineers to interact with such code. A common problem encountered by programmers when interacting with source code is that prior art program editors, while often language-sensitive, build upon fragile representations that are ill-suited to the manipulation of multiple embedded syntactic structures, for which behaviors would ideally be defined in accordance with distinct lexical rules. As a result, such prior art program editors are typically limited in their specialization of behaviors and those specialized behaviors provided often exhibit instability in the face of interactive edits. As will now be described, a particularly common instability often results in confusing language-based display (e.g., text formatting or pretty printing, linguistically-driven typography, etc.) and can result in the loss of previous linguistic analysis of program structures being entered.
FIG. 1 depicts a conventional computing system 10 with which a programmer or other user may enter or edit source code. System 10 includes a computer system 20 having at least one CPU 30 and memory (MEM) 40 contained therein. Memory 40 typically includes both volatile and non-volatile memory or storage. A portion of the volatile memory is typically used as a text buffer 50. The programmer or other user enters source code into computer system 20, typically using a keyboard 60 and often augmented by use of a mouse or trackball 70. In general, text buffer 50 is used to represent information, sometimes referred to as a data model.
Typically, software executable on CPU 30 provides functionality of an editor environment, including display and other functionality appropriate to a particular language context for which the software is intended. Sometimes, editor or editor-like facilities may be provided within other software environments. For example, editor facilities are commonly provided within integrated software engineering tools or environments, including within source level debuggers, source analyzers, viewers, etc. Furthermore, such editor facilities may be provided or embedded within other types of systems, e.g., to support scripting or macro language facilities of a word processing, publishing, spreadsheet or other application. In each case, editor facilities provide display and/or rendering functionality, which is often implemented as software executable by computer system 20, and which displays or renders characters, symbols or graphics corresponding to the information represented in text buffer 50.
Often, display functionality renders information represented in text buffer 50 accordingly to stylistic rules appropriate for a particular language type (e.g., for a comment, string literal or tag). For example, portions of text may be rendered as display 90 on monitor 80 using particular typefaces, font sizes, colors and/or attributes that are appropriate or conventional for a particular language type. In general, such functionality operates on contents of text buffer 50 and applies what is believed, rightly or wrongly, to be the appropriate stylistic rules. Unfortunately, associations between particular contents of text buffer 50 and appropriate stylistic rules are typically quite fragile, particularly in the presence of editing operations. Accordingly, if provided, language-based display (e.g., text formatting or pretty printing, linguistically-driven typography, etc.) is somewhat unstable in prior art editor designs. This instability will be better understood in the context of the following example.
Referring now to FIG. 2A, assume that a programmer enters the following keystrokes:S=E+"}";using system 10. Corresponding contents of text buffer 50 are illustrated in FIG. 2A and a corresponding display (e.g., display 90) is rendered to monitor 80 as shown in FIG. 1.
A typical prior art code-oriented editing environment recognizes language constructs of entered text by performing pattern matching or lexical (language) analysis on context of text buffer 50. Referring illustratively to the contents shown in FIG. 2A, a pattern matching or lexical analysis facility recognizes the group 110 of characters or tokens, namely "}", as a string literal. Having properly recognized string literal from amongst the remaining source language contents of text buffer 50, a prior art editing environment of system 10 may apply special typographical attributes such as special coloring when displaying characters or symbols of the string literal on monitor 80.
Assume now that the programmer wishes to edit the current line so it will eventually read as follows:S="{"+E+"}";
To carry out the above edit, the programmer typically repositions cursor 100 on display 90 so that a corresponding insertion point exists before the existing character E, then begins typing the additional text (namely, the characters "{" +) using keyboard 60. Underlining is used herein as a notational convention to better delimit the relevant characters. The initial double quote character " is the first such character entered and FIG. 2B illustrates the state of text buffer 50 after its entry, but before remaining characters of the desired edit are entered. The illustrated state highlights the fragility of many prior art editor implementations. Typically, such editor systems are unable to properly handle display of text buffer 50 contents after entry of an initial double quote character " that is intended by the programmer to signify start of a new string literal.
Instead, given the text buffer 50 state illustrated in FIG. 2B, a pattern matcher or lexical analyzer of the editor typically re-analyzes the text buffer contents and erroneously assumes that portion 120 of the buffer contents, namely "E+", itself corresponds to a string literal consisting of the characters E+, where underlining is used herein to better delimit the relevant characters. Accordingly, upon programmer entry of the triggering keystroke ", such an editor makes the erroneous assumption (relative to the programmer's intent) that "E+" is itself a string literal and modifies typographic attributes of display 90 accordingly. For example, the supposed string literal "E+" may be rendered using a fixed point font, using a color and size that have been predefined for string literal rendering. Depending on the implementation, inappropriate visual cues may extend to other portions of text buffer 50 contents. For example, since it no longer appears to be preceded by an opening double quote character ", line portion 130 (namely, the right brace character }) may be improperly interpreted as a code construct, rather than as the contents of a string literal intended by the programmer. Indeed, in an editor implementation that performs lexical analysis or even simple matching of braces, a portion may be interpreted (and visually presented) as an unbalanced brace within a context that requires an opening brace for each closing brace.
Furthermore, because the second occurrence of a double quote character " is improperly interpreted as a closing double quote character for the string literal "E+", text buffer 50 contents 140 may also be misinterpreted. For example, a lexical analyzer of the editor may identity the characters "; as an invalid lexeme. In particular, buffer contents 140 may be interpreted as the start of a string literal that lacks a closing double quote character. In some prior art editor implementations, an invalid lexeme may be rendered in such a way, e.g., in red, as to highlight invalidity for the programmer. Unfortunately, such inappropriate visual cues can be quite distracting to the programmer.
As the programmer enters additional keystrokes to complete the desired S="{"+E+"}"; entry, a typical prior art editor will continue to inappropriately interpret text buffer 50 contents. In the above example, upon completion of keystrokes for entry of the string literal "{", visual cues return to appropriate values. However, in general, a keystroke-by-keystroke interpretation of a given edit may result in an ever changing (and distracting) set of visual cues such as color, typeface or other typographic attributes. While many prior art editors exhibit such inappropriate behaviors, others may simply forgo otherwise desirable language-based features such as advanced program typography or lexical analysis on a keystroke-by-keystroke basis because of the challenges created by interactive edits. To facilitate introduction and use of such features, language-based techniques are needed which exhibit greater stability in the face of interactive edits.
To some degree, inappropriate behaviors can be avoided using language structure-based editor techniques. So-called structure-based editors use internal representations that are closely related to the tree and graph structures used by compilers and other programming tools. While, structure-based editors can greatly simplify some kinds of language-oriented services, they generally impose the requirement that the programmer edit using structural, rather than textual, commands. For example, entry of a string literal may require a structural command such as "Insert String Literal" which may be selected from a pull-down menu, bound to a key stroke sequence, such as a control or escape sequence, or invoked by some other non-lexical trigger. In general, such an editing architecture assumes that programs are intrinsically tree structured, and that programmers understand and should manipulate them accordingly. In practice, this assumption has not been borne out and structure editors have not found wide acceptance.
Some structure-based editors allow uses to "escape" structural constraints by transforming selected tree regions into plain text, but usability problems persist. The complex unseen relationships between textual display and internal representation make editing operations confusing and somewhat unpredictable because of "hidden state." In some ways, textual escapes make matters worse with a confusing and distracting distinction between those part of a program where language-based services are provided and those where they are not. Often, language services and tools stop working until all textual regions are syntactically correct and transformed back to structure.
Unfortunately, due in large measure to practical user acceptance and deeply ingrained motor learning habits that involve textual, rather than structural editing, practical code-oriented text editors emphasize a textual representation. One widely adopted code-oriented text editor, the Emacs editor, uses a purely textual representation, assisted by ad-hoc regular expression matching that can recognize certain language constructs. But, by definition, the structural information computed by simple text editors is incomplete and imprecise, and such editors cannot support services that require true linguistic analysis such as advanced program typography. At best, simple text editors typically provide indentation, syntax highlighting, and navigational services that can tolerate structural inaccuracy. Although high quality, linguistically-driven typography can measurably improve the programmer's reading comprehension, such typography is often lacking in prior art source code editors, especially when encountering malformed and fragmentary program code. Although a few text editors can perform per-line lexical analysis with each keystroke, the absence of true program representation leads to confusion in the inevitable presence of mismatched string quotes and comment delimiters.
In view of the above, techniques are desired whereby interactive software engineering tools may reliably implement behaviors including advanced program typography in accordance with a proper lexical context. In particular, techniques are desired that facilitate stable language-oriented representations in the presence of interactive edits, but which do not force a user to enter structural commands.

Interactive software engineering tool with support for embedded lexical contexts


A jet for treating a yarn with a fluid has a flow control plate having a first and a second flow control opening. The flow control openings are located in the plate such that when the plate is mounted between the jet body and the manifold body, at least one, but preferably both, of the flow control openings in the plate at least partially overlap the inlet end of one (or both) of the fluid supply channels, thereby to modify the fluid flow area presented to the manifold by the fluid supply channel(s).

1. Field of the Invention
The present invention relates to a jet apparatus for treating a yarn with a treatment fluid, such as hot gas or steam, and in particular, to a jet apparatus that includes a flow control plate whereby the supply of treatment fluid to the jet may be adjustably controlled.
2. Description of the Prior Art
In the manufacture of synthetic thermoplastic yarn it is known that bulk and interlace may be imparted to the yarn by directing a heated treatment fluid to opposite sides of a yarn as it travels along a passage formed within a jet body. U.S. Pat. No. 3,525,134 (Coon) exemplifies such a dual impingement yarn treatment jet. The jet structure is formed from a jet body having a conjoinable cover. One surface of the jet body has the yarn passage and associated lateral supply conduits precisely machined therein. Treatment fluid is supplied to the lateral supply conduits from supply channels that extend into the jet body from the machined surface. The supply channels typically communicate with a common supply manifold. The supply manifold may be bored into the jet body or formed in a separate manifold body which is itself attachable to the jet body. The relative sizing of the various regions of the yarn passage and the associated conduits and supply channels permits the flow of treatment fluid impinging on the yarn to be precisely controllable. Owing to the care which must be exercised in forming the passage and associated conduits and channels, fabrication of a yarn treatment jet is time consuming and expensive.
In some instances, however, it may occur that the amount of interlace imparted to a yarn by a jet may become excessive. Of course, replacing the jet body with an alternative jet which is engineered to produce a different level of interlace is a direct expedient for altering the interlace level. However, owing to the cost associated with the fabrication of a jet, this alternative is not seen as economically favorable.
Alternatively, it is known that an imbalance in the flow of treatment fluid to opposite sides of the yarn has the effect of reducing the amount of interlace imparted to the yarn. U.S. Pat. No. 5,325,572 (Dickson et al.), assigned to the assignee of the present invention, discloses a jet structure having flow adjustment devices arranged to alter flow through the fluid supply channels and/or in the supply conduits.
In view of the foregoing it is believed desirable to provide an alternative jet structure wherein the flow of treatment fluid may be more easily adjusted so that the relative balance between the flow to the two opposing sides of the yarn may be selectably controlled.

Yarn treating jet having a flow control plate


A body spray nozzle is disclosed wherein the spray pattern can be easily adjusted and the nozzle can be oscillated in a support in a shower fixture. A movable valve element which is cup-shaped is positioned in a valve body and with the base thereof to the inlet side of a stationary valve element. Rotation of the movable valve element is effected from the front of the valve housing which directs different flow paths to a nozzle portion. Two or more of the body spray nozzles are interconnected with linkage members for oscillation by an oscillating source.

A. Field Of The Invention
This invention relates primarily to body spray nozzles wherein the spray pattern can be easily adjusted. More particularly, the invention relates to nozzles of the foregoing type which can be oscillated in a shower fixture.
B. Description Of The Art
It is desirable to provide shower type nozzles with different spray patterns to accommodate the likes of the bather. It is known to provide nozzles with different spray patterns which are achieved by rotating a portion of the shower head. For example in U.S. Pat. No. 166,654 different flow paths are obtained in a nozzle head by rotating a cup-like member so as to orient different passages with parts in the nozzle. U.S. Pat. Nos. 3,558,054 and 3,801,019 also disclose different flow paths in a nozzle structure. In the '054 patent the spray head is rotated and in the '019 patent a shutter plate is used in conjunction with gears and pinions. A problem with these prior art nozzles is that they are not aesthetically appearing, can become disassembled during use or require a multiplicity of moving parts.
A need exists for an improved nozzle which can overcome the foregoing problems of the prior art.
There is also a need in the art of oscillating a nozzle of the foregoing type in a shower fixture so as to automatically cover a wide area of the body. It is also desirable that more than one nozzle be oscillated at the same time. It is desirable to do this with minimal parts and in a compact setting. For example, see U.S. Pat. No. 3,261,369.


The present invention relates to a process for the treatment of heavy oils using a catalytic hydrotreating process. More specifically, the invention relates to the presence of light hydrocarbon components in conjunction with the heavy oils for improved treatment of the heavy oils utilizing moderate temperature and pressure.

1. Field of the Invention
The present invention relates to a process for the treatment of heavy oils, including crude oils, vacuum residue, tar sands, bitumen and vacuum gas oils, using a catalytic hydrotreating process. More specifically, the invention relates to the use of catalysts in series in order to prolong the life of the catalyst. In another embodiment, the presence of light hydrocarbon components in conjunction with the heavy oils is used for improved treatment of the heavy oils utilizing moderate temperature and pressure.
2. Description of the Related Art
Hydrotreating is useful for the purpose of improving heavy oils. The improvement can be evidenced as the reduction of sulfur content of the heavy oil, an increase in the API gravity of the heavy oil, a significant reduction in the metal content of the heavy oil, or a combination of these effects.
The availability of light sweet crudes is expected to diminish in the future as the production of oil becomes increasingly difficult and greater reliance is placed on tertiary and enhanced recovery techniques. Heavier crudes and sour crudes will take on greater importance in overall hydrocarbon production and the upgrading of such crudes into fuels will become increasingly important. In addition to the decreasing quality of the crudes and their derived heavy oils, specifications for on-road and off-road fuel will become increasingly more stringent, driven by environmental legislation around the world. A greater emphasis on upgrading and degree of hydroprocessing can be expected in the refining industry.
One of the main limiting factors for hydroprocessing units is the deactivation of the hydroprocessing catalysts. As the heavy oil feedstock being treated becomes heavier, i.e. has a lower API Gravity, the complexity of the molecules increases. This increase in complexity is both in the molecular weight and also in the degree of unsaturated components. Both of these effects increase the coking tendency of the feedstock, which is one of the main mechanisms of deactivation of the catalyst. Another aspect of feedstock leading to deactivation of catalyst is metal content present in the heavy crude. These metals are normally present in the form of porphyrin type structures and they often contain nickel and/or vanadium, which have a significant deactivating effect on the catalyst. Similar to coking tendency, the metal concentration of the heavy oil feedstream increases with decreasing API gravity.
Any pre-refining of crude oil would provide a significant advantage for downstream process units.
As the refining industry increasingly processes higher sulfur, lower API crudes, catalyst deactivation will become a critical path problem, decreasing the on-stream cycle length and therefore increasing the cost of processing, negatively impacting process profitability. Advances in the treatment of heavy oil with respect to a reduction in catalyst deactivation will therefore be of paramount importance to the refining industry in future years.
Global diesel demand is forecasted to increase in the coming years due to the dieselization trend, equaling global demand for gasoline in the near future and surpassing this demand thereafter. A shift in product slate is occurring. The inherent content of the gas oil in crude oils is limited and conventional, expensive conversion techniques such as hydrocracking are required to increase the diesel yield by conversion. There is a need to provide a process for heavy oils that will increase diesel production in a cost-effective manner to meet market demands. There is a need to provide a process that minimizes capital expenditures necessary while meeting the product specifications.

Process for the treatment of heavy oils using light hydrocarbon components as a diluent


A liquid crystal display (LCD) source driving circuit having a reduced circuit footprint. A plurality of the LCD source driving circuits are typically disposed along a side of an LCD panel and drives the LCD panel in response to digital image signals, such as color signals R, G, B, and control signals received from a control circuit. Also, the LCD source driving circuit includes a plurality of latch circuits, a plurality of level shifters, a plurality of Positive voltage digital-to-analog decoders, a plurality of Negative voltage digital-to-analog decoders, a plurality of multiplexor (MUX) circuits, and a plurality of amplifiers. Thus, the LCD source driving circuit is capable of selectively latching digital image signals using the latch circuits with MUX circuit functions, thereby reducing the circuit footprint of source vertical channels within the LCD source driving circuit.

1. Field of the Invention
The present invention relates to a source driving circuit for a liquid crystal display (LCD), and more particularly, to a Thin Film Transistor (TFT) LCD source driving circuit which has a digital to analog converter
2. Description of the Related Art
A TFT-LCD source driver is a circuit that supplies video signals to an LCD pixel array. Digital video signals are inputted to the TFT-LCD source driver, and the source driver latches the digital video signals and outputs analog R, G, B component signals. Each color signal is digitized as 6 bits, and accordingly the total digital video signal is composed of 18 bits. In general, a liquid crystal display (LCD) includes a TFT-LCD panel 11, a gate driving circuit 12, a source driving circuit 13, and a control circuit 14, as shown in FIG. 1. The LCD panel 11 is a switching device in which pixels using thin film transistors (TFFs) are arranged in a matrix format. A plurality of source driving circuits 13 are arranged along the LCD panel 11 in rows and a plurality of gate driving circuits 12 are arranged along the LCD panel 11 in columns. The control circuit 14 transmits a clock signal CLK to the plurality of gate driving circuits 12 in parallel and transmits a vertical synchronization signal CLD to the one of the plurality of gate driving circuits 12 that is proximate to the control circuit 14.
Also, the control circuit 14 transmits the clock signal CLK, a digital image signals R, G, B, a latch signal CLA, and a polarity signal POL to the plurality of source driving circuits 13, and transmits a start pulse signal SP to the one of the plurality of source driving circuits 13 that is proximate to the control circuit 14.
The gate driving circuit 12 applies a first predetermined bias voltage to the TFT of the LCD panel 11 so as to turn on the TFT. While the TFT is turned on, the pixels are filled with electric charges when predetermined driving voltages are applied by the source driving circuits 13.
Next, the gate driving circuit 12 applies a second predetermined bias voltage to the LCD panel 11, the TFT is turned off and electric charges filled in the pixels are maintained.
The LCD panel 11 consists of 1024×768 pixels. If the LCD panel 11 is a color eXtended Graphics Array (XGA), eight or ten source driving circuits capable of outputting 384 signals are required.
An example of a conventional source driving circuit is disclosed in U.S. Pat. No. 6,008,801. Such a conventional source driving circuit will now be in a greater detail described with reference to FIGS. 2 and 3.
FIG. 2 is a block diagram illustrating a conventional source driving circuit 100 for an LCD. The conventional source driving circuit 100 includes a shift register unit 101, a latch circuit unit 102, a first multiplexor (MUX) circuit unit 103, a level shifter unit 104, a decoding unit 105, a second MUX circuit unit 106, and an amplifying unit 107.
The shift register unit 101 includes a plurality of shift registers SL1 through SLK, and receives a latch signal CLA from the control circuit 14 of FIG. 1 and outputs a plurality of latch signals EN1 through EN2K (K is a natural number more than 1).
The latch circuit unit 102 includes a plurality of latch circuits LA1 through LA3K and latches a digital image signal in response to the plurality of latch signals EN1 through EN2K. The digital image signal is an 18-bit digital data signal that contains six-bit signals R, G, B.
The level shifter unit 104 includes a plurality of level shifters LS1 through LS3K, and increases the voltage levels of the latched signals R, G, B and outputs the signals R, G, B so that the voltage levels fall within a range of voltage levels that can be recognized by the decoding unit 105.
The decoding unit 105 includes a plurality of first decoders PD1 through PD2K and a plurality of second decoders ND1 through ND2K. 64-level first reference voltages (not shown) having positive (+) polarities are applied to the plurality of first decoders PD1 through PD2K and 64-level second reference voltages (not shown) having negative (−) polarities are applied to the plurality of second decoders ND1 through ND2K.
The plurality of first decoders PD1 through PD2K selects and outputs one of the 64-level first reference voltages having positive (+) polarities, in response to the signals R, G, B. The plurality of second decoders ND1 through ND2K selects and outputs one of the 64-level second reference voltages having negative (−) polarities, in response to the signals R, G, B. As a result, analog image signals R1G1B1 through RKGKBK are output from the first decoders PD1 through PD2K and the second decoders ND1 through ND2K.
The amplifying unit 107 includes a plurality of amplifier circuits A1 through A3K. The plurality of amplifier circuits A1 through A3K increase the amount of electric currents and output the analog image signals R1G1B1 through RKGKBK while maintaining the voltage levels of these signals.
In FIG. 2, as shown in dotted line blocks C and D, the polarities of the analog image signals R1G1B1 through RKGKBK that are finally output from the source driving circuit 100 must be alternately changed.
The reason for alternately changing the polarities of these analog images is to prevent low mobility of the liquid crystal in the LCD panel 11 of FIG. 1. For instance, the mobility of the liquid crystal in the LCD panel 11 is degraded when first voltages having the same polarities are continuously applied to the LCD panel 11. The low mobility of the liquid crystal causes the liquid crystal not to respond when second voltages whose levels are different from those of the first voltages are applied to the LCD panel 11. To solve this problem, the source driving circuit 100 outputs the analog image signals R1+G1−B1+ through RK−GK+BK− illustrated in the dotted line block C, or outputs the analog image signals R1−G1+B1− through RK+GK−BK+ illustrated in the dotted line block D, in response to a polarity signal POL output from the control circuit 14.
The analog image signals R1G1B1 through RKGKBK must be output from the source driving circuit 100 in the sequence of a signal R, a signal G, and a signal B as illustrated in the dotted line blocks C and D.
The first MUX circuit unit 103 and the second MUX circuit unit 106 are installed in the source driving circuit 100 to output the analog image signals R1G1B1 through RKGKBK in the sequence of the signal R, the signal G, and the signal B while alternately changing the polarities of these analog image signals.
The first MUX circuit unit 103 includes a plurality of MUX circuits M1 through M3K and the second MUX circuit unit 106 includes a plurality of MUX circuits DM1 through DM3K.
The structures and operations of the first MUX circuit unit 103 and the latch circuit unit 102 will now be described with reference to FIG. 3.
FIG. 3 illustrates the relationship between the MUX circuits M1 and M2 and the latch circuits LA1 and LA2 included in two source vertical channels LA1 through A1 and LA2 through A2, shown in FIG. 2, that output an analog image signals R1 and G1, respectively, in response to digital image signals R and G, respectively.
As shown in FIG. 3, the latch circuit LA1 includes a first latch circuit 110 and a second latch circuit 120, which are connected to each other, and the latch circuit LA2 includes a first latch circuit 130 and a second latch circuit 140 which are also connected to each other.
The first latch circuit 110 includes a transmission gate 111 and a latch 112. The latch 112 includes inverters 113 and 114, a PMOS transistor P1, and an NMOS transistor N1. A latch signal EN1 is input to gates of an NMOS transistor of the transmission gate 111 and the PMOS transistor P1 of the latch 112. A latch signal EN1B is input to gates of a PMOS transistor of the transmission gate 111 and the NMOS transistor N1 of the latch 112. The inverters 113 and 114 are connected to the output of transmission gate 111. Also, the source of the PMOS transistor P1 and the drain of the NMOS transistor N1 are connected to the input terminal of the inverter 113, and the drain of the PMOS transistor P1 and the source of the NMOS transistor N1 are connected to the output terminal of the inverter 114.
The structure of the first latch circuit 130 and the second latch circuits 120 and 140 are identical with that of the first latch circuit 110, except that latch signals EN2 and EN2B, instead of the latch signals EN1 and EN1B, are input to the second latch circuits 120 and 140. Thus, their detailed descriptions will be omitted.
The MUX circuit M1 includes two transmission gates 151 and 152 and the MUX circuit M2 also includes two transmission gates 161 and 162. These transmission gates 151, 152, 161, and 162 are turned ON (i.e., conducting) or OFF in response to selection signals SEL and SELB.
The input terminals of the transmission gates 151 and 162 are connected to the output terminal of the second latch circuit 120 (e.g., the output of inverter 124); and the input terminals of the transmission gates 152 and 161 are connected to the output terminal of the second latch circuit 140 (e.g., the output of inverter 144).
The operations of the first and second latch circuits LA1 and LA2 and the MUX circuits M1 and M2 will now be described in a greater detail.
First, the latch signals EN1 and EN1B are enabled and the transmission gates 111 and 131 are turned ON. The transmission gate 111 receives a digital signal R and passes it to latch 112, and the transmission gate 131 receives a digital signal G and passes it to latch 132. Next, the latch signals EN1 and EN1B are disabled and the transmission gates 111 and 131 are turned off.
Also, when the latch signals EN1 and EN1B are disabled, the PMOS transistor P1 and the NMOS transistor N1 of the latch 112 are turned ON and a PMOS transistor P3 and an NMOS transistor N3 of the latch 132 are turned ON, whereupon digital signals R and G are latched (stored) by latches 112 and 132 respectively.
The latch 112 latches and stores the digital signal R and the latch 132 latches and stores the digital signal G.
(When the latch signals EN1 and EN1B are enabled again, the PMOS transistors P1 and P3 and the NMOS transistors N1 and N3 of the latches 112 and 132 are turned OFF and a new value of each of digital signals R and G may be stored in the respective latches.)
Next, when the latch signals EN2 and EN2B are enabled, the transmission gates 121 and 141 are turned ON. The transmission gate 121 outputs the stored digital signal R received from the latch 112 to the latch 122. The transmission gate 141 outputs the stored digital signal G received from the latch 132 to the latch 142.
Thereafter, the latch signals EN2 and EN2B are disabled, and the transmission gates 121 and 141 are turned OFF. When the latch signals EN2 and EN2B are disabled, the PMOS transistors P2 and P4 and the NMOS transistors N2 and N4 of the latches 122 and 142 are turned ON, whereupon digital signals R and G are latched (stored) by latches 120 and 140 respectively. The latch 122 latches and stores the digital signal R and the latch 142 latches and stores the digital signal G.
(When the latch signals EN2 and EN2B are enabled again, the PMOS transistors P2 and P4 and the NMOS transistors N2 and N4 of the latches 122 and 142 are turned OFF, and a new value of each of digital signals R and G may be stored in the respective latches.)
Next, when the control circuit 14 of FIG. 1 outputs a high-level polarity signal POL, the selection signals SEL and SELB are enabled. (SEL is enabled at a high logic voltage level; SELB is enabled at a low logic voltage level) The transmission gates 151 and 161 of the MUX circuits M1 and M2 are turned ON in response to the enabled selection signals SEL and SELB. The transmission gate 151 passes the digital signal R received from the latch 122; and the transmission gate 161 passes the digital signal G received from the latch 142.
If the polarity signal POL is at a low-level, the selection signals SEL and SELB are disabled and the transmission gates 152 and 162 are turned ON. The transmission gate 152 passes the digital signal G received from the latch 142; and the transmission gate 162 passes the digital signal R received from the latch 122.
As described above, the conventional source driving circuit 100 for an LCD requires the first and second MUX circuits 103 and 106 so as to output the analog image signals R1G1B1 through RKGKBK in the sequence of a signal R, a signal G, and a signal B while alternately changing the polarities of these analog image signals from positive (+) to negative (−) and vice versa. The inclusion of the first and second MUX circuits 103 and 106, however, results in an increase in the area (circuit footprint) of the source vertical channels of the source driving circuit 100 and a reduction in the available area of the semiconductor chip that such a source driving circuit 100 is fabricated on.
Further, as is apparent from FIG. 3, the latch signals EN1 and EN1B are applied to the transmission gages 111 and 131 and the latches 112 and 132 at the same time. Since the signals R, G, B each contain 6-bit digital data, and each source vertical channel handles one bit thereof, the latch signals EN1 and EN1B are each required to control the operation of a total of eighteen transmission gates and eighteen latches, thereby increasing loads driven by the latch signals EN1 and EN1B.

LCD source driving circuit having reduced structure including multiplexing-latch circuits


The present invention provides for reducing current spikes in a circuit when changing clocking frequencies. A first frequency is applied to a clock distribution network. A final frequency is selected. The first frequency is applied to a logic element over the clock distribution network. A hold signal is applied to the logic element. The clock rate of the clock distribution network is changed from the first frequency to the final frequency. The hold signal is unapplied to the logic element.

Power dissipation by a processor can raise various problems. The frequency of chip processing, the system clock of the chip, has increased over time. Presently, chips can run at 3 GHZ, 5 GHZ or more. This can lead to significant power consumption, and hence heat generation. It would be useful to be able to selectively and dynamically decrease processing speed to decrease power consumption and increase, say, battery life. Also, due to the increase of transistors and frequency of the chip, current spikes when switching from one processing speed to another processing speed can be a significant problem, especially when the switching is done quickly. Furthermore, when switching to a faster frequency from a slower frequency, the fast change of switching frequencies can cause voltage rails to fluctuate, which can create errors in the circuit.
In conventional technologies, there are various ways to change to a slower processing speed for a processor. One such way to change frequencies on a processor is to disable the processor entirely, and then change the settings of the PLL (phase locked loop) that is being used to drive the processor. However, shutting down the processor is expensive in terms of performance. Furthermore, it is better if the change in processing speeds occurs dynamically, that is without having to disable the circuit.
Other conventional technologies, therefore, changed processing speeds without entirely disabling the processor. In some previous technologies, they switched from one processing speed to another processing speed without using any intervening processing speeds to mitigate the current charge effect.
However, recently chip processing speeds have continued to increase. Therefore, the current spikes have become more of a problem. This can be compensated by adding more capacitors to the processor, but this makes the chip more expensive.
Therefore, there is a need to change from a first processing speed to a second processing speed in a manner that addresses at least some of the concerns of conventional processing speed switching.

This patent is subject to a terminal disclaimer.

Dynamic frequency scaling sequence for multi-gigahertz microprocessors

International Business Machines Corporation


A feed control method is provided for consumable electrode AC arc welding, in which the welding wire is fed at a predetermined wire feed rate, and a welding voltage applied to an arc is switched in alternation between positive polarity and negative polarity. In the method, a welding current setting signal is generated. The wire is fed at a first feed rate during a period of the positive polarity, whereas the wire is fed at a second feed rate different from the first feed rate during a period of the negative polarity.

1. Field of the Invention
The present invention relates to a feed control method for consumable electrode AC arc welding to obtain a desired bead shape.
2. Description of the Related Art
FIG. 5 is a current-voltage waveform diagram of consumable electrode AC arc welding. In the figure, (A) is a polarity switching signal Spn, (B) is the welding current Iw, (C) is the welding voltage Vw, and (D) is the welding wire feed rate Fw (cm/minute). The figure is for a case of short circuiting transfer arc welding, but substantially similar results are obtained for globular transfer welding and spray transfer welding. In the following explanation, the welding current Iw, welding voltage Vw, and output voltage E explained below refer to absolute values. Hence a statement "a value is large" means that the absolute value is large.
As shown in (A) in the figure, in consumable electrode AC arc welding, welding is performed while switching in alternation between an electrode positive polarity period Tep and an electrode negative polarity period Ten, according to a polarity switching signal Spn. At this time, as indicated in (D) in the figure, the feed rate Fw is constant, independent of the polarity.
As shown in (A) in the figure, at time t1, the polarity switching signal Spn goes to high level, switching to the electrode positive polarity EP, upon which, as shown in (B) in the figure, the welding current Iw for electrode positive polarity EP flows, and as shown in (C) in the figure, the welding voltage Vw of electrode positive polarity EP is applied between the welding wire and the base material. During the short circuit period Ts between times t1 and t2, as shown in (B) in the figure, the welding current Iw gradually increases, and as shown in (C) in the figure, the welding voltage Vw reaches a low short circuit voltage value of approximately several volts. During the arc period Ta between times t2 and t3, as shown in (B) in the figure, the welding current Iw gradually decreases, and as shown in (C) in the figure, the welding voltage Vw reaches the arc voltage value of approximately several tens of volts. Thereafter, until the electrode positive polarity period Tep ends at time t4, there is repetition of the short circuit period Ts and arc period Ta.
As shown in (A) in the figure, at time t4, the polarity switching signal Spn goes to low level, and when the welding power supply output switches to electrode negative polarity EN, an electrode negative polarity EN welding current Iw flows as shown in (B), and as shown in (C), the welding voltage Vw is applied. The short circuit period Ts between times t4 and t5 and the arc period Ta between times t5 and t6 are repeated as above until the end of the electrode negative polarity period Ten at time t7.
FIG. 6 shows an example of wire welding characteristics for electrode positive polarity EP and for electrode negative polarity EN. In the figure, the horizontal axis indicates the welding current average value for each polarity, and the vertical axis indicates the feed rate Fw. The figure shows results for MAG welding using an iron wire of diameter 1.2 mm. The following explanation references this figure.
As shown in the figure, the wire welding characteristics differ greatly for electrode positive polarity EP and for electrode negative polarity EN. As stated above, in consumable electrode AC arc welding, the feed rate Fw is a constant value independent of polarity, so that if for example the feed rate is set to Fw=350 cm/minute, the welding current average value for electrode positive polarity EP is Iep=140 A, and the welding current average value for electrode negative polarity EN is Ien=100 A. In FIG. 5, the average of the welding current value during the electrode positive polarity period Tep is the electrode positive polarity welding current average value Iep, and the average of the welding current value during the electrode negative polarity period Ten is the electrode negative polarity welding current average value Ien. In consumable electrode AC arc welding, the EN ratio Ren (%)=100×(Ten/(Tep+Ten)), which is the ratio of the above electrode positive polarity period Tep to the electrode negative polarity period Ten, may be varied to change the wire welding characteristics, so that a desired bead shape (penetration depth, reinforcement height, and similar) is obtained (see for example Japanese Patent Publication S62-55952, Japanese Patent Laid-open 2004-114088).
The welding current average value Iav over all periods (Tep+Ten) can be represented by the following equation, taking as parameters the electrode positive polarity welding current average value Iep, electrode negative polarity welding current average value Ien, and the EN ratio Ren.Iav=(Ien−Iep)×(Ren/100)+Iep  (1)
The numerical example explained above with reference to FIG. 6 is substituted into equation (1). That is, upon substituting Iep=140 A and Ien=100 A, the following is obtained.Iav=−0.4×Ren+100
This relation is plotted in the graph shown in FIG. 7. In the figure, the horizontal axis represents the EN ratio Ren, and the vertical axis indicates the welding current average value Iav. As is clear from the figure, when the EN ratio Ren changes, the welding current average value Iav varies significantly in a range of 100 to 140 A.
When forming beads into a desired shape on the workpiece, often the penetration depth and the area of the reinforcement portion are set to desired values. In general, the penetration depth changes with the welding current average value Iav, and the reinforcement area changes with the EN ratio Ren. However, as is clear from the figure, if the EN ratio Ren is changed in an attempt to set the reinforcement area, the welding current average value Iav also changes greatly at the same time, and the penetration depth also changes. That is, the penetration depth and the reinforcement area cannot be set independently to desired values. For this reason, numerous preparatory tests are necessary in order to set the bead shape to a desired value, and so considerable time has been required.

Feed control method for consumable electrode AC arc welding


A protective carrier (10) for portable objects has an interior layer (30) and an exterior layer (20) welded together to form a compartment (2) that is surrounded by inflatable air chambers (3). The compartment (2) has an opening in one end (62) through which objects are inserted. The open end (62) may be closed with a fluid-resistant seal (65) that rolls and is secured by buckles (40, 70), making the compartment (2) leak-resistant. The air chambers (3) may be inflated and deflated through a valve (100).

Embodiments disclosed herein generally relate to inflatable, reusable and leak-resistant carriers for transporting, shipping and storing liquid-containing articles and/or breakable articles.
In 2006 the Transportation Security Administration (TSA) imposed a 3-ounce restriction for liquids in carry-on airline luggage. This TSA restriction has highlighted the need for a reliable means of transporting bottled liquids in checked luggage. While there are many products and technologies available to protect items against breakage and leakage during commercial transport, they are not practical for consumer use due to size, expense, complexity and/or special equipment requirements.
Currently, passengers traveling with wine, alcohol, perfumes and other liquids must pack them in checked luggage or relinquish them to TSA authorities prior to boarding an aircraft. For passengers unaware or uninformed of the TSA rule, disappointing and costly losses are incurred. According to officials in Florida, the TSA stopped a daily average of about 150 bottles of liquor from being carried onto flights departing from South Florida's three major airports in 2007. This amounts to roughly $2.4 million annually in wasted consumer dollars in Florida alone.
Informed travelers who know of the restrictions are theoretically able to prevent the loss of their liquid articles to authorities by packing them in checked luggage. However, lack of acceptable carriers to transport these items has resulted in reduced purchases made while traveling, and significant risk of breakage, leakage and damage to surrounding articles for those who transport liquids with inadequate protection. For example, a passenger shopping in Italy may refrain from purchasing prized bottles of olive oil or wine for fear that hand-carrying the bottles would result in their confiscation by authorities, and packing the bottles in a suitcase could result in leakage or damage to clothing. It is well known that airlines have begun to require Styrofoam boxes for wine packed in suitcases due to the frequency of broken bottles. However, these Styrofoam containers cannot assure the integrity of bottled liquids, must be opened for inspection, and cannot contain liquids in the event a bottle breaks, cracks or leaks. A carrier that is safe against leaks would eliminate these problems.
Even in the absence of air travel restrictions, a convenient method of protecting liquids and breakables is still needed. Bottled liquids are often cumbersome and heavy, making them difficult to hand-carry, especially if there are multiple units. Consumers often transport liquids and/or breakable items by car, rail, boat, and other means. Bottled liquids are carried during sports activities including skiing, camping, fishing, hiking, and biking Accordingly, improved convenient leak-resistant carriers are needed.

Inflatable, reusable and leak-resistant carrier


An RFID tag that receives an RF signal from a reader is arranged to derive a threshold signal from a detected envelope of the RF signal, where the threshold signal is proportional to the detected envelope signal. The detected envelope signal is then compared to the threshold signal to derive a digital signal from the received RF signal. By maintaining the threshold signal proportional to the detected envelope signal, false bit detections due to ripple effect on the received signal and interference from other sources are reduced. The threshold signal may be derived employing a switched capacitor attenuator circuit.

Radio Frequency IDentification (RFID) systems typically include RFID tags and RFID readers (the former are also known as labels or inlays, and the latter are also known as RFID reader/writers or RFID interrogators). RFID systems can be used in many ways for locating and identifying objects to which the tags are attached. RFID systems are particularly useful in product-related and service-related industries for tracking large numbers of objects being processed, inventoried, or handled. In such cases, an RFID tag is usually attached to an individual item, or to its package.
In principle, RFID techniques entail using an RFID reader to interrogate one or more RFID tags. The reader transmitting a Radio Frequency (RF) wave performs the interrogation. A tag that senses the interrogating RF wave responds by transmitting back another RF wave. The tag generates the transmitted-back RF wave either originally, or by reflecting back a portion of the interrogating RF wave, in a process known as backscatter. Backscatter may take place in a number of ways.
The reflected-back RF wave may further encode data stored internally in the tag, such as a number. The response is demodulated and decoded by the reader, which thereby identifies, counts, or otherwise interacts with the associated item. The decoded data can denote a serial number, a price, a date, a destination, other attribute(s), any combination of attributes, and so on.
An RFID tag typically includes an antenna system, a power management section, a radio section, and frequently a logical section, a memory, or both. In earlier RFID tags, the power management section included a power storage device, such as a battery. RFID tags with a power storage device are known as active tags. Advances in semiconductor technology have miniaturized the electronics so much that an RFID tag can be powered solely by the RF signal it receives. Such RFID tags do not include a power storage device, and are called passive tags.
Digital information encoded onto the received RF signal is typically decoded in an RFID tag by detecting an envelope of the received RF signal and comparing the detected envelope to another analog signal. Usually, the received RF signal is at a baseline value. The information is encoded in a simple form by causing the RF signal to have a low value at predetermined periods corresponding to digital bit periods. Interference from other intentional and unintentional transmitters in the vicinity and ripple effect on the baseline may result in false bits being detected by the RFID tag.

RFID tag switched capacitor slicer threshold


A method of isolating detomidine (I) hydrochloride as a crystalline salt is provided. The method comprises hydrogenating in the presence of a catalyst of compound of formula (II) in aqueous solution comprising hydrochloric acid, concentrating the solution by distillation, optionally adding hydrochloric acid to the concentrated solution, cooling the concentrated solution and recovering the crystallized detomidine hydrochloride. The product can be recovered directly from aqueous solution with

Detomidine which is 4-[(2,3-dimethylbenzyl)]imidazole of formula I
is a well known pharmaceutical agent currently used as its hydrochloride salt in animal sedation.
The synthesis of detomidine is described in U.S. Pat. Nos. 4,443,466 and 4,584,383. The preparation of detomidine hydrochloride salt is described in U.S. Pat. No. 4,584,383, wherein detomidine obtained from the hydrogenation step is first recovered from alkaline solution as a free base after which the crystalline product is converted into its hydrochloride salt by treatment with HCl-isopropanol in ethyl acetate.

Detomidine hydrochloride crystallization method


A laminate product having both improved grease, oil, wax and solvent repellency and improved glueability and printability properties. The laminate comprises a substrate, at least one layer of a fluorine containing polymer moiety on at least one surface of the substrate and at least one layer comprising a latex on the at least one layer of a fluorine containing polymer moiety layer. Preferably there are more than one fluorine containing polymer moiety layers. Preferably there are more than one layers comprising a latex. A container is constructed from the said laminate. A process for decreasing the contact angle of grease, oil, wax and solvent involving applying the layers to a substrate.

The coating of substrates such as paper products with fluorochemicals to impart grease, oil, wax and solvent repellency has been known for some time. For example, Schwartz, "Oil Resistance Utilizing Fluorochemicals," TAPPI, Seminar Notes, 74, 71-75, (1987), discloses the use of commercially available FDA cleared fluorochemicals to impart resistance to low surface tension fluids on various substrates. U.S. Pat. No. 4,426,466 discloses treatment compositions containing fluorochemical carboxylic acid and epoxidic cationic resin to impart oil and water repellency to cellulosic materials. U.S. Pat. No. 4,529,658 discloses fluorochemical copolymers useful for imparting oil and water repellency to cellulosic and textile materials. U.S. Pat. No. 5,370,919 discloses fluorochemical compositions for imparting oil and water repellency to various substrates.
While these fluorochemical coatings are considered satisfactory for imparting grease, oil, wax and solvent repellency to substrates such as paper products, fluorochemical coatings generally suffer from the disadvantage of interfering with the glueability and the printability of the coated product.

Oil and grease resistant paper products and process for producing the products


A BOC signal acquisition and tracking apparatus and method. In the present invention, a BOC subcarrier, a QBOC subcarrier and harmonics thereof are used as subcarriers. Those subcarriers can be mixed with a received signal and integration result of each mixing result is calculated. Then, all the integration results are combined as a combined correlation. Alternatively, those subcarriers can be combined as a synthesized subcarrier. The synthesized subcarrier is mixed with the received signal, and the integration of the mixing result is calculated to obtain a synthesized correlation.

Nowadays, more than one Global Navigation Satellite System (GNSS) is available. A receiver supporting multi-specification LBS (location based service), wireless multimedia communication and broadcasting signals is becoming an expectation. Take multi-specification LBS as an example, such a receiver able to support multi-mode receiving for GNSS signals can enhance locating precision and access to more services. Among the GNSS systems, different signal frequency bands support different services. As more and more bands need to be supported, band overlapping occurs.
GPS is the U.S. navigation satellite system, which is a network of satellites continuously transmits high-frequency radio signals. The signals carry time and distance information that is receivable by a GPS receiver, so that a user can pinpoint the position thereof on the earth. Galileo, the emerging European satellite navigation system, offers higher signal power and more robust modulation that will enable users to receive weak signals even in difficult environments. When combined, Galileo and GPS will offer twice the number of satellite sources as currently available. This provides redundancy as well as greater availability for the user. The combination of GPS and Galileo basically has four bands, excluding SAR (Safe and Rescue) service. GPS and Galileo systems share some signal bands. That is, GPS and Galileo share some central frequencies and send signals on the same ones of carriers. For example, GPS L1 and Galileo E2-L1-E1 share the same band. To reduce inter-system and intra-system interference, specific modulation schemes are required. Binary offset carrier modulation (hereinafter simply referred to as "BOC") is a widely used method.
The BOC modulation is done by multiplying a pseudo-random noise (PRN) spreading coded signal (simply referred to as PRN coded signal hereinafter) with a square wave subcarrier (SC). The SC has a frequency which is multiple of the code rate of the PRN spreading code. FIG. 1 is a waveform diagram showing the BOC modulation. The BOC-sine (simply referred to as BOC) signal is generated by mixing a SC-sine and a PRN coded signal, while the BOC-cos (also referred to as QBOC, where Q indicates "quadrature-phase".) is generated by mixing an SC-cos and the PRN coded signal.
The BOC signal has a symmetric split spectrum with two main lobes shifted from the center frequency by the frequency of the subcarrier. The characteristics of the BOC signal are dependent on the spreading code chip rate, the subcarrier frequency, and the subcarrier phasing within one PRN code chip. The common notation for a BOC-modulated signals in the GNSS field is represented as BOC(fc, fs), where fc is the code chip rate, and fs is the frequency of the subcarrier. Both fc and fs are usually represented as a multiple of the reference frequency 1.023 MHz. Therefore, the BOC signal can also be represented as BOC(n,m), where n is the multiple of 1.023 MHz for the PRN code chip rate fc, and m is the multiple of 1.023 MHz for the subcarrier fs.
For satellite signal navigation, the BOC signal is preferably applied in tracking under white noises. Such scheme provides better inherent multipath mitigation compared to the spreading code alone. However, BOC scheme makes acquisition and tracking more difficult due to a multiple peak autocorrelation phenomenon. The presence of the subcarrier in the BOC signal introduces secondary peaks in a range of −1/+1 chip in BOC autocorrelation. FIG. 1 is a diagram showing autocorrelation of BOC(1,1). That is, BOC(1,1) correlates with BOC(1,1). As shown, there are two troughs at both sides of the main peak in the middle. To calculate correlation power, square of correlation is usually used. Accordingly, the two troughs will cause two secondary peaks in view of correlation power. Such secondary peaks may cause a problem of mis-lock. That is, a receiver may lock the secondary peak rather than the main peak, and therefore resulting in erroneous tracking. A significant deviation of approximately 150 m would occur in the range measurement. Such an error is unacceptable in navigation.

BOC signal acquisition and tracking method and apparatus


A method for analyzing medical image includes obtaining a plurality of surface fronts on an object, such points being disposed in a three dimensional volume in the object; varying the volume of each one of the points such volumes combining into a common volume; and terminating the process when the common volume reaches boundaries of the object.

As is known in the art, medical image analysis plays an increasingly prominent role in Computer Aided Diagnosis (CAD) and therapy planning. As a preliminary stage of the analysis, segmentation of structures from medical images and reconstruction of these structures are difficult due to the large volume of the data involved and the complexity of the anatomic shapes of interest.
Three-dimensional (3D) visualization and labeling of rib structures, for example, in a CAD system provide important information for radiologists since they need to report any pathology pertaining to bones in a chest CT scan. The ribs have valuable properties common to bone tissues, i.e., they are rigid and stable in shape, and map to prominent intensities in CT data. Further, rib structures are highly ordered and symmetrical. Because of these features, rib feature group can be used for reliable registration and reference. To make full use of the structural advantages of the ribs, they should be extracted and labeled individually. There are 12 pairs of rib structures in a human body with 8-11 pairs visible in a chest CT volume dataset. They are connected at one end with the spine, and the upper pairs are also connected to the sternum.

Method for analyzing medical image data using level set


A control system is provided for a vehicle including an autonomous emergency braking system, characterized in that the control system includes: a brake control arrangement adapted to apply a friction-estimating braking when the autonomous emergency braking system has initiated a possible intervention; a brake force capacity estimation arrangement adapted to estimate the brake force capacity of the vehicle as a function of longitudinal wheel slip based on the applied friction-estimating braking; a road information arrangement adapted to obtain information about road curvature ahead of the vehicle; a lateral tyre force prediction arrangement adapted to predict lateral tyre force needed during autonomous emergency braking based on the obtained information about road curvature; and a brake strategy adaptation arrangement configured to adapt the brake strategy of the autonomous emergency braking system based on the estimated brake force capacity and the predicted lateral tyre force needed.

The invention relates to a control system and method for a vehicle comprising an autonomous emergency braking system. The invention can for example be applied in heavy-duty vehicles, such as trucks, buses and construction equipment.
An autonomous emergency braking (AEB) system, which may also be referred to as an advanced emergency braking system (AEBS), is an autonomous road vehicle safety system that monitors the traffic situation ahead of a vehicle and that automatically apply the vehicle's brakes when certain conditions are fulfilled in order to avoid or mitigate accidents. However, the AEBS assumes that certain conditions apply. For example, the test procedure for AEBS according to Regulation No 131 of the Economic Commission for Europe of the United Nations (UN/ECE) states that the vehicle shall travel in a straight line for at least two seconds prior to the functional part of the test. Also, the AEBS has an emergency braking phase with a deceleration of at least 4 m/s2.
Furthermore, US2013173132 (Yuasa et al.) discloses a braking force control apparatus which controls a braking force applied to a vehicle based on a relation thereof with an obstacle ahead of the vehicle, irrespective of a braking operation of a driver, wherein a lateral force is predicted which can be generated in cases where avoidance steering is carried out by the driver, in order to avoid an obstacle which has been detected, and an actual braking force actually applied to a longitudinal direction of the vehicle is limited in accordance with a braking force which can be applied in the longitudinal direction of the vehicle and which is calculated based on the lateral force thus predicted and on a friction of the vehicle with respect to a road surface on which the vehicle is running.
It is desirable to provide an improved control system and method for a vehicle comprising an autonomous emergency braking system, which control system and method in particular can take "non-ideal" road conditions into account.
According to the first aspect of the invention, there is provided a control system for a vehicle comprising an autonomous emergency braking system, wherein the control system comprises: brake control means adapted to apply a friction-estimating braking when the autonomous emergency braking system has initiated a possible intervention; brake force capacity estimation means adapted to estimate the brake force capacity of the vehicle as a function of longitudinal wheel slip based on the applied friction-estimating braking; road information means adapted to obtain information about road curvature ahead of the vehicle; lateral tyre force prediction means adapted to predict lateral tyre force needed during autonomous emergency braking based on the obtained information about road curvature; and brake strategy adaptation means configured to adapt the brake strategy of the autonomous emergency braking system based on the estimated brake force capacity and the predicted lateral tyre force needed.
The present invention is based on the understanding that applying a "standard" autonomous emergency braking (e.g. the aforementioned ≥4 m/s2 deceleration) when an object is detected in a curve ahead of the vehicle may cause the vehicle to skid off the road (or leave its lane) because the applied braking may severely reduce the lateral tyre force, which lateral tyre force is needed to stay on the road (or in the lane). To this end, by predicting lateral tyre force needed during emergency braking based on information about road curvature ahead of the vehicle, the brake strategy of the autonomous emergency braking system may be adapted so that the vehicle does not skid off the road (or lane) during the emergency braking in the curve. Furthermore, by applying the friction-estimating braking when the autonomous emergency braking system has initiated a possible intervention, the actual road friction at the time and place for this particular intervention may be taken into account. If the friction is relatively low (e.g. because of wet, icy or snowy road conditions) and/or a significant road curvature is identified ahead of the vehicle, the brake strategy may typically be adapted so that the autonomous emergency braking is initiated earlier and with a lower longitudinal brake force than under ideal conditions (dry, straight road). Overall, the present control system may reduce the risk of accidents when autonomous emergency braking is applied under non-ideal conditions. Furthermore, a more accurate distance to stop position can be estimated based on the adapted brake strategy.
The information about road curvature ahead of the vehicle may be obtained from a camera of the vehicle. An advantage of using a camera is that the actual road curvature ahead of the vehicle is detected. Alternatively or complementary, the information about road curvature ahead of the vehicle may be obtained from a navigation system of the vehicle. The navigation system may for example be a built-in GPS. An advantage of using the navigation system is that such a navigation system may already be present in a vehicle, whereby the control system may utilize already existing infrastructure in the vehicle.
The information about road curvature ahead of the vehicle may include a radius r. The lateral tyre force Fy needed may then be predicted using the formula Fy=(mv×2)/r, where m is the mass of the vehicle and vx is the speed of the vehicle.
The lateral tyre force prediction means may be adapted to predict the lateral tyre force by repeatedly predicting lateral tyre forces towards a desired collision free state of the vehicle relative to an object detected by the autonomous emergency braking system in an ego lane of the road ahead of the vehicle. In this way, the brake strategy may continuously be updated during the intervention, for example to take into account that reduced speed of the vehicle reduces the needed lateral tyre force and/or that the curvature (radius) of the road may change. A reduced radius results in increased lateral tyre force, whereas an increased radius results in decreased lateral tyre force. A 'collision free state' may be construed as stop position of the vehicle relative to a stationary object detected by the autonomous emergency braking system, or a state wherein time to collision (TTC) between the vehicle and a moving object is infinite. An 'ego lane' may be construed as the lane in which the vehicle is travelling.
The friction-estimating braking may be applied only to a certain wheel axle of the vehicle, such as a tag or pusher axle. An advantage of this is that the influence of the friction-estimating braking on the vehicle's normal behaviour and stability may be reduced.
The friction determination means may be adapted to apply the friction-estimating braking directly when, or a predetermined time after, the possible intervention is initiated. An advantage of this is that the friction-estimating braking may function as haptic warning that an autonomous emergency braking system intervention has started. The friction-estimating braking may also be part of a pre-brake phase of the autonomous emergency braking system. Furthermore, since the friction-estimating braking is applied only in conjunction with the autonomous emergency braking system intervention, there is no nuisance fuel consumption increase or brake-disc wear.
The vehicle may be an articulated vehicle comprising a trailer, wherein the brake strategy adaptation means is configured to adapt the brake strategy such that there is enough friction left to maintain trailer stability. The required friction may be calculated as Fy=(mtrailerv×2)/r, wherein mtrailer is the mass of the trailer, vx is the speed of the vehicle, and r is the radius of the road curvature.
The control system may further comprise alerting means adapted to alert a driver of the vehicle if the autonomous emergency braking system determines, based on the adapted brake strategy, that the vehicle cannot brake to avoid an object detected by the autonomous emergency braking system. The alert means may for example be adapted to send out a visual and/or acoustic warning that an accident cannot be avoided by braking and that steering is the only option left. Since the control system takes real conditions into account (friction and road curvature), a more accurate warning may be issued.
The control system may further comprise assistance means adapted to assist a driver in a steering manoeuvre to avoid an object detected by the autonomous emergency braking system by automatically brake individual wheels of the vehicle to increase or decrease yaw motion of the vehicle needed to avoid the object if the autonomous emergency braking system determines, based on the adapted brake strategy, that the vehicle cannot brake to avoid the object detected by the autonomous emergency braking system. This may be accomplished by tightening the reference yaw rate band for yaw control of the vehicle, by a feedback control of desired yaw rate with excluded deadband around the reference yaw rate calculated from vehicle speed and steering wheel angle using a simple bicycle model. The braking of the assistance means is then mainly correcting under/over steer, which may increase the chance of successful steering avoidance manoeuvre.
According to a second aspect of the present invention, there is provided a vehicle comprising a control system according to the first aspect.
According to a third aspect of the present invention, there is provided a control method for a vehicle comprising an autonomous emergency braking system, which method comprises the steps of: applying a friction-estimating braking when the autonomous emergency braking system has initiated a possible intervention; estimating the brake force capacity of the vehicle as a function of longitudinal wheel slip based on the applied friction-estimating braking; obtaining information about road curvature ahead of the vehicle; predicting lateral tyre force needed during autonomous emergency braking based on the obtained information about road curvature; and adapting the brake strategy of the autonomous emergency braking system based on the estimated brake force capacity and the predicted lateral tyre force needed. This aspect may exhibit the same or similar features and/or technical effects as the other aspects of the invention.
According to a forth aspect of the present invention, there is provided a computer program comprising program code means for performing the steps of the control method of the third aspect when said program is run on a computer.
According to a fifth aspect of the present invention, there is provided a computer readable medium carrying a computer program comprising program code means for performing the steps of the control method of the third aspect when said program is run on a computer.
Further advantages and advantageous features of the invention are disclosed in the following description and in the dependent claims.

Control system and method for a vehicle comprising an autonomous emergency braking system


A variable speed wind power generation system including a wind turbine, a generation power command unit for generating a generation power command value based on a state quantity of the wind turbine and a generator control unit for controlling the power converter for controlling electric power of the generator, wherein the generator control unit operates to regulate the generation power of the generator in order to change the generation power amount according to the generation power command value.

The present invention relates to a wind power generation system with variable rotating speed of a generator.
A wind power generation apparatus receives wind energy on its blades and then converts it into rotational energy to generate rotational torque at a rotor of a generator. The wind power generation apparatus produces electric power from wind-induced torque by generating a magnetic field at the rotor (or stator or both of them). It supplies the produced electric power to a power system or load through electric wires.
Since a wind power generation system utilizes wind energy, it has a problem that the generated power fluctuates resulting in voltage fluctuation of the power system connected.
U.S. Pat. No. 5,083,039 discloses a wind power generation system which utilizes torque control for generation control and performs power factor control in order to prevent voltage fluctuation.

Variable speed wind power generation system


A method and apparatus for generating pulses that includes a circuit having a dynamical transfer function is disclosed. The circuitry exhibits oscillatory behavior when its operating point is forced to an unstable region of the transfer function by means of manipulating the transfer function. In an embodiment, a voltage source signal is used to manipulate the transfer function of the circuit. By manipulating the transfer function, the operating points can be dynamically set in the stable or the unstable region.

This invention relates generally to techniques for generating pulses and more specifically to techniques for converting arbitrary analog waveforms to produce sequences of pulses.
Free running oscillations based on the relaxation oscillator approach are known. Many circuit configurations are possible. One example is a circuit comprising a tunnel diode connected in series with an inductor and a constant voltage source, to produce a periodic square waveform that has a constant frequency. U.S. Pat. No. 3,312,911 discloses a tunnel diode relaxation oscillator that produces a relaxation oscillation with the desired polarity. An op-amp based relaxation oscillator is described in U.S. Pat. No. 3,967,210. This oscillator is capable of producing oscillations in several selectable modes at different frequencies. All of these oscillators can be categorized as a free running oscillator.
The method and apparatus for a communication system disclosed in U.S. application Ser. No. 09/429,519 uses a controlled relaxation oscillator. In that application, the circuit is able to generate a number of desired oscillations followed by a substantially instant cessation of oscillatory behavior in response to an input waveform. Similarly, the circuit can also respond substantially instantly to yield a desired oscillatory behavior substantially without transients. However, the circuit disclosed in that application has reactive input impedance. The circuit is therefore frequency dependent which is not desirable under some conditions. In the U.S. application Ser. No. 09/805,845, a circuit is disclosed that has similar transfer function properties and which also possesses a resistive input impedance.
The approaches disclosed in the foregoing co-pending and co-owned application produce oscillatory behavior (i.e. generate groups of one or more pulses) when the operating point of the circuit is forced to the unstable region portion of the transfer characteristic. The oscillatory behavior ceases by forcing the operating point to a stable operating region portion of the transfer characteristic. However, the operating point of the disclosed circuits is determined solely by the input voltage. In some applications, it is desired to have the additional freedom to control the operating point via an additional input. As an example, an additional input that serves as an enable/disable control might be useful. Hence, there is a need for a circuit having transfer function characteristics that can be controlled dynamically.
In accordance with the present invention, producing pulses from analog waveforms includes providing a circuit having a transfer function characterized by having a stable operating region and an unstable operating region. The circuit is made to operate at a first operating point. The transfer function is adjusted by application of a signal to the circuit. In response, the circuit is made to operate at a second operating point. Either or both operating points can produce oscillatory behavior in the circuit. In one embodiment of the invention, the oscillatory behavior manifests itself as the production of groups of one or more pulses.
Further in accordance with the invention, producing information from an analog signal includes the foregoing to produce groups of one or more pulses. A decoding is made of the pulses to produce symbols representing the information.

Method and apparatus for generating pulses using dynamic transfer function characteristics


In certain embodiments, a radial configuration of time based information is displayed by a computing system in a graphical user interface. The radial configuration includes a graphical timeline spirally disposed about at least one axis point in the graphical user interface. In certain examples, the graphical timeline represents a time period and includes a first section representing a first portion and a second section representing a second portion of the time period. In certain other embodiments, a radial configuration of time based information is displayed by a computing system in a graphical user interface. The radial configuration represents a time period and includes a first radial section and a second radial section disposed about an axis point at different radial distances from the axis point. The first radial section represents a first portion and the second radial section represents a second portion of the time period.

Advances in electronic technologies and devices have put a wide variety of applications, features, and information at people's fingertips. The proliferation of such applications, features, and information on electronic devices has challenged designers of user interfaces for the electronic devices. For example, a common challenge has been to design and implement user interface elements that provide an intuitive and appropriate balance of information and functionality. The difficulty of the challenge is exacerbated for electronic devices that have limited resources and/or that are small in size such as a mobile phone device.

Systems and methods for radial display of time based information


A fiber reinforced polyamide resin composite material is suitable for use as a molding material. A liquid lactam added with an anionic polymerization catalyst and another liquid lactam added with an activator are supplied to an impregnation chamber while being mixed together at a predetermined or selected ratio. In the impregnation chamber, long reinforcing fibers are impregnated with the mixed liquid to form a strand. Then a coating layer of thermoplastic resin is continuously formed all over the outer peripheral surface of the strand, after which the strand is introduced into a heated polymerization chamber for anionic polymerization of the mixed liquid in the reinforcing fibers. The strand is cut into pellets of a predetermined or selected length after or without removing the coating layer. The composite material manufactured by this method has a high adhesive strength between the reinforcing fibers and the resin and provides excellent physical properties to ultimate moldings.

The present invention relates generally to a fiber reinforced polyamide resin composite material and its manufacturing method and, more particularly, to a composite material which is suitable for use in molding articles and in which an adhesion between resin and reinforcing fibers is fast or firm to provide excellent mechanical strength, and a method for manufacturing such a composite material with high productivity.
By virtue of their light weight, excellent mechanical strength, corrosion resistance and so forth, various composite materials consisting of reinforcing fibers and thermoplastic resins are widely used for manufacture of electrical parts, auto parts, etc. It is well-known in the art that the fiber reinforced resin compositions for such uses are roughly divided into two types: one is a short-fiber reinforced pellet which is obtained by mixing short glass fibers with molten thermoplastic resin in an extruder, extruding therefrom the mixture in the form of a rod and cutting it into pellets of a predetermined shape; and the other is a long-fiber reinforced pellet which is obtained by impregnating long reinforcing fibers with molten thermoplastic resin, or liquid thermoplastic resin dissolved in a solvent, and then cutting it into a predetermined length.
The short-fiber reinforced pellet is defective in that it is inferior to the long-fiber reinforced pellet with regard to reinforcement effect, because the reinforcing fibers are cut short in the pelletization step and in the extruder during injection molding. On the other hand, manufacture of the long-fiber reinforced pellet involves problems such as difficulty in the impregnation of the long reinforcing fibers with the molten thermoplastic resin or, in case of impregnation with the thermoplastic resin in the form of a solution, difficulty in removal of the solvent and insufficient bond strength between the resin and the reinforcing fibers after the removal of the solvent.
As an improved method for impregnation of the resin into the reinforcing fibers, in particular, there is disclosed in H. Ishida and G. Rotter, "RIM-pultrusion of thermoplastic matrix composite," SPI 43rd Ann. Conf., 6-E (1988) a fiber reinforced nylon-6 RIM pultrusion method according to which two low-viscosity, reactive liquid monomers are mixed in a mixing chamber and the mixture is impregnated into the reinforcing fibers.
With the method disclosed in the above-mentioned literature, however, pot life after mixing the two liquids is relatively short. This poses a problem such as a limitation on the transfer of the mixture from the mixing chamber to an impregnation chamber or unbalanced supply of the mixture to the impregnation chamber. Besides, polymerization rate is low which results in low productivity, clogging of a die in the polymerization step and an increase in drawing resistance.
The inventors herein have been devoted to studying a fiber reinforced polyamide resin composite material and its manufacturing method which are free from the above-noted problems and, as the result of their studies, they have now made the present invention.

Fiber reinforced polyamide resin composite material and method of manufacture thereof


The present invention includes a speech recognition system comprising a light element, a power control switch, the power control switch varying the power delivered to the light element, a controller, a microphone, a speech recognizer coupled to the microphone for recognizing speech input signals and transmitting recognition results to the controller, and a speech synthesizer coupled to the controller for generating synthesized speech, wherein the controller varies the power to the light element in accordance with the recognition results received from the speech recognizer. Embodiments of the invention may alternatively include a low power wake up circuit. In another embodiment, the present invention is a method of controlling a device by voice commands.

The present invention relates to speech recognition and techniques for configuring and controlling devices incorporating speech recognition. In particular, the embodiments of the present invention relate to methods and apparatuses for controlling the operation of a device by voice commands.
Speech recognition systems are electronic systems implemented in hardware, software or a combination of hardware and software that allow a machine to recognize speech inputs. Speech recognizers can be used to control the behavior of an electronic system in accordance with the particular speech inputs received. For example, a speech recognition system may recognize a certain number of utterances (i.e., words or phrases). The set of utterances that a recognizer can understand is often referred to as the "recognition set." When a user speaks to a recognizer, the recognizer may produce different results (typically electronic signals or software states) corresponding to whether or not the input speech was an utterance in the recognition set, and additionally, but not necessarily, which of the utterances in the recognition set was received.
Typically, when a speech recognition system is powered on, the speech recognizer is always on and always listening for utterances in the recognition set. However, a speech recognizer that is always on and always listening for commands has two problems:
1. In battery operated products, the current drained by analyzing each sound can quickly wear down batteries.
2. In all products there is an issue of the recognizer incorrectly interpreting unintended sounds as commands (false accepts). This issue is exacerbated in products that are always on and always listening.
To address the first issue, battery operated speech recognition products typically require a button press or other switch to turn on the recognizer. These devices typically power down after some time if no command is recognized, thereby saving battery life. This approach, however, is self-defeating, because it requires the use of ones eyes, hands, and feet to locate the speech recognition device and turn it on. Examples of the use of such speech recognition in consumer electronic products include U.S. Pat. Nos. 6,188,986 and 6,324,514 for electrical switches, U.S. Pat. Nos. 6,101,338 and 5,980,124 for cameras, U.S. Pat. No. 4,771,390 for cars, and U.S. Pat. Nos. 6,526,381 and 5,199,080 for remote controls.
Improvements in speech recognition technology have decreased the false accept rate in continuously listening products. To further decrease this false accept rate, developers utilize "dual triggered" or "gated" approaches, in which the recognizer first listens for a trigger word, the occurrence of which activates a second recognition set whose output controls the device of interest. By this two step process, false accepts are less likely because wrong utterances must pass through two hurdles instead of one to activate the device. However, this introduces the problem of increasing the false reject rate, because the "right" words also must pass the double hurdle. Furthermore, this approach makes usage more cumbersome because a series of words must be recalled to activate the device.
To alleviate these problems, speech recognition has been used in combination with auxiliary sensing devices to improve recognition accuracy while decreasing false trigger rates. For example, U.S. Pat. Nos. 6,532,447 and 5,255,341 describe an auxiliary sensing device that is a proximity detector that turns on a speech recognizer in a cell phone and an elevator, respectively, when a potential user is nearby.
A proximity detector can also assist in saving battery life by keeping the device in a low power mode, but will not necessarily help the false triggers and recognition accuracy when people are in its vicinity. One such example is a speech recognizer that provides voice control of lights in a room even when there are people in the room; the recognizer would automatically go on, and conversations could created false triggers. Other types of sensors could be more effective in preventing false triggers. For example, a voice activated lamp or nightlight could be enabled only when needed during darkness to prevent false triggers when it is not needed (during daylight). Such a situation is more complex because one auxiliary sensing device for controlling the speech recognizer, such as the light sensor, is not sufficient to control its full operation. This occurs when the light sensor that activated the speech recognizer during the darkness gets deactivated by the light of the lamp. Once the room is illuminated by the lamp, the light detector would deactivate the recognizer, so the lights would have to be turned off manually and the benefit of turning the light off with a voice command would be lost.
The current state of the art for controlling the operation of a speech recognizer with an auxiliary sensing device (e.g. proximity sensor) is described by the block diagram of FIG. 1, in which power is provided to speech recognizer 3 from power supply 5 through switch 7 whose operation is controlled by auxiliary sensing device 9. When switch 7 is closed by auxiliary sensing device 9, speech recognizer 3 is powered to receive and analyze audio signals coming from microphone 1. The output of speech recognizer 3 controls the operation of device under control 11 when appropriate speech commands are spoken into the microphone. For example, auxiliary sensing device 9 may be the proximity sensor of U.S. Pat. No. 5,255,341, which causes speech recognizer 3 to be powered on when a potential user is in the proximity of an elevator, which is device 11 of FIG. 1. Thus, when a person is near the elevator and only when a person is near the elevator, the recognizer is activated to receive audio signals from microphone 1, which controls the operation of the elevator. The function of auxiliary sensing device 9 in this example is to minimize false commands to the elevator at times when no one is near but when false triggers from background noise might otherwise activate its operation.
The device described by FIG. 1 is not adequate to control the operation of a speech recognizer in all circumstances. For example, consider the case of a device under control 11 being a lamp that is controlled by commands to speech recognizer 3. Without a mechanism for controlling the power fed to the recognizer, it would consume unnecessary power and would false trigger the lamp off and on in response to extraneous noises or conversations when people are near. Thus, auxiliary sensing device 9 might be a light sensor that causes switch 7 to close only when the room is dark, because there is no need to command the lamp when the room is light. In this case, when the room is dark, speech recognizer 3 is powered from power supply 5 through switch 7 to control the lamp operation via verbal commands received by it from microphone 1. Thus, a person can turn on a lamp in the middle of the night without having to find it and push a button.
A problem arises when this same person wishes to turn off the lamp to go back to sleep. In this case auxiliary sensing device 9 may be activated to close switch 7 by the light coming from the lamp. So the only method for the person to turn off the lamp is to reach for it and push a button. This requirement greatly diminishes the utility of a lamp that is controlled by a speech recognizer.
Thus, there is a need for more sophisticated methods and apparatuses for controlling the operation of a device by voice commands.

System and method for controlling the operation of a device by voice commands


A filter of the present invention comprises a multilayer substrate, two terminals, a ground conductor and a hybrid resonator. The multilayer substrate includes a plurality of conductor layers and a dielectric configured to isolate said plurality of conductor layers from each other. The hybrid resonator is disposed in the multilayer substrate and comprises a first and a second resonant elements and a coupling strip connecting the first and said second resonant elements. Each resonant element comprises a signal via, a group of ground vias and an artificial dielectric. Each signal via is disposed through the multilayer substrate. Each group of ground vias is disposed through the multilayer substrate and configured to surround the signal via. Each artificial dielectric is disposed in the multilayer substrate and between the signal via and the group of ground vias. The artificial dielectric comprises a conductive plate connected to the first signal via and an isolating slit isolating the first conductive plate from the group of ground vias.

A high-selective filter is a crucial component in wired and wireless communication systems, because they control the usage of frequency spectrum there. Due to a close proximity of the operation frequency band of functional elements in a device, the frequency characteristics skirt of the filter applied has to be sharp.
However, providing such electrical performance is a complex problem in high-density and multifunctional devices, because additional resonant elements are required.
Moreover, the use of such additional elements, which can improve the filter skirt sharpness, can lead to the increase of the in-band insertion losses that can be unac-ceptable for real applications.
Japanese Patent JP4367660 (U.S. Pat. No. 7,705,695B2) discloses composite via structures and filters based on these structures, which are formed in multilayer substrates. Compactness of resonant elements in these structures is provided by conductive plates connected to the signal via forming in such way an artificial dielectric of a high permittivity.
PCT Laid Open Patent Publication WO 2010/073410 discloses via structures and filters based on these via structures, in which an artificial dielectric of a high permittivity is formed by corrugated conductive plates connected to the signal via.
PCT Laid Open Patent Publication WO/2011/010393 discloses resonant elements and filters based on these elements, in which an artificial dielectric is formed by double corrugated surface obtained by the corrugation of both the signal plates and ground plates.
Above-mentioned structures are miniature and cost-effective ones. However, it is important to provide such type of resonators in a filter which can improve its selectivity.

Hybrid resonators in multilayer substrates and filters based on these resonators


An insert may include an outer sleeve that includes a first tubular portion and a first disk portion perpendicular to the first tubular portion at an end of the first tubular portion. An inner sleeve includes a second tubular portion and a second disk portion perpendicular to the second tubular portion at an end of the second tubular portion. The second tubular portion of the inner sleeve may be configured to be inserted in the first tubular portion of the outer sleeve. The first disk portion of the outer sleeve may include a first surface and a second surface, wherein the second surface includes a recess configured to accommodate the second disk portion of the inner sleeve when the second tubular portion is inserted in the first tubular portion.

Panels used on aircrafts may be coupled to one another using fastening devices. For example, interior floor panels of a passenger cabin in an aircraft may be made of carbon fiber honeycomb panels mounted to a seat track below with fastening assemblies and devices. Manufacturers are often faced with challenges due to corrosion concerns of such fastening assemblies and the surrounding areas of the panels because of the environment in which the aircrafts are exposed on a regular basis and because of the type of material with which they are made. Therefore, corrosion resistive techniques for mounting panels in an aircraft are desired.

Structural insert reinforcement systems and methods