The present invention includes a micro-actuator assembly. The micro-actuator assembly includes a planar micro-actuator and a vertical micro-actuator. The planar micro-actuator provides at least one planar micro-actuator arm for coupling to a slider. The vertical micro-actuator couples with the planar micro-actuator arm. The planar micro-actuator arm supports moving the slider in a planar direction. The vertical micro-actuator supports moving the slider, through the micro-actuator arm, in a vertical direction. The planar micro-actuator may include two planar micro-actuator arms. It is preferred that at least one of the micro-actuators include a piezoelectric device. The vertical micro-actuator preferably includes a bulk piezoelectric device for cost reasons. The vertical micro-actuator may include a thermoelectric device supporting vertical slider movement. The invention includes manufacturing head gimbal assemblies, actuator arms, voice coil actuator assemblies, and hard disk drives. The hard disk drives, actuator assemblies, actuator arms, and head gimbal assemblies, are products of these processes.

1. Field of the Invention
The present invention relates generally to micro-actuators positioning sliders in a hard disk drive and, more particularly, to a micro-actuator capable of three-dimensional positioning of a slider.
2. Background Information
Modern hard disk drives may have one or more disks. Each disk may have two disk surfaces in use. The hard disk drives also include a servo controller that drives a voice coil actuator to position a read-write head near a track on the surface of a rotating disk. The read-write head communicates with the servo controller, providing feedback, which is used in controlling the read-write head's positioning near the track. The read-write head is embedded in a slider, which floats on a thin layer of air, known as an air bearing, a very short distance above the rotating disk surface.
The trend in the hard disk drive industry is to increase the areal density of the rotating disk surfaces. This is usually achieved by decreasing the flying height of the read-write head above the rotating disk surface, thus reducing the air bearing. Currently read-write heads fly at about 10 nano-meters (nm) from the rotating disk surfaces.
There are problems with flying the read-write heads and sliders so near to the rotating disk surfaces. Occasionally, the read-write heads can contact the disk surface, which tends to reduce the reliability of the data stored on the disk, and possibly damage the read-write head. Contact between the read-write heads and the disk surface they access needs to be minimized to insure the reliability of the hard disk drive.
A voice coil actuator typically includes a voice coil, which swings at least one actuator arm in response signals from the servo controller. Each actuator arm includes at least one head gimbal assembly typically containing a read-write head embedded in a slider. Each disk surface in use has an associated slider, coupled to an actuator arm. The head gimbal assembly couples to a load beam coupled to the actuator arm in the voice coil actuator.
Today, the bandwidth of the servo controller feedback loop, or servo bandwidth, is typically in the range of 1.1 K Hz. Extending servo bandwidth increases the sensitivity of the servo controller to drive the voice coil actuator to finer track positioning. Additionally, it decreases the time for the voice coil actuator to change track positions. However, extending servo bandwidth is difficult, and has not significantly improved recently. As areal densities increase, the need to improve track positioning increases.
One answer to this need involves integrating a micro-actuator into each head gimbal assembly. These micro-actuators are devices typically built of piezoelectric ceramic materials, often including lead, zirconium, and tungsten. The piezoelectric effect generates a mechanical action through the application of electric power. The piezoelectric effect of the micro-actuator, acting through a lever between the slider and the actuator arm, moves the read-write head over the tracks of the rotating disk surface.
The micro-actuator is typically controlled by the servo-controller through one or two wires. Electrically stimulating the micro-actuator through the wires triggers mechanical motion due to the piezoelectric effect. The micro-actuator adds fine positioning capabilities to the voice coil actuator, which effectively extends the servo bandwidth. In the single wire approach, the servo-controller provides a DC (direct current) voltage to one of the two leads of the piezoelectric element. The other lead is tied to a shared ground. In the two wire approach, the servo-controller drives both leads of the piezoelectric element of the micro-actuator.
A problem arises when integrating micro-actuators into hard disk drives with multiple disk surfaces. Each of the micro-actuators requires its leads to be controlled by the servo-controller. These leads are coupled to wires, which must traverse the main flex circuit to get to the flexure. The flexure provides electrical coupling to the leads of the micro-actuator.
The main flex circuit constrains many components of the voice coil actuator. If the shape or area of the main flex circuit is enlarged, changes are required to many of the components of the actuator arm assembly and possibly the entire voice coil actuator. Changing many or most of the components of an actuator arm assembly, leads to increases in development expenses, retesting and recalibrating the production processes for reliability, and inherently increases the cost of production.
The existing shape and surface area of the main flex circuit has been extensively optimized for pre-existing requirements. There is no room in the main flex circuit to run separate control wires to each micro-actuator for multiple disk surfaces. This has limited the use of micro-actuators to hard disk drives with only one active disk surface.
What is needed is a way to minimize the time that the read-write heads fly close to the rotating disk surfaces they access. What is further needed, is a way to integrate micro-actuators into a hard disk drive with multiple disk surfaces, using the existing surface area and shape of the main flex circuit.

Method and apparatus for a micro-actuator providing three-dimensional positioning to a slider in a hard disk drive


{Technical Problems}

A lighting device that uses a light emitting diode (hereinafter referred to as LED) has a large number of LEDs. To the LEDs, a driving current is fed to cause them emit light to illuminate as a lighting device. When a forward supply voltage to each of the LEDs used in the device as the light source is increased gradually from a state of approximately zero volts, the LED begins to pass a current at the prescribed voltage of VLC (V) and light emission starts. Further increase in the supply voltage causes the current flowing through the LED to increase, and the light emission amount of the LED increases.
LEDs, unlike ordinary diodes, have a large forward voltage drop, which invite large power consumption. The power is consumed not only for light emission, but in addition a considerable portion of the power uselessly escapes as the heat loss causing rise in the temperature of LEDs.
If temperature of the LED rises due to heat generation of LED, there arises a danger of ignition of dusts, and in addition the life of the LED is adversely affected. Therefore, a heat dissipation arrangement of metallic material having an excellent thermal conductivity is provided. This arrangement dissipates heat that the LED generates and suppresses, thereby, the temperature rise of the LED. For example, Japanese Patent Application Laid-open No. TOKKAI 2012-69303 (Patent Literature 1) has disclosed a technique, wherein a metal pedestal 30 having heat dissipation effect is provided in a straight tube 10 and fire heat generated from an LED module 20 is dissipated thereby to suppress the temperature rise of the LED module 20.

Abstract: {Technical Problems}

Abstract: To provide a simple style of lighting device using LED

Abstract: {Means for Solving Problems}

Abstract: A lighting device using LED, comprising an LED group 250 configured with series-connected plural number of LED 252 and a driving circuit 550 for feeding the light-emission current to the LED group, wherein

Abstract: the driving circuits 550 has a parallel circuit comprised of a peak current setting capacitor 222 and a resistor 220 connected in parallel thereto, and a full-wave rectification circuit 230; wherein

Abstract: the LED group 250 is connected to the output terminal of the full-wave rectification circuit, and the capacitance of the peak current setting capacitor has a value within a region in which the peak value of the pulsating current behaves to increase its value in accordance with the increase of the capacitance of the peak current setting capacitor; wherein

Abstract: an interruption period that is determined in accordance with the number of the series-connections of the LED in the LED group is specified, and the pulsating current, of which peak value is determined in accordance with the capacitance of the peak current setting capacitor, is fed to the LED group.


The present invention is a mobile-energy generating system capable of providing redundant direct current power. It comprises a reciprocating engine and generator having dual fuel capability, a fuel cell, commercial electrical power hookups, and capacitors used for bridging purposes. Back-up fuel for the engine and fuel for the fuel cells are stored in propane and hydrogen storage tanks, respectively.

Traditionally, commercial power from a utility has been used as the primary source of electrical power for a consuming entity, e.g., a telecommunications facility. Many power systems include backup power sources to deliver power in the event the utility is unable to deliver power. Black-outs and other disturbances in the commercial power grid make this necessary. To provide back-up, many facilities use a diesel generator, which is then backed up by an array of batteries.
Conventionally, all of these systems—the commercial AC receiving equipment, the diesel generator, and the batteries—are all physically installed around or in the facility. The installation process drains engineering time because it typically involves customizing the equipment to meet the needs of the facility.
Operationally, if power from the commercial utility is lost, the diesel generator is activated to supply power to the facility. It takes time for the diesel generator to come online, though. Because of this, the battery array provides power during the time it takes to switch from the utility source to the diesel-generated source. If the generator also fails (e.g., runs out of fuel, suffers a mechanical failure), then the battery array is able to provide power for an additional, but limited, period of time.

Mobile-power system utilizing propane generator, fuel cell and super capacitors


An optical fiber modulator comprises an optical fiber, a substrate having a groove pattern in which the optical fiber is fixed, and a modulation unit including a polarizer, an electrooptic element, and an analyzer aligned in a light path of the optical fiber in this order, wherein the electrooptic element is made of a poled portion of the optical fiber, and when the electrooptic element is in an electric field-free condition, an absolute value, .delta., of a phase difference of a beam passed through the electrooptic element is within the following range EQU (m/2-1/6).pi..ltoreq..delta..ltoreq.(m/2+1/6).pi.. wherein m is an odd number. When the portion of the optical fiber is poled from two different directions, the modulation unit should further include a wave plate, and an absolute value, .delta.1, of a phase difference of a beam passed through the wave plate and the electrooptic element is within the following range of (n/2-1/6).pi..ltoreq..delta..ltoreq.(n/2+1/6).pi. wherein n is an odd number. Methods for making the modulators are also described.

1. Field of The Invention
This invention relates to an optical fiber modulator wherein an optical fiber has a poled portion serving as an electrooptic element and having a second-order nonlinear optical effect, and also to a method for making the fiber modulator. The optical fiber modulator of the invention may be applicable to not only as a sensor, but also as an optical switching device and an optical fiber modulator for communication systems.
2. Description of the Prior Art
Known electrooptic elements used in optical fiber sensors for measuring a voltage or in optical fiber modulators are made, for example, of optical crystals of LiNbO.sub.3 (hereinafter referred to simply as LN), Bi.sub.12 SiO.sub.20 (hereinafter abbreviated to BSO), Bi.sub.12 GeO.sub.20 (hereinafter abbreviated to BGO), and the like. According to "Optical Fiber Sensors" (published by Ohm Co., Ltd. and edited by Takayosi Ohkoshi (1986), pp. 149 to 153), optical fiber voltage sensors have high insulating properties, and have been developed especially for the measurement of high voltage.
In recent years, in order to reduce the number of optical elements used in optical fiber sensors, studies have been made on optical fiber sensors of the type wherein lenses and mirrors are omitted from the sensor, and instead, an magnetooptic element or an electrooptic element is assembled in the light path of an optical fiber. This type of sensor is described, for example, in Japanese Laid-open Patent Application Nos. 5-297086, 6-74979, and 8-219825. Quite recently, it has been found that when an optical fiber block is poled, a second-order nonlinear optical effect develops. Using the poled block, optical modulation devices have now been made as described, for example, by A. C. Liu et al in Opt. Lett. Vol. 19, pp. 466-468 (1994), by T. Fujiwara et al in IEEE Photonics Lett. Vol. 7, pp. 1177 to 1179 (1995), and in Japanese Laid-open Patent Application No. 9-230293.
However, with optical fiber sensors or modulators using LN, which is representative of second-order nonlinear optical material, it is necessary that an input beam be controlled so as to make an angle of axial deviation at around 0.1 to 0.2 or below as described in Japanese Laid-open Patent Application No. 3-44562 and "Optical Fiber Sensors" (published by Ohm Co., Ltd. and edited by Takayosi Ohkoshi (1986), page 153).
Problems involved in these sensors are described with reference to FIGS. 8a and 8b. FIG. 8a schematically shows a working principle of a typical optical fiber voltage (or electric field) sensor. In FIG. 8a, a randomly polarized input beam transmitted from an optical fiber is passed to a polarizer wherein a linearly polarized beam component alone is transmitted. The beam transmitted through a .lambda./4 plate is converted to a circularly polarized beam because the phase difference of the beam relative to the respective principal dielectric axes occurs by .pi./2. Further, when passed through an electrooptic element, the beam undergoes a phase difference corresponding to a voltage applied to the element, and is changed in various forms including from circularly polarized beam to linearly polarized beam. This is particularly shown in FIG. 8a as the state of polarized output beam. After transmission through an analyzer, the change in the polarized state is observed as a change in beam intensity. In FIG. 8a, P and t of shaded sketches, respectively, indicate a beam intensity and a time, and the sketches show that a beam with given powder is inputted, and a modulated beam is outputted at the positions depicted, respectively.
FIG. 8b is a graph showing the relation between the beam output strength and the phase difference or optical bias of a fiber sensor. The quantity of transmission of output light or beam is determined by the phase difference of the beam based on an electrooptic effect and an optical bias (determined by a .lambda.4 plate). The output beam intensity is expressed by SIN function. When the optical bias is given by .pi./2 or by a multiple of an odd number of .pi./2, a portion of the SIN function, which exhibits good linearity, can be used. On the other hand, when the optical bias is deviated from .pi./2, e.g. when the optical bias is at 3.pi./4, the output waveform is distorted. In addition, when the optical bias is considerably deviated (e.g. when the optical bias is at zero), not only the output waveform is considerably distorted, but also a degree of modulation becomes very low as is particularly shown in FIG. 8b. With LN, when a beam is passed from its crystal axis (z axis), any birefringence phenomenon does not appear. Only a phase difference of .pi./2 caused by the .lambda./4 plate appears, so that modulation signals, which are free of any distortion, can be obtained as designed. However, when an input beam is deviated from the z axis, a great phase difference appears owing to the great spontaneous or natural birefringence of LN, thereby causing the optical bias to be deviated from an original one. As a result, there arise the problems that the waveform distorts, and the degree of modulation suffers a great temperature change due to the great change of spontaneous birefringence depending on the temperature.
In order to solve these problems, it may occur to use crystals which are free of spontaneous birefringence. Known spontaneous birefringence-free, nonlinear optical materials or crystals include, for example, BGO, BSO, Bi.sub.4 Ge.sub.3 O.sub.12 and the like. However, both BGO and BSO, respectively, have the optical rotary power (i.e. the effect of the plane of polarization being rotated in proportion of the crystal length), so that the crystal length cannot be large, with the attendant problem that the degree of modulation of a beam cannot be optionally set and the degree of modulation cannot be sufficiently increased as described, for example, in the above-mentioned "Optical Fiber Sensors", edited by T. Ohkoshi, pp. 152 to 153. On the other hand, Bi.sub.4 Ge.sub.3 O.sub.12 undesirably involves a DC drift at high temperatures, thus presenting the problem that when used as an optical modulator, a stable temperature characteristic is not ensured. This is particularly reported, for example, by O. Kamada (Jp. J. Appl. Phys. Vol. 32 (1993), pp. 4288 to 4291).
In an optical fiber sensor of type wherein an ordinary electrooptic element is set in position in an optical fiber, any lens is not used. Accordingly, it is necessary to suppress an adverse influence caused by the divergence of a beam, disenabling one to take a sufficiently large crystal length. Accordingly, in case where LN, which has a relatively large electrooptic constant, is used as an electrooptic element, there arises the problem that sensitivity is not enough for use as an optical fiber sensor. Alternatively, if liquid crystals are used, problems are involved in that the response speed becomes very low, an abrupt change of voltage cannot be measured accurately, and such liquid crystals may be solidified when used at low temperatures.
Where part of an optical fiber is poled and used as an electrooptic element, there arises a problem as experienced in the case of a sensor wherein an LN crystal is used as an electrooptic element and an incident beam is deviated from an optical axis (z axis). More particularly, if an optical fiber is poled at part thereof for use as an electrooptic element, not only a nonlinear optical effect (electrooptic effect), but also the anisotropy of refractive index (spontaneous birefringence) develops. When such a poled fiber is used in an optical fiber sensor, it is difficult to obtain an intended fiber sensor. This difficulty does not occur in known optical modulators wherein a change in refractive index based on the electrooptic effect of one of principal dielectric axes is utilized, and in fact, has not been recognized at all up to now.
In an optical modulator proposed, for example, in Japanese Laid-open Patent Application No. 9-230293, the electrooptic effect alone is taken into account, and no mention is made of any optical device as to how to deal with spontaneous birefringence. Accordingly, the resultant modulator has poor linearity. In this instance, two holes are made in the clad portion of an optical fiber so as to insert electrodes thereinto. As a result, there is developed spontaneous birefringence which is ascribed to the anisotropy of the sectional structure of the optical fiber and which is much greater than the spontaneous birefringence developed according to the poling treatment. This optical fiber has such a function as a so-called "polarization-preserving fiber", and the polarized state of a beam inputted from portions other than principal dielectric axes (i.e. a line connecting a pair of holes and a direction normal to the line) becomes very unstable. If such an optical fiber is under varying temperature conditions or is applied with an external pressure thereon, the state of polarization of the beam changes considerably. When this optical fiber is used as an electrooptic element and a beam, which has the direction of poling different from the principal dielectric axes, is inputted to the fiber, the degree of modulation greatly changes by changing a temperature, for example, only by several degrees in centigrade. Thus, the electrooptic element has a very poor temperature characteristic and a large distortion rate.

Optical fiber modulator having an optical fiber having a poled portion serving as an electrooptic element and method for making same

Matsushita Electric Industrial Co., Ltd.


A method of diagnosing bladder pathology uses Vesico Internal Sphincter ElectroMyogram (VISEMG) waveforms obtained from a plurality of VISEMG electrodes disposed on a patient. The VISEMG waveforms are converted to noninvasive (NI) urodynamic graphs. Further, a programmed computer assesses the condition of the bladder based on the VISEMG waveforms. The method does not require traditional urodynamics or any other invasive procedure. An apparatus to perform the inventive method uses a plurality of VISEMG electrodes placed on the patient. Each electrode signal is amplified and filtered and converted to a digital signal. A computer converts the digital signals (the VISEMG waveforms) to NI urodynamic graphs. Any combination of the VISEMG waveforms, the NI urodynamic graphs, and the condition of the bladder based on the VISEMG waveforms can then be shown on a display screen.

The bladder collects and stores urine from the kidneys and allows for discharge of the urine. The two bladder functions are controlled by the sympathetic and the parasympathetic autonomic neurological systems, and these are coordinated by the brain via the spinal cord.
The first function is to store urine in a low pressure environment without leakage. The detrusor, or bladder muscle, maintains low pressure within the bladder cavity during the storage phase. A sympathetic input prevents an increase of intravesical pressure during the accumulation of urine, and it inhibits bladder contraction. It also activates the internal sphincteric muscle (bladder neck) thus providing continence of urine.
For evacuation of the urine (micturition), the parasympathetic system causes the contraction of the detrusor muscle and the relaxation of the internal sphincter (bladder neck), thus permitting an unobstructed flow of urine.
Patients exhibit urinary symptoms due to various neurogenic (functional) or non neurogenic (anatomic) causes such as bladder outlet obstruction, overactive bladder, poor urethral support due to abnormal relaxation of the pelvic floor musculature, or sphincteric incompetence.
Urodynamic testing is a set of standard diagnostic tests used to study various urinary disorders. The testing typically includes bladder and abdominal pressure measurements, uroflows, electromyographic (EMG) signals of the external sphincter and the pelvic floor muscles, and radiographic images of the internal structure of the bladder's cavity and urethra. (See: The Bladder, Fitzpatrick, Krane, Urodynamic Studies, chapter 6, Y. Berger, pages 119–128, Churchill Livingstone, 1995; Outcomes and Obstacles of urodynamics, Contemporary Urology, Y. Berger, pages 15–31, August 1995 both of which are incorporated by reference herein). Urodynamic testing, while supplemented by electrical measurements and radiology, is primarily a system of mechanical tests. Pressure measurements are obtained via catheters that are inserted into the bladder (for intra vesical and intraabdominal pressure recordings and urethral profile pressure) or rectum (for intra abdominal pressure recordings). Uroflows are graphical and numerical data that record the stream of urine (typically measured in milliliters (ml)/sec). The EMG electrophysiological recordings are obtained from the striated external sphincteric and pelvic floor muscles and are obtained with patches (electrodes) or needles. And finally, radiographic imaging of the internal structure and contour of the bladder and its outlet can be obtained via fluoroscopic or still images during the phases of bladder storage and micturition. These measurements have standardized values that are representative of normal or abnormal bladder function.
Urodynamics, however, does not record the electromyographic activity of the smooth muscles of either the bladder (detrusor) or the internal sphincteric muscle (bladder neck). These muscles are subjected to the input of the autonomic (sympathetic and parasympathetic) neurological system. Therefore, the current evaluation of bladder function as displayed by the traditional urodynamic measurements may reflect only the outcome of mechanical pressure changes (normal or abnormal) that are the results of electrophysiological (neurogenic or myogenic) activities (normal or abnormal) that are not being assessed. For example, in the case of overactive bladder (OAB), the urodynamics will reveal evidence of involuntary detrusor contractions (IDC's) measured as abrupt bladder pressure elevations, but not disclose the cause of the IDC's. In addition, the urodynamic tests are invasive in nature, and they cannot be performed in an ambulatory setting. Urodynamic testing must be done in a clinic (office or hospital), the tests cause patient discomfort, and the data produced is artificial from a non-natural environment. Nonetheless urodynamic tests present results, primarily in the form of urodynamic graphs, that doctors and urologists are accustomed to employing in diagnosing bladder pathology.
Accordingly there is a need for a noninvasive method of measuring bladder activity for diagnosing bladder pathology and advantageously presenting the measurements in the urodynamics format familiar to doctors and urologists.

Method and apparatus for measuring bladder electrical activity to diagnose bladder dysfunction


An electronic apparatus includes a display unit including a display panel and a display circuit board connected to the display panel. An input sensing unit includes a touch panel which includes an active area and a peripheral area adjacent to the active area and includes sensor patterns disposed in the active area, and a touch circuit board connected to the peripheral area of the touch panel. A polarizing film is disposed on the input sensing unit and is configured to polarize incident light. A step-difference compensation member is disposed between the polarizing film and the input sensing unit and includes a main portion overlapping the active area and a plurality of slit portions disposed between the main portion and the touch circuit board.

The present disclosure herein relates to an electronic apparatus, and more particularly, to an electronic apparatus with improved reliability.
Various electronic apparatuses including multimedia apparatuses such as a television, a portable phone, a navigation system, a computer monitor, and a game console have been developed. An electronic apparatus may include various components assembled with each other. An electronic apparatus may be designed in consideration of reliability in manufacturing processes and reliability in use.


A new and distinct variety of apple tree rootstock Malus domestica×Malus robusta hybrid ‘G.41’ is described herein. The new variety is a dwarfing rootstock that is resistant to fire blight (Erwinia amylovora) and crown rot (Phytophthora cactorum). The ‘G.41’ rootstock is useful in that it can be propagated clonally and used as a rootstock or root system for apple trees as well as for interstems of apple trees.

The invention described here is a new variety of apple tree rootstock, Malus domestica×Malus robusta hybrid, hereinafter referred to as 'G.41'. 'G.41' originated from a planned cross in 1975 in Geneva, N.Y. The new variety is a dwarfing rootstock that is resistant to fire blight and crown rot. It is precocious and highly productive, and can be used as a rootstock as well as for interstems of apple trees.
In the spring of 1975, pollen from a Malus robusta 'Robusta 5' apple tree was applied to emasculated flowers of a Malus domestica 'Malling 27' apple tree at the New York State Agricultural Experiment Station ("NYSAES"), Cornell University, Geneva, N.Y. In the fall of 1975, approximately 500 seeds resulting from this pollination were extracted from mature fruit derived from this cross. In the winter of 1975-76, the seeds were stratified and planted in large flats under conditions effective to germinate seeds and obtain seedlings. When germinated seedlings were about 2.5 cm tall they were inoculated with a mixture of isolates of the fungus Phytophthora cactorum (the causal agent of crown and root rots). The flats were flooded to mid-hypocotyl level and kept at 23° C. for one week. Surviving seedlings were transplanted into individual pots.
In the summer of 1976, each of the transplanted seedlings was inoculated with approximately 106 colony forming units of the Ea 273 strain of the fire blight bacterium Erwinia amylovora by inserting a 26-gauge hypodermic syringe needle into the shoot tip. The seedling designated at #041 was one of the survivors of this battery of inoculations from the same cross. All the surviving plants were transplanted to the Loomis field (NYSAES, Cornell University, Geneva, N.Y.) in the fall of 1976 and allowed to grow side shoots for propagation/evaluation. In 1978, 'G.41' was evaluated for rooting ability, lack of spine production, and low root brittleness in a layering bed (stool bed). In 1982, 4 finished trees with 'G.041' rootstock were planted in a first test orchard on the Loomis farm (NYSAES, Cornell University, Geneva, N.Y.) with Malus domestica cv. 'Northern Spy' grafted onto this rootstock as the scion cultivar. In 1983, two trees of the 'G.41' rootstock were also planted with Malus domestica cv. 'Golden Delicious' as the scion cultivar. This rootstock performed well (top 20% of many rootstocks tested) in these first test trials and more material was propagated by stool bed to be entered into new trials at the Research South Farm (NYSAES, Cornell University, Geneva, N.Y.). The 'G.41' rootstock performed well with all the scion cultivars that were tested. In summer 2002, 40 rootstock liners were inoculated with four different strains of fire blight (ten liners per strain) in the Plant Genetic Resources Unit greenhouse (NYSAES, Cornell University, Geneva, N.Y.) of the U.S. Department of Agriculture Agricultural Research Service. As a result, the apple rootstock 'G.41' was classified as resistant to the most virulent strains of fire blight.
Asexual reproduction of the 'G.41' apple rootstock has been achieved using the traditional method of clonally propagating apple rootstocks. In particular, the original seedling of the 'G.41' apple rootstock was planted in the Loomis field (NYSAES, Cornell University, Geneva, N.Y.) and allowed to develop into a "mother plant." The 'G.41' mother plant was then used to obtain rooted liners using conventional layering procedures. The resulting liners were then planted in a row to generate a layering stool bed (also referred to as the "mother stool bed"). The living tissues (i.e. leaves, stems, roots, buds, and spines) of the mother stool bed were observed to be identical to secondary and tertiary stool bed plants. In addition to conventional layering, the 'G.41' apple rootstock variety has been asexually reproduced by root cuttings, by budding and grafting onto seedling and clonal rootstocks, and by tissue culture. Observations of trees from these propagations indicate that all trees have proven true to type and identical in all appearances to the original tree.


In one embodiment, a method for discriminating between a machine generated multi-tone signal and a simulated voice multi-tone signal is provided. The method may comprise comparing output profiles generated from sampled outputs of a plurality of filters. The plurality of filters may have a single input sample stream applied to them and each filter may be preset at a measured multi-tone frequency associated with an identified prospective multi-tone signal. Based on the comparison of the output profiles, an inequality degree between the output profiles is generated and compared to an inequality threshold, thereby to determine whether the input sample stream comprises a machine generated multi-tone signal.

Various signaling techniques or protocols have been used over the years to convey information over a network, such as a telephone communication network. For example, dual-tone multi-frequency (DTMF) signaling was developed (and is still used in various telephone communications networks today) as a signaling or communication method in telephone central offices, various branch exchanges and various other applications where signaling occurs over a line in a voice-frequency band.
Phone calls may be generated with cellular or mobile telephones in mobile communication networks. These telephones may use voice compression to generate a digital signal from an analog voice signal, e.g., by using common encoding techniques such as Code Excited Linear Prediction (CELP). CELP coding encodes a voice signal as a time-variable filter excited by a pulse stream at the so-called "pitch frequency" of a speaker. A consequence of this is that a voice signal that has a constant pitch frequency and relative low modulation for a duration similar to a DTMF digit duration (e.g., 45 ms) may have a line spectrum instead of a fairly broadband signal, for example in circumstances where the voice signal is not modulated. Tone lines of the generated line spectrum may be of uniform frequency spacing and may further correspond to a pair of frequencies of a DTMF tone pair, resulting in this voice signal mimicking machine generated DTMF signals. These circumstances necessitate discrimination between machine generated DTMF signals and voice simulated DTMF signals produced by encoding techniques.


An orthopedic drill bit includes a cutting head formed to include diametrically opposed cutting lips leading to a central point and away to a radiused periphery to center said bit. The drill includes flutes extending from a cutting end, said flutes having a dulled periphery to prevent out of round holes. The flute design increases in width progressively from the tip up the shank, to maintain an adequate and unrestricted space for chips to easily move upward, preventing the chips from being compressed into a smaller opening while maintaining the tapered depth of the flutes for strength.

Drilling straight, round holes using a hand held power drill often results in a less than desired outcome. Current drillbit technologies often perform poorly, resulting in holes with negative issues such as, oblong, oversized and misaligned holes often with packed flutes in the drill bit and over-heated surrounding bone.
An even bigger problem of a poor cutting drill bit in the operating room is excessive plunging through the back side of the bone. Plunging or breakthrough does serious damage to vital soft tissues suck as veins, arteries, muscles, tendons ligaments and other bones. Any of these issues can result in extended healing time and even non-union of a fracture than can result in amputation. Current drillbits being used every day fail to address these vital issues.
This invention addresses all of these issues while helping to reduce the cost to the end user of the drill bit by making it in two pieces which is faster and less wasteful.


A pipe cutter having an over-center feature which facilitates automatic charging of a spring to which a cutter is mounted.

1. Field of the Invention
This invention relates to a hand tool for cutting pipe, particularly copper pipe such as that used in central-heating installations. As used herein, `cutting` includes providing a circumferential groove in the pipe.
2. Prior Art
Various forms of hand tools for cutting pipe are known, such pipe cutters generally having a rotatably mounted cutting wheel for engaging, in use, one side of the pipe, which is supported at its opposite side by a pair of spaced rollers.
In one form, the pipe cutter is adjustable to enable a range of different diameter pipes to be cut. This is accomplished by providing screw or other means for effecting relative adjustment movement between the cutting wheel and the rollers. Once a size of pipe is clamped tightly between the cutting wheel and the rollers, cutting is carried out by relative rotation between the tool and the pipe, normally by rotating the tool around a fixed pipe. PCT Specification No. WO90/05610 shows adjustable pipe cutters of this form, one of which has the cutting wheel axle fixed in one body part which is hinged to a second body part. The two body parts are urged together by a strong compression spring acting between them.
European Patent specification No. 0204802 B discloses a further form of pipe cutter designed for cutting a particular size of pipe. The device has a rotatable cutting wheel mounted on a shaft which is movable in one direction along an arcuate track when a pipe is inserted into a central hole of the device through an entry slot. After insertion the wheel snaps forward so that the pipe is held in engagement with a pair of spaced rollers at one of its sides, and with the cutting wheel at its opposite side. Thereafter relative rotation in one direction between the tool and the pipe causes the wheel to rotate and bite into the pipe as the cutting wheel shaft rotates and moves along the arcuate track in the opposite direction to its movement on pipe insertion. During such movement, the shaft presses against, and is pressed inwards by, strip springs which define part of the arcuate track. Continued relative rotation effects cutting of the pipe. Whilst this cutter is generally satisfactory in use, it is relatively expensive to produce.


Cache coherency rules for a multi-processor computing system that is capable of working with compressed cache lines' worth of information are described. A multi-processor computing system that is capable of working with compressed cache lines' worth of information is also described. The multi-processor computing system includes a plurality of hubs for communicating with various computing system components and for compressing/decompressing cache lines' worth of information. A processor that is capable of labeling cache lines' worth of information in accordance with the cache coherency rules is described. A processor that includes a hub as described above is also described.

FIG. 1 shows a portion of an architecture for a basic computing system that includes: 1) a processor 101; 2) a cache 102; 3) a memory controller 103; and, 4) a system memory 104. The processor 101 implements software routines by executing instructions that perform various operations on elements of data. The instructions and data elements are stored in the cache 102 and/or system memory 104. When the processor 101 needs a specific instruction or data element it looks to the cache 102 for the desired instruction or data element before requesting it from system memory 104.
Generally, cache 102 is deemed to be "faster" than the system memory 104. Better said, the processor 101 waits less time waiting for an instruction or data element that resides in the cache 102 than an instruction or data element that resides in the system memory 104. This disparity in waiting time as between the cache 102 and system memory 104 typically arises as a consequence of the cache 102 being implemented with inherently faster memory cells (e.g., SRAM cells) than those of which the system memory is implemented (e.g., DRAM cells).
Per bit of storage space an SRAM type cache 102 is more expensive than a DRAM type system memory 104. The computing system architecture of FIG. 1 therefore attempts to optimize both cost and performance by being designed to store more frequently used instructions and data elements in the cache 102 and less frequently used instructions and data elements in the system memory 104. By storing the more frequently used instructions and data elements in the cache, the processor should endure acceptable "timing penalty hits" in the form of wasted time waiting for instructions/data to be fetched from system memory 104 because a significant percentage of the instructions/data needed by the processor will be found in the cache 102.
In order to enhance the percentage of "cache hits" (i.e., the instances where a needed instruction or data element is found the cache 102), notions of "temporal locality" and "spatial locality" come into play. Temporal locality is the notion that a single instruction or data element is apt to be used soon after it has already been used. Spatial locality is the notion that instructions and data elements that are located near each other in memory (i.e., have similar addresses) tend to be used at about the same time. Temporal locality is accounted for by keeping instructions and data elements in cache 102 for at least some period of time after they are first transferred from system memory 104 into cache 102.
Spatial locality is accounted for by designing the cache 102 to be loaded with a block of data from system memory 102 (i.e., multiple instructions or data elements) whose content is proximate to (e.g., "surrounds") any single instruction or data element that needs to be fetched from system memory 104. For example, if an instruction at address X is needed from system memory 104, instead of transferring only the needed instruction from system memory 104, instead of transferring only the needed instruction from system memory 104 to cache 102, a block of content corresponding to a plurality of addresses that are related to address X is transferred from system memory 104 to cache 102.
FIG. 2 attempts to depict such a situation by showing that a first contiguous "block" of content 105 (which is referenced through multiple system memory addresses) is loaded into a single cache line 107; and, that a second contiguous "block" of content 106 (which is referenced through a different set of multiple system memory addresses) is loaded into another single cache line 108. For simplicity, FIG. 2 shows the cache 204 as a single structure. Various computing systems are designed with different levels of cache, however. For example, many types of computing systems have two levels of caches (a level one (L1) cache and a level two (L2) cache) where the first level cache (L1) corresponds to less processor waiting time than the second level cache (L2). The L1 cache is supposed to store the most frequently used data elements and instructions while the L2 cache is supposed to store data elements and instructions that are used less frequently than those in L1 cache but more frequently than those in system memory.
Traditionally, both cache levels are implemented with a faster memory type as compared to system memory (e.g., both L1 and L2 cache are implemented with SRAM memory cells); however, the L1 cache is integrated onto the same semiconductor die as the processor while the L2 cache is implemented with different semiconductor die than the processor. As "on chip" cache accesses are faster than "off chip" cache accesses, accesses to the L1 cache correspond to less waiting time for the processor than accesses to the L2 cache.
The memory controller 103 is responsible for taking requests from the processor 101 for data, that are not satisfied by the cache, and managing the process of servicing those requests in system memory 104. There may be many different kinds of requests, such as load requests for data that is not present in the cache, and evictions of data from the cache that need to be stored back into memory. Typically, the memory controller is able to pipeline requests, so that many requests may be outstanding, and can be serviced in parallel with a much shorter average latency. The memory controller is responsible for interfacing with the details of a particular memory technology, and isolates the system memory from the processor in a modular fashion. The memory controller may either be integrated with the processor, e.g. on the same die, or may be separated, e.g. in a chipset.
The system memory is typically implemented with a specific type of system memory (e.g., EDO RAM, SDRAM, DDR, etc.).

Multi-processor computing system that employs compressed cache lines' worth of information and processor capable of use in said system


The invention provides for a method of using a network analyzer and a test controller for measuring S-parameters of a device, which can assume a plurality of states, and which can switch very fast from one state to another. The test controller sends a trigger to the analyzer, which starts a frequency sweep when it receives this trigger. The frequency sweep, having substantially the same start and stop frequency, is provided to the device. The analyzer then executes a measurement of at least one S-parameter of the device, stores the S-parameter data from the measurement and provides the test controller with a trigger. The test controller then updates the device to the next state in a predetermined sequence of states when it receives the trigger from the analyzer. These steps are repeated until all states in the predetermined sequence of states have been measured. In addition, the invention provides for a system for measuring at least one S-parameter of a microwave device, which system comprises a test controller a network analyzer and the microwave device itself.

Linear networks, or nonlinear networks operating with signals sufficiently small to cause the networks to respond in a linear manner, can be completely characterized by parameters measured at the network terminals (ports) without regard to the contents of the networks. Once the parameters of a network have been determined, its behavior in any external environment can be predicted, again without regard to the contents of the network.
Although a network may have any number of ports, network parameters can be explained most easily by considering a network with only two ports, an input port and an output port, like the network shown in FIG. 1.
To characterize the performance of such a network, any of several parameter sets can be used, each of which has certain advantages. Each parameter set is related to a set of four variables associated with the two-port model. Two of these variables represent the excitation of the network (independent variables), and the remaining two represent the response of the network to the excitation (dependent variables). If the network in FIG. 1 is excited by voltage sources V1 and V2, the network currents I1 and I2 will be related by any of the following equations:
H-ParametersY-ParametersZ-ParametersV1 = h11I1 + h12V2I1 = y11V1 + y12V2V1 = z11I1 + z12I2I2 = h21I1 + h22V2I2 = y21V1 + y22V2V2 = z21I1 + z22I2
The only difference in the parameter sets is the choice of independent and dependent variables. The parameters are the constants used to relate these variables.
The above H-parameters can be used as an explanatory example to clarify how parameter sets of this type can be determined through measurement. The parameter h11 is determined by setting V2 equal to zero, e.g. by applying a short circuit to the output port of the network. The parameter h11 is then the ratio of V1 to I1, I.e. the input impedance of the resulting network. The parameter h12 is in turn determined by measuring the ratio of V1 to V2 (I.e. the reverse voltage gain) having the input port open circuited. It is important to note that both open and short circuits are essential for obtaining the above-mentioned H-parameters, Y-parameters and Z-parameters.
However, the use of said H-, Y- and Z-parameters in connection with higher frequencies, especially in the microwave domain, present a problem since a short circuit looks like an inductor and an open circuit has some leakage capacitance. Active devices such as transistors and tunnel diodes are often instable if short or open circuited. In addition it is difficult to achieve short and open circuits over a broad band of frequencies, which is typically required. Moreover, it is difficult to measure total current or total voltage, which is required when using H-, Y-, or Z-parameters.
It is obvious that another method has to be used for characterizing these devices at high frequencies, especially microwave frequencies.
If we embed the exemplifying two-port device in FIG. 1 into a transmission line, and terminate the transmission line in its characteristic impedance ZL, we can think of the stimulus signal provided by a generator having a impedance ZS that matches said characteristic impedance as a traveling wave incident on the device, and the response signal as a wave reflecting from the device or being transmitted through the device, see FIG. 2.
We can then establish this new set of equations relating these incident and "scattered" waves:E1r=S11E1i+S12E2i  [1]E2r=S21E1i+S22E2i  [2]Wherein E1r and E2r are the dependent voltages reflected from the 1st and 2nd ports respectively, whereas E1i and E2i are the independent voltages incident upon the 1st and 2nd ports respectively.
Dividing the new set of equations by Z0 (where Z0 is the characteristic impedance of the transmission line) we can alter these equations to a more recognizable form:b1=S11a1+S12a2  [3]b2=S21a1+S22a2  [4]Wherein
                                                                                b              n                        =                                          E                nr                                                              Z                  0                                                              ,                                                    and                                                                      [        5        ]                                                      a            n                    =                                    E              ni                                                      Z                0                                                    ;                            [        6        ]            and wherein:    S11 is the input reflection coefficient equal to b1/a1 with a2=0, i.e. no incident wave E2i, which is accomplished by terminating the output of the two-port in an impedance equal to Z0.    S22 is the output reflection coefficient equal to b2/a2 with a1=0, I.e. no incident wave E1i, which is accomplished by terminating the input of the two-port in an impedance equal to Z0.    S21 is the forward transmission (insertion) gain equal to b2/a1 with a2=0, I.e. no incident wave E2i, which is accomplished by terminating the output of the two-port in an impedance equal to Z0.    S12 is the reverse transmission (insertion) gain equal to b1/a2 with a1=0, i.e. no incident wave E1i, which is accomplished by terminating the input of the two-port in an impedance equal to Z0.
Where, for example:
|b1|2=Power reflected from the 1st port; and
|a1|2=Power incident on the 1st port.
The above scattering parameters or S-parameters are determined with resistive termination, which obviates the difficulties involved in obtaining the broadband open and short circuit conditions required for the H-, Y-, and Z-parameters. Moreover, parasitic oscillations in active devices are minimized when the device is terminated in resistive loads. There is also standard equipment available for determining S-parameters since only incident wave Eni and reflected voltages need to be measured.
S-parameters are conveniently measured by means of modern professional microwave network analyzers, e.g. the Agilent E8362B vector network analyzer from Agilent Technologies Inc. with Head Quarters in Palo Alto, Calif., USA. S-parameters are measured by a modern microwave network analyzer substantially in the same way as indicated above, I.e. by providing a well-defined incident wave E1i, E2i to the device under test and by measuring a possible reflected wave E1r, E2r caused by the incident wave E1i, E2i. The conventional way to do this is to provide an incident wave E1i, E2i with a frequency sweep that covers all the frequencies of interest for a certain state of a device under test, and then change the state of the device under test and provide a new frequency sweep.
However, the number of states that need to be measured tends to be very large when measuring a device that can assume several thousand of different states. An example of such a device is the transmit-and-receive modules (T/R-module) in radar equipments. Such T/R-modules can assume thousands of different states regarding phase and magnitude. Each such state affects the magnitude and/or phase of a signal that is transmitted or a signal that is received by the T/R-module.
The states in a T/R-module or a similar device under test can be changed very fast compared to changing the frequency in a network analyzer to accomplish a frequency sweep. Typically it takes milliseconds to change the frequency in a network analyzer and just 20-30 μs to change the state in the T/R-modules that are commonly measured today.
Moreover, it takes time to extract measured data from the microwave network analyzer to an external verification unit in setups comprising a verification unit. Every time communication is established there is also a certain amount of overhead. Depending on the type of instrument and the protocol used the total time for extracting data varies. In the Agilent E8362B the time is typically 30-100 milliseconds.
The time consumed during frequency change (10-20 ms for each frequency) and data retrieving with a microwave network analyzer (30-100 ms) is multiplied with the number of states that are to be measured. If a lot of states are to be measured this easily takes hours, e.g. when characterizing a T/R-module that may assume more than 600000 states. Such delays are clearly an inconvenience, particularly if a large number of T/R-modules or similar devices are to be characterized, which e.g. may be the case when developing and manufacturing such modules.
Consequently, there is a need for a method that gives a much faster measurement.


The present invention relates to computer implemented methods and system for creating and executing an query plan for SPARQL Protocol And Query Language (SPARQL) queries. The methods and systems are designed to accept as input a query in SPARQL syntax, convert this query to semQA2 and generate a parse tree, perform filter pushdown, generate an efficient query plan potentially using a cost function, and execute this query plan against data sources complying to or modeled as Resource Description Framework (RDF). The result of these methods and of the systems implementing these methods is a set of triples contained in the data sources that comprise a solution of the SPARQL query provided.

The SPARQL Protocol And Query Language for RDF (SPARQL) is a World Wide Web Consortium (W3C) Recommendation for querying Resource Description Framework (RDF) datasets. Currently, a new revision of the specification, SPARQL 1.1, is being developed. SPARQL 1.1 is designed to add functionality in the form of aggregation functions, subqueries, negation, and property paths, but is fully compatible with the previous version, so that any query that is valid under SPARQL 1.0 is also valid under 1.1. The following describes briefly the SPARQL query language; more information can be found in the Recommendation produced by the W3C.
Let I be the set of IRI references, B the set of blank nodes, and L the set of literals.                An RDF graph G is a set of triples tε(I∪B)×I×(I∪B∪L).        The set of RDF terms is RDF-T=(I∪B∪L).        A canonical model of an RDF graph G is a model equivalent to G with blank nodes replaced with some IRI not appearing elsewhere in G nor in the context in which it is used, i.e., in queries. Every subsequent mention of RDF graphs in this application assumes a canonical model.        An RDF dataset D is a set {Go, (u1, G1), . . . , (un, Gn)}, where each Gi is an RDF graph and each ui is an IRI; the graph Go is called the default graph, and each pair (ui, Gi) is a named graph. One of the graphs in the dataset, called the active graph, is used for basic graph pattern matching.        A triple pattern is a tuple tPε(RDF-T∪V)×(I∪V)×(RDF-T∪V), where V is a set of variables disjoint from RDF-T.        A basic graph pattern is a set of triple patterns.        A value constraint is a Boolean-valued expression using elements from (RDF-T∪V), logical functions, equality and inequality symbols, and unary predicates.        Let P1, P2 be graph patterns, and r a value constraint; the SPARQL standard defines the following expressions:                    a basic graph pattern {P1. P2}            a graph pattern with filter {P1 FILTER r},            a group graph pattern {P1} {P2},            an alternative graph pattern {P1} UNION {P2}, and            an optional graph pattern {P1} OPTIONAL {P2}.                        These SPARQL expressions can be defined in turn by SPARQL algebra operators as shown in the following table:
SPARQL syntactic expressionSPARQL algebra operatorP1.P2Join(P1,P2)P1 . FILTER rFilter(r,P1){PI}{P2}Join(P1,P2)P1 UNION P2Union(P1,P2)P1 OPTIONAL P2 . FILTER rLeftJoin(P1,P2,r)Diff(P1,P2,r)                SPARQL also defines a graph graph pattern, which does not lend itself to algebraic manipulation and which is therefore ignored in this document.        Note that the Join operator defines both the basic graph pattern and the group graph pattern, since functionally these two graph patterns are equivalent, and group graph patterns are essentially used to define scoping of variables and other operators. Note also that the Diff operator does not have a counterpart syntactic expression, since this operator is only used internally in the SPARQL algebra, as part of the definition of the LeftJoin operator.        It should also be observed that, in rigor, the SPARQL algebraic expressions operate over solution multisets rather than over graph patterns. We denote graph patterns and their solution multisets with the same symbols for simplicity, since in this context it is not necessary to make such distinction.
Given two graph patterns P1 and P2, we say that P2 implies P1, and denote it P1←P2, if for every RDF graph G, every solution for P2 is also a solution for P1. P1 and P2 are said to be equivalent, denoted P1P2, if they imply each other. The following equivalences can then be derived from the SPARQL algebra:Commutativity of Join: Join(P1,P2)Join(P2,P1)  (1)Commutativity of Or: Or(P1,P2)Or(P2,P1)  (2)Associativity of Join: Join(P1,Join(P2,P3))Join(Join(P1,P2),P3)  (3)Associativity of Or: Or(P1,Or(P2,P3))Or(Or(P1,P2),P3)  (4)Distributivity of Join over Join(P1,Or(P2,P3))Or:Or(Join(P1,P2),Join(P1,P3))  (5)
Based on their associativity properties, then, we denote the sequences of binary Join and Or, Join( . . . Join(P1, P2), . . . , Pn) and Or( . . . Or(P1, P2), . . . , Pn), using the multiple-operator shorthands Join(P1, P2, . . . , Pn) and Or(P1, P2, . . . , Pn) respectively.
Algebraic manipulation of SPARQL queries is hampered by the non-distributivity of the disjunction Union operator over the LeftJoin operator. To address this issue, the semQA query algebra extension for SPARQL [1] proposes the definition of an idempotent disjunction operator Or, where Or is distributive over LeftJoin:
Definition 1.
                Let P1 and P2 be two graph patterns. The idempotent-disjunction graph pattern Or(P1,P2) results in all solutions for P1 or for P2 such that there does not exist a solution that is a subset of another solution, and such that each solution exists only once in the solution set. In this way, a solution for Or(P1, P2) is a solution for Union (P1, P2) that is not a subset of any other solution for Or(P1, P2). This definition makes Or an idempotent disjunction.
With this Or operator, LeftJoin can be expressed in terms of Or and Join:LeftJoin conversion: LeftJoin(P1,P2,r)Or(P1,Filter(r,Join(P1,P2)))  (6)
This conversion of LeftJoin into a graph pattern consisting of Or and Join permits the elimination of any LeftJoin within the graph pattern, simplifying algebraic manipulation of queries. semQA then proposes mechanisms where any SPARQL graph pattern is converted to an i-d graph pattern by changing every Union operator for an Or operator, and replacing every LeftJoin operator by its equivalent Or-Join expression.
To drive optimization of queries, semQA also proposes filter pushdown methods against both Or and Join:Filter(r1&&r2,P1)Filter(r1,Filter(r2,P1))  (7)Filter(r1&&r2,P1)Join(Filter(r1,P1),Filter(r2,P1))  (8)Filter(r1∥r2,P1)Or(Filter(r1,P1),Filter(r2,P1))  (9)
The symbols && and ∥ denote respectively logical-and logical-or operations on value constraints. To derive additional algebraic equivalences that allow the pushdown of filters, semQA provides a set of definitions that allow the processing of different types of value constraints.
Definition 2.
                (a) An atomic value constraint is a value constraint that does not include logical- and or logical-or operators. (b) A conjunctive value constraint is a value constraint composed of one or more atomic value constraints linked by logical-and operators. (c) a value constraint in disjunctive normal form consists of one or more conjunctive value constraints linked by logical-or operators.Definition 3.        Let var(r) denote the set of variables in a value constraint r. Given a conjunctive value constraint r and a graph pattern P, a restriction of r on P, denoted R(r,P), is defined as follows:                    If r is atomic, R(r,P)=r if var(r)⊂var(P) and r is not of the form !bound(v), true otherwise.            If r=(r1 && r2 && . . . && rn), where every ri is a conjunctive value constraint,                            R(r,P)=false if for all ri, var(ri)⊂var(P) and ri is not of the form !bound(v); OT                Otherwise, R(r,P)=R(r1,P) && R(r2,P) && . . . && R(rn,P).Definition 4.                                                Given a conjunctive value constraint r and graph patterns P1 and P2, the overlap of r on P1 and P2, denoted L(r,P1,P2), is defined as follows:                    If r is atomic, L(r,P1,P2) is                            r if it is of the form !bound(v); or if var(r)⊂(var(P1)∪var(P2)), and var(r)⊂var(P1) and var(r)⊂var(P2).                false if var(r)⊂(var(P1)∪var(P2))                true if var(r)⊂var(P1) or var(r)⊂var(P2)                                    If r=(r1 && r2 && . . . && rn), where every ri is a conjunctive value constraint, L(r,P1,P2)=L(r1,P1,P2) && L(r2,P1,P2) && . . . && L(rn,P1,P2).
These definitions lead to the following equivalence, supposing that r is a conjunctive value constraint:Filter(r1,Join(P1,P2))Filter(L(r,P1,P2),Join(Filter(R(r,P1),P1),Filter(R(r,P2),P2)))  (10)
In addition, we have the following:Filter(r1,Or(P1,P2))→Join(Filter(r1,P1),Filter(r1,P2))  (11)
Note that the implication in (11) is unidirectional, since the reverse is not necessarily true. semQA also proposes mechanisms for the resolution of i-d graph patterns to create result sets conformant to the original SPARQL graph pattern. This is done by taking the results obtained from evaluation of an i-d graph pattern and constructing SPARQL results by processing them through the SPARQL query.
While this method is mathematically sound, it suffers from an important drawback. The expansion of LeftJoin into its Or-Join equivalent, and the subsequent conversion of the resulting semQA graph pattern into disjunctive normal form, increases exponentially the size of the query. This patent application concerns a set of mechanisms and an implementation designed to enable the algebraic processing of SPARQL queries into semQA2 graph patterns that do not need to eliminate the LeftJoin operator. For this, we make use of the algebraic principles already developed under semQA to improve query performance, we add capabilities for the algebraic manipulation and pushdown of filters with LeftJoin operators, and we define a mechanism to create an optimized SPARQL query plan using semQA2.


An apparatus for detecting a physical manipulation on a security module that stores security-relevant data includes a sensor device for generating sensor data that describe a physical influence on the security module, and a first and a second monitoring device, wherein the first monitoring device is set up to receive the sensor data from the sensor device and to take the sensor data as a basis for generating first monitoring data, and the second monitoring device is set up to receive the first monitoring data from the first monitoring device and to use the received first monitoring data to detect a manipulation of the security module. Two monitoring devices communicating with one another that in each case can discern a manipulation on the security module are used to ensure a high level of security for the security module.

It is often necessary to protect security modules storing security-relevant data against physical manipulations, for example against opening or drilling-open of a housing of the security module. Such protection can be provided using tamper protection. This is usually accomplished by using different tamper sensors that sense physical properties of the security module. The sensor data are analyzed by evaluation algorithms in order to detect a manipulation. To ensure a high level of protection for the security module, particularly precise sensors and complex evaluation algorithms are frequently used.
An aspect relates to providing an improved apparatus for detecting a physical manipulation on an electronic security module.

Apparatus and method for detecting a physical manipulation on an electronic security module


A passive magnetic bearing suspension system for rotatable or translatable applications. Such bearings systems contain subsystems acting in mutually perpendicular directions to produce an overall system that is statically and dynamically stable. Further, these bearings can be constructed entirely of ring, disk, and/or bar-shaped magnets that are axially magnetized. This reduces the manufacturing difficulties associated with previous systems that required conical magnets and/or radial magnetization.

Magnetic suspension systems are well known in the art. Such systems can be divided into two basic classes: active bearings and passive bearings. Active bearings use electromagnets that are controlled by a closed loop control or servo mechanism. Such systems require means to measure the position of the supported body and means of regulating the electric current in the electromagnets. They are, therefore, complex and costly systems.
Passive bearings in general use the attractive and repulsive forces of electromagnets or, preferably, permanently magnetized materials to generate support forces. No servo control or positioning measuring means are required. The passive bearings currently in use, however, are limited to one axis of stability, while the axes orthogonal to the stable axis are generally unstable. For example, in a rotatable configuration a passive bearing can be configured to be stable radially, but is then unstable axially. Conversely the bearing could be configured to be stable axially, but is then unstable radially. Linear bearings have similar stability limits.
One method of addressing this limitation is to use a mechanical bearing or an active magnetic bearing to stabilize and provide load support in the non-stable axis. This introduces the limitations of the mechanical or active magnetic bearing into the systems, respectively.
Another known method of addressing this problem is to construct bearings from conically shaped magnets. The unstable axis in this configuration is parallel to the surface of the cone, while the stable axis is perpendicular to the surface. Mechanical stability can be achieved for a limited range of cone angles. Unfortunately it is difficult and costly to manufacture conical magnets with the high magnetic energy required to produce useful bearing forces.
Yet another method of addressing the shortcoming is to rely on gyroscopic or eddy current forces to achieve dynamic stability. These types of systems are unstable in one or more axis when at rest, but become stable when the system rotational speed exceeds a certain critical value. These systems require mechanical bearings and/or active magnetic bearings to stabilize and provide load support below the critical rotational speed. This again introduces the limitations of the mechanical or active magnetic bearing into the systems.


A method and system for controlling a climate control system on a vehicle after entering a heat soak mode in which the outside air temperature associated with the vehicle is affected by absorption of non-ambient heat includes an ambient temperature sensor for sensing a current ambient temperature outside the vehicle. A controller coupled to the ambient temperature sensor compares the current ambient temperature to a stored ambient temperature representative of the outside air temperature prior to entering the heat soak mode. The controller controls the climate control system using the current ambient temperature if the current ambient temperature is less than the stored ambient temperature. If the current ambient temperature is greater than the stored ambient temperature, the controller determines a heat build up affecting the current ambient temperature and controls the climate control system using the current ambient temperature only upon elimination of the heat build up.

A climate control system on a vehicle, such as a motor vehicle, maintains a condition within an occupant compartment of the vehicle at a comfortable level by providing heating, cooling and ventilation. One example of a condition is air temperature, another is air distribution, while still another is air flow rate. Typically, the comfort level is subjectively determined by an occupant of the vehicle and communicated to the climate control system via a set point or other temperature control actuator, as is known in the art.
Climate control within the occupant is maintained by an integrated mechanism referred to in the art as a heating, ventilation and air conditioning (HVAC) system. In an automatic HVAC system, the comfort level within the occupant compartment of the vehicle is dependent on many objective and subjective factors, such as occupant preference, vehicle operating conditions, ambient temperature, humidity level, and sun heating load. The HVAC control system typically includes sensing mechanisms either within or outside the occupant compartment to maintain the desired comfort level. One example of a sensing mechanism is an ambient temperature sensor that measures the outside air temperature. The outside air temperature sensed by the ambient temperature sensor is one of several factors used by the HVAC system in maintaining the comfort level within the occupant compartment.
An ambient temperature sensor is typically located behind the vehicle front bumper. The sensor reading sometimes is increased by the engine heat, or the ground heat while the vehicle is idling, short time parking or moving at a very low vehicle speed. This causes an error in ambient temperature measurement. Typically a software routine is designed to filter out the errors in ambient temperature measurement by determining when to use the sensor reading as the control input and when to replace the sensor reading by using a previous sensor reading. The integrity of the ambient temperature sensor reading filter routine will affect the HVAC comfort level.
The key for a good ambient temperature reading is timing. The first decision needed is to determine when to stop using the sensor reading; this state is called the Heat Soak Mode. The Heat Soak Mode is typically entered when the vehicle speed is under a predetermined speed limit for a predetermined amount of time. While the system is in the Heat Soak Mode, the sensor reading is at error and will not be used. Instead the last ambient temperature sensor reading before entering the Heat Soak Mode will be used as the ambient temperature input until the system exits the Heat Soak Mode. Thus, the second decision needed is to determine when the ambient temperature sensor reading can be used again. The known prior art exits the Heat Soak Mode and uses the actual ambient temperature sensor reading when the vehicle speed is above a fixed limit for a predetermined amount of time, as disclosed in U.S. Pat. No. 5,416,728. However, the actual time period for when the ambient temperature sensor readings should be used is not fixed, but rather variable. Thus, using a variable timer will improve the accuracy of the measurement.
It is, therefore, an object of the present invention to provide, in a vehicle, a method and system for determining when to use a current ambient temperature with a climate control system after entering a heat soak mode.

Method and system for controlling a climate control system


A system and method for locating a wireless device in one or more wireless networks within a selected geographic region. The method includes generating a computer model of a selected geographic region including a layout and inputting information associated with one or more components of a wireless network into the computer model. The one or more components includes at least one or more sniffer devices. Additionally, the method includes determining signal intensity characteristics of the one or more components of the wireless network over at least a portion of the selected geographic region and receiving one or more wireless signals from one or more wireless devices. Moreover, the method includes determining a plurality of probabilities associated with a plurality of locations for at least one of the one or more wireless devices.

The present invention relates generally to wireless computer networking techniques. More particularly, the invention provides a method and a system for estimating physical location of wireless transmitters in wireless networks according to a specific embodiment. Merely by way of example, the invention has been applied to a computer networking environment based upon the IEEE 802.11 family of standards, commonly called "WiFi." But it would be recognized that the invention has a much broader range of applicability. For example, the invention can be applied to Ultra Wide Band ("UWB"), IEEE 802.16 commonly known as "WiMAX", cellular wireless networks such as CDMA, GSM, GPRS, and others.
Computer systems proliferated from academic and specialized science applications to day to day business, commerce, information distribution and home applications. Such systems include personal computers, which are often called "PCs" for short, to large mainframe and server class computers. Powerful mainframe and server class computers run specialized applications for banks, small and large companies, e-commerce vendors and governments. Smaller personal computers can be found in many if not all offices, homes, and even local coffee shops. These computers interconnect with each other through computer communication networks based on packet switching technology such as the Internet protocol or IP. The computer systems located within a specific local geographic area such as office, home or other indoor and outdoor premises interconnect using a Local Area Network, commonly called, LAN. Ethernet is by far the most popular networking technology for LANs. The LANs interconnect with each other using a Wide Area Network called "WAN" such as the famous Internet.
While conventional computer networks proliferated in the past, currently wireless communication technologies are increasing in popularity. That is, wireless communication technologies wirelessly connect users to the computer networks. Examples of wireless networks include, but not limited to, wireless local area networks (WLAN) and cellular networks. One desirable application of wireless networks is to provide wireless access to the LAN in the office, home, public hot-spots, and other geographical locations. As merely an example, the IEEE 802.11 family of standards, commonly called WiFi, is the common standard for such wireless application. Among WiFi, the 802.11b standard-based WiFi often operates at 2.4 GHz unlicensed radio frequency spectrum and offers wireless connectivity at speeds up to 11 Mbps. The 802.11 g compliant WiFi offers even faster connectivity at about 54 Mbps and operates at 2.4 GHz unlicensed radio frequency spectrum. The 802.11a provides speeds up to 54 Mbps operating in the 5 GHz unlicensed radio frequency spectrum. The WiFi enables a quick and effective way of providing wireless extension to the existing LAN.
In order to provide wireless extension of the LAN using WiFi, one or more WiFi access points (APs) connect to the LAN connection ports either directly or through intermediate equipment such as WiFi switch. A user now wirelessly connects to the LAN using a device equipped with WiFi radio, commonly called wireless station that communicates with the AP. The connection is free from cable and other physical encumbrances and allows the user to "Surf the Web", check e-mail or use enterprise and e-commerce computer applications in an easy and efficient manner. Since access points have limited signal coverage, multiple access points may be required to provide signal coverage throughout a facility. Another advantage of wireless networks is that wireless stations can move throughout the signal coverage area and continue to connect to the computer network. In a typical operational wireless network, multiple wireless stations operate from different locations within the geographic area comprising the wireless network. Station locations may also change from time to time as the users carrying those devices move.
Determining physical location of a wireless station, or that of a signal transmitting device, is useful for many applications, such as dispatching and location based applications. Physical location information regarding a wireless station is also useful if said station either deliberately or unknowingly is causing harm to the wireless network in the form of security breach, intrusion, denial of service attack (DOS), and the like. Knowing the physical location of the wireless station in these scenarios enables the network administrator to track down the station and take action (e.g. remove it from the vicinity of the network) to avoid security or performance catastrophe. However, location tracking capability is often not supported by standard WiFi communication systems and hence a solution is highly desirable.
Prior solutions have attempted to provide mechanisms to determine physical location of a wireless station, with varying degrees of success. One technique known in prior art is to analyze time delays encountered by the radio frequency signals received by (e.g., as in global positioning system or GPS) or transmitted from (e.g., as in time difference of arrival or TDOA used in cellular network) the station with respect to transmitters (e.g., satellites in GPS) or receivers (e.g., base stations in cellular network) located at known reference positions. However this approach has several limitations in local area wireless networking environment. For example, the GPS is often infeasible for indoor environments (e.g., office buildings, warehouses, apartments, commercial facilities, and like) as the signal from satellites may not reach indoors. Further, in these environments, the time delay encountered by the radio frequency signal between the transmitter and the receiver is usually too small to be accurately measured. Also these techniques require specialized hardware and/or software in the wireless station which is often not available.
Another conventional technique involves triangulating the position of the wireless station with respect to at least three reference locations, based on signal strength measurement. The receive signal strengths at different wireless access points from the transmitting wireless station are measured. The station is then estimated to be located at the center of the triangle formed by three access points for which a cost function of the receive signal strengths (e.g., sum of squares of received signal strengths at three access points) is maximized. However, this technique fails to account for signal attenuation and reflections resulting from spatial layout components such as walls, doors, partitions, obstacles and like, and hence the location estimate is often inaccurate.
Yet another conventional technique involves definition of areas, sometimes called "locales", within the geographic region of interest. The signal strength signature is then created for each area representing received signal strength at one or more network access points from the device transmitting from the area. During the operation, the area in which a transmitting wireless station resides is determined by comparing with the signal strength signature for areas, the observed signal strengths from the transmitting wireless station received at the network access points. The comparison is done via pattern matching. By way of limitation, this deterministic pattern matching approaches, fails to compute and represent the uncertainties in the location of the wireless station arising out of factors such as antenna orientation of wireless station, transmit power variations, imprecise knowledge of obstacles, movement of people and obstacles (e.g. opening/closing of doors) within the area of interest, and like. Not representing the reality of environment can be a serious limitation, especially in applications directed to security. Additionally, some of these techniques require prior definition of areas which can be a cumbersome procedure requiring manual effort and guesswork. The techniques may also require extensive on-site measurements to come up with the signal strength signatures. This is tedious process requiring manual effort and needs to be repeated for every change in the environment such as changing location of access points, changing area layout, and so on.
Accordingly, there is need for techniques for accurate and realistic estimation of transmitter location in wireless networks requiring less manual effort.

Method and system for location estimation in wireless networks


A magnetic property measuring system includes a stage configured to hold a sample and a magnetic structure disposed over the stage. The stage includes a body part, a magnetic part adjacent the body part, and a plurality of holes defined in the body part. The magnetic part of the stage and the magnetic structure are configured to apply a magnetic field, which is perpendicular to one surface of the sample, to the sample. The stage is configured to move horizontally in an x-direction and a y-direction which are parallel to the one surface of the sample.

Embodiments of the inventive concepts relate to a magnetic property measuring system, a method for measuring magnetic properties, and a method for manufacturing a magnetic memory device using the same. More particularly, embodiments of the inventive concepts relate to a system and a method for measuring magnetic properties of a magnetic tunnel junction by using a magneto-optical Kerr effect (MOKE), and a method for manufacturing a magnetic memory device using the same.
As high-speed and/or low power consumption electronic devices have been demanded, high-speed and/or low-voltage semiconductor memory devices used therein have also been demanded. Magnetic memory devices have been developed as semiconductor memory devices capable of satisfying these demands. The magnetic memory device may include a magnetic tunnel junction (MTJ) pattern. The magnetic tunnel junction pattern may include two magnetic layers and an insulating layer disposed between the two magnetic layers. A resistance value of the magnetic tunnel junction pattern may be changed depending on magnetization directions of the two magnetic layers. For example, when the magnetization directions of the two magnetic layers are anti-parallel or not parallel to each other, the magnetic tunnel junction pattern may have a relatively high resistance value. When the magnetization directions of the two magnetic layers are parallel to each other, the magnetic tunnel junction pattern may have a relatively low resistance value. The magnetic memory device may read/write data using a difference between the resistance values of the magnetic tunnel junction pattern.
When the magnetization directions of the two magnetic layers are substantially perpendicular to an interface between the insulating layer and the magnetic layer, the magnetic tunnel junction pattern may be defined as a perpendicular magnetic tunnel junction pattern. A measuring system using a polar magneto-optical Kerr effect (polar MOKE) may be used to measure perpendicular magnetic properties of the perpendicular magnetic tunnel junction pattern.

This patent is subject to a terminal disclaimer.

Magnetic property measuring system, a method for measuring magnetic properties, and a method for manufacturing a magnetic memory device using the same


An induction heating assembly for a vapour generating device includes an induction coil, radially inward of which a heating compartment is defined for receiving, in use, a body including a vaporisable substance and an induction heatable susceptor; and a temperature sensor located against a side of the heating compartment on the central longitudinal axis of the induction coil at an end of the heating compartment, wherein the induction coil is arranged to heat, in use, the susceptor, and the temperature sensor is arrange to monitor, in use, a temperature related to heat generated from the susceptor. There is also provided an induction heatable cartridge for use with the induction heating assembly. The cartridge includes a solid vaporisable substance; and an induction heatable susceptor held by the vaporisable substance, the susceptor being planar and having an outwardly facing edge and an inwardly facing edge.

The present invention relates to an induction heating assembly for a vapour generating device.
Devices which heat, rather than burn, a substance to produce a vapour for inhalation have become popular with consumers in recent years.
Such devices can use one of a number of different approaches to provide heat to the substance. One such approach is that of simple provision of a heating element to which electrical power is provided to heat the element, the element in turn heating the substance to generate vapour.
One way to achieve such vapour generation is to provide a vapour generating device which employs an inductive heating approach. In such a device an induction coil (hereinafter also referred to as an inductor and induction heating device) is provided with the device and a susceptor is provided with the vapour generation substance. Electrical energy is provided to the inductor when a user activates the device which in turn creates an electromagnetic (EM) field. The susceptor couples with the field and generates heat which is transferred to the substance and vapour is created as the substance is heated.
Using induction heating to generate vapour has the potential to provide controlled heating and therefore controlled vapour generation. However, in practice such an approach can result in unsuitable temperatures unknowingly being produced in the vapour generation substance. This can waste power making it expensive to operate and risks damaging components or making ineffective use of the vapour generation substance inconveniencing users who expect a simple and reliable device.
This has been previously addressed by monitoring temperatures in a device. However, these temperatures have been found to be unreliable and not representative of the temperatures actually produced further reducing the reliability of such a device.
The present invention seeks to overcome at least some of the above problems.

Induction heating assembly for a vapour generating device


A game apparatus includes, for example, a CPU, and a ROM and/or a RAM for executing and storing game programs and game program backup data. The RAM has multiple pre-allocated backup game data storage areas for use by different game programs during their respective execution including a single-player game backup data area, a multi-player game backup data area and a shared backup data storage area. The shared backup data storage area is provided for storing information that is accessible in common by a plurality of games, and separate game backup data storage areas are provided for each of the single-player version of a game and the multi-player version of a game. If a predetermined game condition is accomplished during progress of a game by an operator playing one of the plurality of stored game programs, the CPU writes information relating to the accomplished condition to the shared backup data storage area and to the backup data storage areas for both the single-player game version and the multi-player game version corresponding to the particular game in progress in which the condition was accomplished.

1. Field of the Invention
The present invention relates to a game apparatus and a backup writing control method. More specifically, the present invention relates to a game apparatus and a backup writing control method which are capable of playing a plurality of games and sharing backup data of the plurality of games with each other and applies changes to the backup data of the plurality of games according to progress of any one of the games.
2. Description of the Prior Art
One example of such a kind of conventional game apparatus is disclosed in a Japanese Patent Laying-open No. 2001-204966 (International Classification: A63F13/10) laid-open on Jul. 31, 2001. The prior art is a game apparatus capable of playing a plurality of games related with each other. When any one of a plurality of game programs is selected and instructed to be started, another related game is searched, and a part of the game program is changed depending upon a state of the backup data of a found game.
The prior art changes, when starting the game, a content (program) thereof according to a state of the backup data of another related game so as to generate different scenario, but never brings about changes to the backup data of another related game either, for example.
Furthermore, in the prior art, backup areas are respectively provided with respect to the plurality of game programs, and data useable in common such as brightness of a screen, utilized language and etc. is set for each of the game programs and stored in each of the backup areas in a duplicated manner. Accordingly, it is necessary to prepare more capacity of the backup area than necessity, and it is troublesome to set such the common data for each of the games.

Game apparatus and backup writing control method


An optical detector having a detection surface and a mirror sized and positioned relative to the surface so as to receive and return light which is reflected off of the detecting surface within the response time of the system.

Almost all systems which utilize light beams for communications, measurement, experiment or otherwise, include devices for detecting the light. Such devices are generally referred to as optical detectors which, in most communications or measurement applications, comprise semiconductor photodiodes.
A semiconductor photodiode comprises a semiconductor surface which, when exposed to light, causes an electrical current to flow on the surface. The output of a semiconductor photodiode type optical detector is typically coupled to processing electronics which amplify and condition the produced electrical signal. For example, circuitry may be provided 1) to sharpen the edges of light pulses by detecting when the signal strength passes a threshold level and cutting off the signal at that point or 2) to check and modify the timing of a series of pulses.
How well an optical detector performs its function of detecting light and producing electric current therefrom is sometimes termed quantum efficiency and depends on 1) its sensitivity to light striking its detection surface, 2) the intensity of the light which strikes the detection surface and 3) the reflectivity of the detector surface.
Sensitivity of a semiconductor photodiode depends on the operating conditions, the detector design, and how the particular semiconductor material used responds to light of different wavelengths. For instance, silicon photodiodes are particularly sensitive to light of 0.8 to 0.9 micrometer wavelength but are not usable for detecting light of 1.3 micrometers in wavelength. Other semiconductor photodiode materials such as germanium or indium gallium arsenide (InGaAs) are more sensitive to longer wavelengths.
Normally, significant light energy is wasted at the optical detector because a percentage of the light which strikes the photodiode is reflected off of the semiconductor surface instead of absorbed. It is not unusual for 20% or more of the light which strikes the surface of a semiconductor photodiode type optical detector to be reflected and wasted. The less light which is reflected and wasted, the higher the quantum efficiency of the photodiode.
U.S. Pat. No. 3,815,977 issued to Vasiliev discloses a photo detector incorporating a prism above the detecting surface for returning light which was reflected off of the detector surface back to the detector surface. Vasiliev teaches two different embodiments. In the first embodiment, incident light reflected off of the photo-detector surface strikes a face of the prism and is returned to a different point on the detector surface. Reflection off of the detector surface from that second point is again reflected off of a different face of the prism and returned to a third point and so on for subsequent reflections. In the second embodiment taught by Vasiliev et al., light is returned to the original point of incidence on subsequent reflections, however, the light is reflected off of two separate surfaces of the prism before being returned to the point of incidence. As in the first embodiment, light is returned to the detector surface a plurality of times, but with each return requiring reflections off of two separate surfaces of the prism rather than one. The photo-detector of Vasiliev recovers only light reflected along the primary axis of reflection. Light which is scattered (i.e., not reflected along the primary axis of reflection) is not recovered in the photo-detector of Vasiliev et al.
Accordingly, it is an object of the present invention to provide an improved optical detector arrangement.
It is a further object of the present invention to provide an optical detector with a significantly decreased reflection loss.

Mirror apparatus for increasing light absorption efficiency of an optical detector