A system and method for treating wastewater by continuously flowing wastewater into a chemostat and continuously discharging clean water out of the chemostat. The system can include sensors and an electronic controller for on-line measuring ambient parameters in the chemostat and adjusting the chemostat's operating conditions accordingly.

Industrial wastewater is produced as a by-product of industrial processes, for example, processes in oil refineries and petrochemical plants.
Wastewater from refineries may be highly contaminated given the number of sources it can come into contact with during the refinery process. This contaminated water may, for example, be process wastewater from desalting, water from cooling towers, storm water, distillation, or cracking. This water can be recycled through many stages during the refining process and typically goes through several treatment processes, including wastewater treatment, before being released into surface water.
Existing technologies for the treatment of contaminated water in oil refineries and petrochemical plants consist of a series of sequential steps, including the steps shown in the flow diagram of FIG. 1.
To-date, the majority of the wastewater treatment is done by using the "activated sludge" (depicted in the flow diagram of FIG. 2) or "membrane bioreactors" ("MBR") (depicted in the flow diagram of FIG. 3) technologies. In general, in activated sludge plants, atmospheric air or pure oxygen is bubbled through wastewater combined with organisms, to develop a biological floc which reduces the organic content of the wastewater. In all activated sludge plants, once the industrial wastewater has received sufficient treatment, an additional step of settling out the biological floc is required. Part of the settled material, the sludge, is returned to the system to re-seed the new industrial wastewater entering the tank. The remaining sludge then needs to be disposed of. The MBR technology combines the use of an activated sludge bioreactor with a cross flow membrane filtration loop. The membrane is used for the additional step of biological floc removal, by filtration, and as a result recycled and waste sludge are produced.
U.S. Pat. No. 6,916,427 to Roth discloses a method of purifying wastewater, including running the wastewater as a fluent into a headworks where some preliminary treatment takes place, passing the fluent into a primary reservoir where it is analyzed as to certain control parameters such as pH, dissolved oxygen and/or dissolved solids. Thereafter the fluent flows into a primary reactor having a plurality of electrolytic cells therein. While in that reactor the fluent is subjected to electrical contacts which are located at the bottom and the top of the reactor. The effluent from the primary reactor passes through a ratio weir into a secondary receptor containing sensors for the measurement of control parameters such as pH, DO, TDS and chlorine. Thereafter, the fluent is passed to a filtering device.
U.S. Pat. No. 5,989,428 to Goronszy provides a method and apparatus for treating waste material to remove selected components form the waste is described using a reactor or a series of reactors in fluid communication with each other for receiving the waste to be treated as influent. The influent forms a biomass including the waste and microorganisms and is treated by controlling the metabolic activity of the microorganisms by monitoring the oxygen utilization rate or the potential oxygen utilization rate of the biomass so as to determine the required amount of oxygen to be supplied to the biomass and to determine the period of aeration of the biomass in order to maintain a predetermined oxygen utilization rate or value so as to remove the selected components of the waste. The preferred selected components to be removed are nitrogenous, carbonaceous and/or biological phosphorus containing materials or derivatives.
US Published Patent Application No. 20080047903 to Morse discloses a system and process for optimizing chemical additions, mixing energy, mixing time, and other variables while treating a contaminated liquid stream. Samples from the contaminated liquid stream are tested to determine the optimal parameter for each variable, including type and amount of the chemicals to be added, chemical sequence, mixing energy, mixing time, temperature, and pressurization. A system of mixers, a flotation chamber, and a dewatering subsystem are designed to achieve optimal turbidity of the wastewater stream. The system can be modified in real-time in response to a continually changing contaminated liquid stream via a controller and set of sensors, valves, and ports. The process takes place during the pre-treatment stage. There is need for a stable, efficient, continuous and cost-effective wastewater treatment process to overcome the shortcomings of existing processes.


A golf ball (20) having a non-planar parting line (25), a first false non-planar parting line (26a) and a second false non-planar parting line (26b). A first group 32 of parting dimples defines the non-planar parting line (25). A second group (33) of parting dimples defines the first false non-planar parting line (26a). A third group (34) of parting dimples defines the second false non-planar parting line (26b). A plurality of hexispheres (70) are defined by the non-planar parting line (25) the first false non-planar parting line (26a) and the second false non-planar parting line (26b).

1. Field of the Invention
The present invention relates to a dimple pattern for a golf ball. More specifically, the present invention relates to a dimple pattern for a golf ball that has false parting lines.
2. Description of the Related Art
Golf ball designers have been improving the symmetry of a golf ball for many years. Over the years, many golf ball surface patterns have been proposed to improve symmetry.
Yamada, U.S. Pat. No. 4,744,564, discloses a golf ball with smaller volume dimples near the poles than those close to the parting line.
Ihara, U.S. Pat. No. 4,915,389, discloses a golf ball with no parting line and dimples positioned on all great circles.
Yamada, U.S. Pat. No. 4,946,167 discloses a golf ball which improves symmetry by arranging dimples within a spherical triangles so as to be in a point or a line symmetrical relationship without intersecting the ridge lines of a complete geodesic 24-hedron.
Oka et al., U.S. Pat. No. 5,072,945, discloses a golf ball with a great circle zone along a parting line and dimple sin a P region and a S region being geometrically symmetric about the parting line.
Oka, U.S. Pat. No. 5,078,402, discloses a golf ball with dimples arranged to create four great circle zones.
Oka et al., U.S. Pat. No. 5,090,745, discloses a golf ball having a parting line and dimples formed thereon.
Oka, U.S. Pat. No. 5,123,652, discloses a golf ball with dimples arranged to create great circle zones with unintersecting dimples.
Oka, U.S. Pat. No. 5,145,180, discloses a golf ball with dimples arranged to create one great circle zone with unintersecting dimples, and 300 to 550 dimples formed on the golf ball.
Oka et al., U.S. Pat. No. 5,156,404, discloses a golf ball having a one great circle and four half great circles without intersecting dimples.
Yamaguchi, et al., U.S. Pat. No. 5,824,258, discloses a golf ball injection mold with gates along the parting line.
Shimosaka, et al., U.S. Pat. No. 5,827,135, discloses a golf ball dimple pattern with dimples intersecting all potential great circles.
Inoue et al., U.S. Pat. No. 5,840,351, discloses a mold with an offset center split which allows for dimples to be formed on a great circle of a golf ball.
Stiefel, et al., U.S. Pat. No. 5,890,974, discloses a tetrahedral dimple pattern with six dimple-free great circles.
Shimosaka, et al., U.S. Pat. No. 5,902,193, discloses a golf ball dimple pattern with dimples on the parting line.
Kasashima, et al., U.S. Pat. No. 5,906,551, discloses a golf ball dimple pattern with large volume dimples on the parting line.
Shimosaka, et al., U.S. Pat. No. 5,908,359, discloses a golf ball dimple pattern without dimples on the parting line, and which is designed to have equal ball hitting effects from the seam and the pole.
Kasashima, et al., U.S. Pat. No. 6,053,820, discloses a golf ball dimple pattern with two to five different dimples in a uniform arrangement.
Shimosaka, et al., U.S. Pat. No. 6,179,731, discloses a golf ball dimple pattern with dimples on the parting line and a raised portion.
Kasashima, et al., U.S. Pat. No. 6,200,232, discloses a golf ball dimple pattern with dimples intersecting all great circles, and the dimples arranged in a polyhedral arrangement.
Kasashima, et al., U.S. Pat. No. 6,241,627, discloses a golf ball dimple pattern with the dimples arranged in a regular icosahedron arrangement.
Shimosaka, et al., U.S. Pat. No. 6,346,054, discloses a golf ball dimple pattern with dimples equally distributed in spherical triangle arrangements.
Winfield, et al., U.S. Pat. No. 6,527,653, discloses a pentagonal hexecontahedron dimple pattern.
Winfield, et al., U.S. Pat. No. 6,533,684, discloses a phyllotaxis-based dimple pattern.
Ogg, U.S. Pat. No. 6,551,203, discloses a dimple pattern with 384 dimples covering 86% of the surface area of the golf ball.
There is still a need for a golf ball with improved symmetry.


Novel concepts are proposed for line terminations of coplanar lines that are as anechoic as possible, having a neutral wire and two outer conductors that are situated at least from section to section on both sides of the neutral wire, the line termination including at least one resistor element, via which the neutral wire is connected at its end with the two outer conductors. A connection at the end between the two outer conductors exists independently of the at least one resistor element. Alternatively or in supplementation to this, at least one resistor element of the line termination is situated at a slanting angle to the neutral wire, i.e. at an angle which is either greater or less than 90°.

The technology of coplanar lines (CPWS, coplanar waveguides) is used for high-frequency circuits, particularly in the millimeter wave range, since coplanar lines demonstrate superb high-frequency properties, especially in connection with microelectromechanical switches for high-frequency signals.
The construction of a coplanar line, as it is known from the related art, is shown in FIGS. 1a and 1b, FIG. 1a showing a section through a structural element having a coplanar line and FIG. 1b showing a top view onto the surface of the structural element. The structural element is constructed from a substrate 1, which may be made up of a plurality of layers. On uppermost substrate layer 2 there are situated a neutral wire 3 of width w and thickness tW and two outer conductors 4 and 5 having widths ba and bb and thicknesses ta and tb. The two outer conductors 4 and 5 here run parallel to neutral wire 3. The gaps between neutral wire 3 and outer conductors 4 and 5 have the same width ga and gb, which does not have to be that way for every coplanar line. Neutral wire 3 is used as a signal conductor. The line geometry for a certain impedance at a certain frequency is a function of the material parameters and thicknesses of the substrate layers and the conducting layer in which neutral wire 3 and outer conductors 4 and 5 are implemented. This structure may be covered by one or a plurality of overlayers.
A line termination for a coplanar line which is implemented, for example, on calibration substrates for network analyzers, is shown in FIG. 2. In this application, the line dimensions are relatively small. 50 μm neutral wires are typical. The line termination includes, in this case, two resistor elements 6 which are positioned orthogonally to the direction of the coplanar line, i.e. orthogonally to neutral wire 3 and to outer conductors 4 and 5. The resistor elements are trimmed to a direct current resistance of exactly 50 Ohm (+/−0.3%). Thereby, in the range of 50 . . . 110 GHz, matching of ca 30 . . . −25 dB is achieved. Under ca 26 GHz the matching is better than −35 dB.

Structural element having a coplanar line


Received data is applied in units of blocks to an error correcting unit and a data holding unit. If the error correcting unit normally performs error correction, the output from the error correcting unit is stored in a frame buffer. If the error correcting unit does not normally perform error correction, the data in the data holding unit is stored in the frame buffer. In this manner the first error correction processing is performed. Bit data is sequentially read out in units of bits from each block stored in the frame buffer, subjected to the second error correction processing, and returned to the frame buffer. The third error correction processing is further performed for the data sequentially output in units of blocks from the frame buffer.

1. Field of the Invention
The present invention relates to a method of correcting data errors of a received digital signal in text broadcasting such as FM multiplex broadcasting and an apparatus for use in the method and, more particularly, to an error correcting method which receives one frame of a digital signal used in, e.g., the DARC (Data Radio Channel) standard, together with a parity code and performs error corrections in both the horizontal and vertical directions
2. Description of the Prior Art
Text information service has been put into practical use in FM multiplex broadcasting in which a digital signal is transmitted by using an idle spectrum region of an FM stereo signal. However, in text information using a broadcast radio wave, many pieces of error information are sometimes contained in the received digital information. Errors of this received digital information are particularly significant upon reception in mobile communication inferior in transmission quality. Therefore, it is necessary to correct errors of the received digital information on the receiving side.
Various systems have been proposed for error correction of this received digital information and the following three systems have been put into practical use as the international standard or the Japanese standard: a DRAC system and a fixed reception system primarily studied in Japan and RDS (Radio Data System) developed in Europe. These three systems are different from each other; i.e., the DARC system uses the product codes of (272,190) codes, the fixed reception system uses (272,190) codes, and the RDS uses (26,16) codes. The DARC system is considered to have a higher error correction accuracy than the other systems. The basic operation of the DARC system, i.e., error correction using the product codes of (272,190) codes will be described below.
In the DARC system, one frame of information is divided into 272 blocks and sequentially transmitted. Each block consists of 272 bits. Each of the first 190 blocks consists of a 16-bit block identification code, 176-bit data, a 14-bit CRC code, and an 82-bit first parity code. Each of the last 82 blocks consists of a 16-bit block identification code, a 190-bit second parity code, and an 82-bit third parity code. The first parity code corresponds to 190 bits of the data and the CRC code of that block, the second parity code corresponds to the data bits and the CRC codes from the first to 190th blocks, and the third parity code corresponds to the first parity codes from the first to 190th blocks.
On the receiving side, as shown in FIG. 1, a data input unit 41 sequentially supplies a signal in units of blocks of 272 bits to an error correcting unit 43. After error correction is performed by using the first and third parity codes, the signal is stored in a frame buffer 44. When the error correcting unit 43 performs error correction, an error signal 42 is output When the frame buffer 44 stores 272 blocks, the first error correction processing is complete. FIG. 2 shows the flow of this first error correction processing. Also, FIG. 3 shows an example of the result of the first error correction processing Each full circle 45 represents a bit still remaining as an error as a result of the first error correction. FIG. 3 shows that a considerable number of errors still remain.
Subsequently, vertical error correction is performed for the signal with the bit array as in FIG. 3 stored in the frame buffer 44. Corresponding bits in the 272 blocks are supplied to the error correcting unit 43, FIG. 1, where vertical error correction is performed by using the second parity code described above. The result is returned to the frame buffer 44. When this processing is sequentially repeatedly performed for the 272 bits (at least 190 bits of data bits and a CRC code), vertical error correction as the second error correction processing is complete. FIG. 4 shows the flow of this second error correction processing, and FIG. 5 shows an example of the result of the second error correction processing. Each open circle 46 represents a bit corrected by the second vertical error correction. Each full circle 47 represents a bit which still remains as an error even after the first and second error corrections. FIG. 5 indicates that as a result of the horizontal and vertical error corrections, a considerable number of error bits are corrected but a few errors still remain.
Accordingly, horizontal error correction is again performed for the signal with the bit array as in FIG. 5 stored in the frame buffer 44. 272 bits of each block are sequentially supplied to the error correcting unit 43, FIG. 1, horizontal error correction is again performed by using the first and third parity codes, and the result is returned to the frame buffer 44. When this processing is sequentially repeatedly performed for the 272 blocks, horizontal error correction again performed as the third error correction processing is complete. FIG. 6 shows the flow of this third error correction processing, and FIG. 7 shows an example of the result of the third error correction processing. Each open circle 49 represents the position of a bit whose error is finally corrected. As a result, all errors are corrected with a very high accuracy.
If, however, the received signal is inferior in quality and contains a large number of errors, error bits which are left uncorrected exist as indicated by full circles 48. If these error bits 48 remain, this frame is discarded and a frame received next is similarly error corrected and output to the screen. Alternatively, as proposed in Japanese Unexamined Patent Publication No. Hei 5-145500, a block in which error bits remain is rewritten with data of a corresponding block received thereafter and is output to the screen. Still another measure is to again receive frame information after 5 seconds or more elapse, perform horizontal error correction for blocks corresponding to blocks (BLK9, BLK11, and BLK264 in FIG. 7) containing error bits, and, if the errors are corrected, output these error-corrected blocks to the screen in place of the preceding blocks (BLK9, BLK11, BLK264 in FIG. 7) in which error bits remain.
As a result of a simulation of this system, the error correction probability when decoding is done by a variable threshold value is about 90% for errors of 11 bits and 30% for errors of 13 bits. When the signal has an 82-bit parity code for 176-bit data, errors up to 11 bits can be corrected with a high accuracy, but the error correction probability for errors more than that is extremely low. The reason for this is as follows. For a predetermined parity code, errors having the number of bits larger than a predetermined number, e.g., 11, cannot be normally corrected, i.e., they are abnormally corrected. This makes the subsequent correction processing using parity check unreliable, so even normal bit data is also rewritten. If normal bit data is thus rewritten, normal data cannot be restored in the subsequent second and third error corrections.
As described above, when a block which cannot be corrected by three error corrections in the horizontal, vertical, and horizontal directions is replaced with a subsequent signal, the processing time is undesirably prolonged. If final error data exists in a final block, the processing time becomes almost twice the processing time when error correction processing is completed by three error corrections.
In the conventional error correcting system, in a signal containing error bits exceeding the error correcting capacity, even normal bit data is also corrected by error correction processing Since this cannot be corrected by the subsequent error correction processing, the correcting capacity is extremely degraded. Also, when this abnormally corrected signal is replaced with a subsequent signal, the time required for a series of error corrections is prolonged. This influence on, e.g., FM multiplex broadcasting is that it takes a very long time to display information or characters on the screen of a liquid crystal display or the like.

Data error correcting method for digital signal frames and apparatus used in the method


A scintillator for neutron detection, comprising a metal fluoride crystal containing, as constituent elements, a metal having a valence of 2 or higher, such as calcium, aluminum or yttrium; lithium; and fluorine, the metal fluoride crystal containing 1.1 to 20 atoms per unit volume (atoms/nm3) of 6Li, having an effective atomic number of 10 to 40, containing a lanthanoid such as cerium, praseodymium or europium, and being represented by, for instance, LiCaAlF6, LiSrAlF6 and LiYF4. The scintillator for neutron detection has high sensitivity to neutron rays, and is reduced in a background noise attributed to γ rays.

A scintillator is a substance which, when hit by radiation such as α rays, β rays, γ rays, X-rays, or neutron rays, absorbs the radiation to emit fluorescence. The scintillator is used for radiation detection in combination with a photodetector, such as a photomultiplier tube, and has wide varieties of application fields such as the medical field, for example, tomography, the industrial field, for example, nondestructive inspection, the security field, for example, inspection of personal belongings, and the scientific field, for example, high energy physics.
Among the scintillators are various types of scintillators available according to the types of radiation and the purposes of use. They include inorganic crystals such as Bi4Ge3O12, Gd2SiO5:Ce, PbWO4, CsI, and KI, organic crystals such as anthracene, fluorescent substance-containing polymers such as polystyrene and polyvinyltoluene, and special scintillators including liquid scintillators and gas scintillators. When neutron rays are the object of detection, they are generally detected by utilization of a nuclear reaction which converts neutrons promptly into charged particles having energy, since neutrons have strong power to pass through a substance without performing any interaction in the substance.
Typical characteristics demanded of the scintillator include a large quantity of light (light emission intensity), high stopping power for radiation (detection efficiency), and fast decay of fluorescence (fast response). The scintillator designed to detect neutrons, in particular, needs to have the ability to discriminate between neutrons and the γ rays, because a radiation capture reaction tends to occur between neutrons and the absorbing substance, generating γ rays.
A 6Li glass scintillator has so far been used as a scintillator for neutron detection. However, its manufacturing process has been very difficult and thus expensive, and there has been a limit to its upsizing. A scintillator for neutron detection, comprising a fluoride crystal, on the other hand, is advantageous in that an upsized scintillator can be produced at a low cost. For example, a scintillator comprising a lithium barium fluoride crystal has been proposed. However, this scintillator has high sensitivity to γ rays, and its background noise attributed to γ rays has been great. Thus, there has been need to take a complicated technique in using it as a scintillator for neutron detection (see Non-Patent Document 1).
In connection with such problems, the inventors have attempted to apply cerium-doped LiCaAlF6 crystals as scintillators for neutron detection. In making these attempts, they have performed the evaluation, etc. of scintillation characteristics under simulated conditions involving ultraviolet excited light emission or α ray irradiation. These crystals cause light emission by mechanisms in two stages, namely, generation of α rays which are secondary radiation due to the reaction of incident neutrons with 6Li (primary mechanism), and light emission of ultraviolet rays at about 290 nm ascribed to the electron transition of Ce ions by the α rays (secondary mechanism). However, the evaluations made so far have not involved irradiation with neutron rays per se. This means that the primary mechanism has not been evaluated, namely, that the efficiency of α ray generation has not been evaluated at all. As seen from these facts, the true characteristics of the crystals as scintillators for neutron detection have not been evaluated. As a result, the optimal composition of the scintillator for neutron detection has not been specified yet (see Non-Patent Document 2). The 6Li content (to be described later) in the crystals used in the above-mentioned publicly known technologies has only been of the order of 0.73 atom/nm3, and the inventors themselves have confirmed that such a content results in the insufficient efficiency of neutron detection.
Thus, an ideal scintillator for neutron detection which fulfills all the characteristics is not existent at the present time. In the present invention, a material comprising a substance which absorbs the incident neutrons to emit fluorescence is called a scintillator for neutron detection.
Non-Patent Document 1: C. W. E. van Eijik et al., "LiBaF3, a thermal neutron scintillator with optimal n-gamma discrimination", Nuclear Instruments and Methods in Physics Research A 374 (1996) 197-201.
Non-Patent Document 2: Kentaro Fukuda, Kenji Aoki, Akira Yoshikawa and Tsuguo Fukuda, Abstracts of Lectures at the 66th Congress of the Japan Society of Applied Physics, No. 1, 211 (2005)

Scintillator for neutron detection and neutron detector


Methods for purifying fucoidan in extracts from brown seaweed are disclosed. In particular, methods of purifying fucoidan in the extract to remove heavy metal ions, bacterial and endotoxin contaminants, and other impurities are disclosed. The methods include the use of a chelating agent, selective precipitation, and filtration.

Normal blood coagulation is a complex physiological and biochemical process that is regulated at several levels. The process of blood coagulation involves activation of a coagulation factor cascade leading to fibrin formation and platelet aggregation along with local vasoconstriction (reviewed by Davie et al., Biochemistry 30:10363, 1991). The clotting cascade is composed of an "extrinsic" pathway thought to be the primary means of normal coagulation initiation and an "intrinsic" pathway contributing to an expanded coagulation response. The normal response to a bleeding insult involves activation of the extrinsic pathway. Activation of the extrinsic pathway is initiated when blood comes in contact with tissue factor (TF), a cofactor for factor VII that becomes exposed or expressed on tissues following insult. TF forms a complex with FVII that facilitates the production of FVIIa. FVIIa then associates with TF to convert FX to the serine protease FXa, which is a critical component of the prothrombinase complex. The conversion of prothrombin to thrombin by the FXa/FVa/calcium/phospholipid complex stimulates the formation of fibrin and activation of platelets, all of which is essential to normal blood clotting. Normal hemostasis is further enhanced by intrinsic pathway factors IXa and VIIIa, which also convert FX to FXa. See also Weitz, J. I., et al., Chest, 126 (3). September 2004 (Suppl), 265 S.
Sulfated polysaccharides are a class of molecules characterized by a plethora of biological activities with often favorable tolerability profiles in animals and humans. These polyanionic molecules are often derived from plant and animal tissues and encompass a broad range of subclasses including heparins, glycosaminoglycans, fucoidans, carrageenans, pentosan polysulfates, and dermatan or dextran sulfates. Heparin-like sulfated polysaccharides exhibit differential anticoagulant activity mediated through antithrombin III and/or heparin cofactor II interactions (Toida T C, Linhardt, R J., Trends in Glycoscience and Glycotechnology 2003; 15:29-46).
While one such sulfated polysaccharide, oral heparin, has been considered for development as an anticoagulant (A Dunn, Idrugs, 3:817-824, 2000), heparin is inadequate because of its serious complications which include intraoperative and postoperative bleeding, osteoporosis, alopecia, heparin resistance, heparin rebound, heparin-induced thrombocytopenia (HIT), heparin-induced thrombocytopenia thrombosis syndrome (HITTS), and other disadvantages including multiple days for anticoagulation to attenuate after discontinuing the drug (Iqbal O, et al, Fareed J, Expert Opin Emerg Drugs 6:111-135, 2001; Roberts, H R, Anesthesiology 100:722-730, 2004). Heparin is conventionally administered parenterally, and possesses an oral uptake level of only about 1% (Fitton, J. H., Glycoscience, The Nutrition Science Site, modified Jan. 1, 2005).
In contrast to heparin, another sulfated polysaccharide, fucoidan, a sulfated polysaccharide isolated from sea algae, has been shown to regulate (i.e., promote) coagulation (U.S. Patent Publication No. 2005/0282771). Specifically, fucoidans, when administered at low concentrations in vitro, or low subcutaneous doses in vivo, provide improved (accelerated) clotting in hemophilic settings through extrinsic pathway activation (Liu, T., et al., and Johnson, K. W., Thrombosis and Haemostasis, 95:68-76, 2006), demonstrating a pro-coagulant activity. At higher doses fucoidan can have an anticoagulant effect similar to heparin. In light of the problems associated with current anticoagulants like heparin or warfarin, there clearly remains a need for agents, such as fucoidan, that can overcome one or more of the problems associated with currently available anticoagulant therapy.
Thus, there remains a need for an improved method to cost-effectively and efficiently produce fucoidan enriched extract with optimal activity for procoagulant or anticoagulant therapeutic use.

This patent is subject to a terminal disclaimer.

Methods for fucoidan purification from seaweed extracts


A method for preparing a Pickering emulsion using a peanut protein isolate includes preparing a peanut protein isolate dispersion liquid from a peanut protein isolate solution as a raw material; preparing a mixed dispersion of protein and polysaccharide using a polysaccharide solution and the peanut protein isolate dispersion; adding transglutaminase to the mixed dispersion of protein and polysaccharide, preparing a monolithic gel by cross-linking reaction; preparing a microgel particle dispersion by using the monolithic gel as a raw material; and further adding the microgel particle dispersion to an edible oil to obtain a Pickering emulsion. During the preparation process, no inorganic material is added, and the obtained Pickering emulsion has good biosafety and strong biocompatibility. The prepared Pickering emulsion can keep stable at room temperature for 30 days or more, and can be used as a delivery system for fat-soluble and photosensitive active substances.

Emulsions play a critical role in the food industry, for example, protein drinks, ice cream, mayonnaise and the like are common emulsion systems in food consumption. Emulsion not only exhibits unique sensory qualities, but also has important value in nutrient delivery. However, in recent years, the safety of low-molecular-weight surfactants (LWSFs) in traditional emulsifiers has caused consumers' concern, and food emulsions without LWSFs will be more suitable for the actual needs of consumers.
Pickering emulsion is a kind of emulsion which is stabilized by solid particles, rather than traditional emulsifiers. Compared with a traditional emulsion which is stabilized by low-molecular-weight surfactants and natural macromolecules, the adsorption process of solid particles on the water-oil interface, which play the function of emulsification in a Pickering emulsion, is irreversible, and the particles not only reduce the total free energy of the system, but also provide a spatial physical barrier for the contact between the droplets, which gives the Pickering emulsion a stronger stability.
However, at present, the particles capable of stabilizing the Pickering emulsion are mostly inorganic material particles such as SiO2 and TiO2. When applied to the food field, they have many problems such as low bioavailability and poor biodegradability, and thus there is an immediate need to develop food-grade Pickering emulsion.
Peanut protein is rich in nutrient value and contains 8 kinds of essential amino acids. Wherein, the content of lysine is 3 to 8 times higher than that of rice, wheat and corn, and the effective utilization rate of lysine is up to 98.94%, while the effective utilization rate of lysine in soybean is only 78%. In addition, arginine and glutamic acid are high in content. The peanut protein has functions of brain strengthening and memory enhancement. The contents of indigestible sugar, raffinose and stachyose in peanut protein is equivalent to 1/7 of soy protein, and thus the peanut protein does not cause bloating, and has a biological value much higher than that of soybean. In addition, peanut protein has strong functional properties, good emulsifying properties and good gelling properties, and it can be used in meat products and cereal baked food to improve the texture and structure of the products. Peanut protein is a high quality raw material for the development of food-grade Pickering emulsions, in both terms of nutritional enhancement and functional quality.
However, so far there is no ideal method for preparing a Pickering emulsion using peanut protein isolate.

Pickering emulsion prepared using peanut protein isolate and preparation method thereof

INSTITUTE OF FOOD SCIENCE AND TECHNOLOGY, CHINESE ACADEMY OF AGRICULTURAL SCIENCES


A system for detecting chemical/biological substances and a detection method. The system comprises a plurality of sensing units or nodes and a radiofrequency link. Each unit has several sensors with different sensing curves. Each sensor is able to transmit information related to the sensed substance on a specific frequency. The sensors preferably comprise AlGaN/GaN high electron mobility transistors.

1. Field
The present writing is directed to GaN-based sensor nodes for in situ detection of gases.
2. Related Art
The AlGaN/GaN hetero structures contain polarization sheet charges (i.e. a two dimensional electron gas) at the interfaces due to differences in the piezoelectric effect of AlGaN and GaN. These polarization charges respond very sensitively to the exposure to polar liquids and gas molecules. In the AlGaN/GaN high electron mobility transistors (HEMT), the ions created by the reaction of chemical molecules with the transition metal contacts induce significant effects on the electrostatic surface termination of the nitride and thus influence the barrier height of the Schottky contacts. In fact, several experimental results published in recent literature indicate that AlGaN/GaN HEMT has a strong potential for chemical sensor. See, for example, "Gas Sensitive GaN/AlGaN-heterostructures" by Schalwig J, Muller G, Eickhoff M, Ambacher O, Stutzmann M, Sensors and Actuators B-Chemical, 87 (3): 425-430 Dec. 20 2002; "Group III-nitride-based Gas Sensors for Combustion Monitoring" by Schalwig J, Muller G, Eickhoff M, Ambacher O, Stutzmann M, Materials Science and Engineering B-Solid State Materials for Advanced Technology, 93 (1-3): 207-214 May 30, 2002; "GaN-based heterostructures for sensor applications" by Stutzmann M, Steinhoff G, Eickhoff M, Ambacher O, Nebel CE, Schalwig J, Neuberger R, Muller G, Diamond and Related Materials, 11 (3-6): 886-891 March-June 2002; "High-Electron-Mobility AlGaN/GaN Transistors, (HEMTs) for Fluid Monitoring Applications" by Neuberger R, Muller G, Ambacher O, Stutzmann M, Phys. Status Solidi A 185, 85 (2001); and "GaN-based diodes and transistors for chemical. Gas biological and pressure sensing" by Pearton S. J., Kang B. S., Kim S., Ren F., Gila B. P., Abernathy C. R., Lin J., Chu S. N. G., J. Phys.: Condens. Matter 16 (2004) R961-R994.
However, a limitation of AlGaN/GaN hetero structure devices, similar to other chemical sensing FETs (field effect transistors), is poor selectivity in chemical detection. The low selectivity in chemical detection is a major hurdle to practical approach.
Further, a majority of the current stand-off or remote chemical detection/monitoring systems are based on optical/IR spectral analysis and deployed on mobile platforms. These systems offer excellent chemical identification capability but are large, expensive, and require long data acquisition times.
Another major drawback of optical/IR systems is that functionality can be dramatically reduced in bad weather/fog due to undesirable signal attenuation. In addition, for the safety and security of the end users, real-time and autonomous monitoring of the continuously changing chemical environment using remote sensing networks is also very important.

The United States of America as represented by the Secretary of the Navy


Disclosed are various embodiments for inferring quality in point cloud-based three-dimensional objects using topographical data analysis. A first graph is generated representing a three-dimensional model, each vertex in the first graph representing a respective connected component within a layer of the three-dimensional model and each edge in the first graph representing a connection between two respective connected components within two respective layers of the three-dimensional model. A second graph representing negative space associated with the three-dimensional model is also generated, each vertex in the second graph representing a connected component of a negative space region within the layer of the three-dimensional model and each edge in the second graph representing a connection between two respective connected components with two respective layers of the three-dimensional model. A persistent homology analysis is applied to the first graph to determine whether a hole or tunnel exists in each vertex of the first graph. An error with the three-dimensional model can then be identified based at least in part on the first graph, the second graph, and the persistent homology analysis.

Three-dimensional (3D) printing is a popular technology. However, the quality of three-dimensional models can be difficult to assess prior to actually 3D printing an object based on the model. For example, point cloud-based models, such as those generated by 3D scanners, may not represent an object with complete fidelity. This can result 3D models having holes or tunnels where a solid mass should be located, having two or more components connected when they should not be connected, having two or more components not be connected when they should be connected, as well as other problems.

Inferring quality in point cloud-based three-dimensional objects using topographical data analysis


There is provided a balun transformer, in which first to fourth layer coils are stacked and coupled magnetically; one end of each coil of the first to fourth layer coils is grounded; the second and third layer coils are connected in parallel, an unbalanced signal is input/output to/from a common terminal of the second and third layer coils; a first balanced signal is input/output to/from the other end of the first layer coil; and a second balanced signal is input/output to/from the other end of the fourth layer coil.

1. Field of the Invention
The present invention relates to a balun transformer used for a balance-unbalance signal converter for converting balanced signals into an unbalanced signal and vice versa, a phase converter and the like, and more particularly to a compact, broadband balun transformer and a mounting structure for a balun transformer and an electronic apparatus having a built-in mounting structure.
2. Description of Related Art
A balun transformer is used, for example, as a converter for converting balanced signals into an unbalanced signal or vice versa. Balanced lines have a pair of signal lines, and a balanced signal is propagated as a potential difference between paired signal lines. An unbalanced line is used for an unbalanced signal propagated as a potential at one signal line relative to a ground potential. As an unbalanced signal is input to an unbalanced terminal of a balun transformer, two balanced signals having a phase difference (opposite phases) of 180° and the same amplitude are output from balanced terminals of the balun transformer. A mobile communication apparatus such as a portable phone uses the balun transformer as a balance-unbalance signal converter. The balun transformer is also called a balun and a balun circuit.
There are many reports on a balun transformer.
The following description is given in Patent Document 1: Japanese Patent Application Publication No. 2000-58328 (paragraphs 0010 and 0011) titled "Stacked Type Balun Transformer".
The stacked type balun transformer regarding the invention described in Patent Document 1 includes at least a pair of first and second strip lines electromagnetically coupled via a dielectric layer and facing each other in a magnetically coupled area and a pair of third and fourth strip lines electromagnetically coupled via a dielectric layer and facing each other in an magnetically coupled area. The two pairs of strip lines are stacked with a dielectric layer in between, and a ground electrode facing the strip line is stacked having a dielectric layer in between at least at one of a position between the two pairs of strip lines, a position above the two pairs of strip lines, and a position under the two pairs of strip lines. One end of the first strip line and one end of the fourth strip line are electrically connected; the other end of the first strip line is electrically connected to an input/output external electrode; the other end of the fourth strip line is opened; one end of the second strip line is electrically connected to the input/output external electrode and the other end thereof is electrically connected to the ground electrode; and one end of the third strip line is electrically connected to the input/output external electrode and the other end thereof is electrically connected to the ground electrode.
With this structure, each strip line is not juxtaposed on the same dielectric layer, but each strip line is stacked with a dielectric layer positioned in between so that a balun transformer of a small area can be realized. Further, a thickness of the dielectric layer sandwiched between the pair of strip lines electromagnetically coupled can be adjusted independently from the dielectric layer sandwiched between the other pair of strip lines.
The following description is given in Patent Document 2: Japanese Patent Application Publication No. 2003-7538 (paragraphs 0019 and 0020, paragraphs 0024 and 0025, FIG. 3) titled "Stacked Type Balun Transformer".
FIG. 15 of the present specification corresponds to FIG. 3 of Patent Document 2, and is an electrical equivalent circuit of the first embodiment of the stacked type balun transformer of Patent Document 2.
A balanced signal terminal 242a is electrically connected to one end of a first line 225, a balanced signal terminal 242b is connected to one end of a second line 228, and a relay terminal 243 is electrically connected to ends of a third line 224 and a fourth line 227.
In the balun transformer 221, the third and first lines 224 and 225 are disposed between the ground electrodes to constitute a strip line structure. The fourth and second lines 227 and 228 are also disposed between the ground electrodes to constitute a strip line structure. The third and fourth lines 224 and 227 are serially connected via the relay terminal to constitute an unbalanced transmission line 238. The first and second lines 225 and 228 constitute balanced transmission lines 239 and 239. The lines 224 and 225 and the lines 227 and 228 are formed facing each other with a dielectric sheet being interposed therebetween.
Although one end of the unbalanced transmission line 238 (specifically, at the end of the line 227) is opened, this end may be set as a ground end. The balun transformer 221 has upper and lower ground electrodes so that the shielding effect is provided.
Next, with reference to FIG. 15, description will be made on a case in which the balun transformer 221 is used as a balance-unbalance signal converter. As an unbalanced signal S1 is input to the unbalanced signal terminal 241, the unbalanced signal S1 propagates the unbalanced transmission line 238 (line 224-relay terminal 243-line 227). The line 224 line-couples the line 225, and the line 227 line-couples the line 228. Therefore, the unbalanced signal S1 is converted into balanced signals S2 which are output from the balanced signal terminals 242a and 242b. Conversely, as the balances signals S2 are input to the balanced signal terminals 242a and 242b, the balanced signals S2 propagates the balanced transmission lines 239 and 239 and converted into the unbalanced signal S1 at the unbalanced transmission line 238 which is then output from the unbalanced signal terminal 241.
The following description is given in Patent Document 3: Japanese Patent Application Publication No. 2003-8312 (paragraphs 0003 to 0006, paragraphs 0013 to 0015, FIGS. 1 to 3) titled "Balun Transformer".
FIGS. 16A to 16C of the present specification correspond to FIGS. 1 to 3 of Patent Document 3. FIG. 16A is a circuit diagram of a balun transformer according to an embodiment of the invention of Patent Document 3, and FIGS. 16B and 16C are circuit diagrams showing examples of an existing balun transformer.
Some of balun transformers interconnecting an unbalanced transmission line and balanced transmission lines to transmit a high frequency signal use distributed constant transmission lines. Examples of an existing balun transformer of this type are shown in the circuit diagrams of FIGS. 16B and 16C.
In FIGS. 16B and 16C, a first transmission line 310 has a length of about a quarter wavelength or shorter of a high frequency signal. A second transmission line 311 having a length of about a quarter wavelength or shorter is disposed parallel to the first transmission line 310 on the same plane or three-dimensionally parallel to the first transmission line and electromagnetically coupled to the first transmission line. An input terminal IN is an unbalanced terminal provided to the first transmission line 310, and output terminals OUT1 and OUT2 are balanced terminals provided to opposite ends of the second transmission line 311. In the example shown in FIG. 16B, a center of the second transmission line 311 is grounded, and in the example shown in FIG. 16C, the second transmission line 311 is not grounded.
As shown in FIGS. 16B and 16C, a balun transformer constituted of existing transmission lines uses the first transmission line 310 whose one end is used as unbalanced input terminal IN and whose other end is grounded, and the second transmission line 311 whose opposite ends are used as the balanced output terminals OUT1 and OUT2, and has either the structure that the center of the second transmission line 311 is grounded as shown in FIG. 16B or the structure that the second transmission line 311 is not grounded as shown in FIG. 16C.
The existing balun transformer of this type is, however, associated with the following problem. If an unbalanced signal is input to the unbalanced signal input terminal IN of the balun transformer, in the examples shown in FIGS. 16B and 16C, the positional relation between the input terminal IN and output terminal OUT1 are in a proximity positional relation so that the input terminal IN and output terminal OUT1 are capacitively coupled. Therefore, a phase shift from the opposite phases and an amplitude level difference between two balanced signals picked up from the output terminals OUT1 and OUT2 of the balun transformer become larger as the frequency becomes higher.
FIG. 16A is a circuit diagram showing an example of the balun transformer of the embodiment of Patent Document 3. In FIG. 16A, a first transmission line 301 has a length of about a quarter wavelength or shorter of a high frequency signal. A second transmission line 302 and a third transmission line 303 having a length of about a ⅛ wavelength or shorter are disposed parallel to the first transmission line 301 on the same plane or three-dimensionally parallel to and straight to the first transmission line and electromagnetically coupled to the first transmission line. An unbalanced terminal IN as an input terminal of an unbalanced signal is provided at one end of the first transmission line 301. Balanced terminals OUT1 and OUT2 for balanced signals are provided to confronting ends of the second and third transmission lines 302 and 303. The first transmission line 301 has the unbalanced terminal IN at its one end, and the other end is grounded. The second and third balanced lines 302 and 303 have the balanced terminals OUT1 and OUT2 at the confronting ends thereof, and the other ends are grounded. The first to third transmission lines 301 to 303 are formed on the surface of or in a dielectric substrate which is not shown in FIG. 16A.
The balun transformer of Patent Document 3 having the structure described above uses as the dielectric substrate including a multi-layer dielectric substrate formed by stacking a plurality of dielectric layers. The first to third transmission lines 301 to 303 are made of microstrip lines, strip lines or coplanar lines formed on the surface of or in a multi-layer substrate having a plurality of dielectric layers. The other ends of the first to third transmission lines 301 to 303 are grounded to an external ground via through conductors such as through hole conductors and via conductors formed in the dielectric substrate and/or terminal electrodes formed on the side walls of the dielectric substrate and made of metalized conductor layers, so-called casterllation conductors or the like. In this manner, the balun transformer which is compact and has excellent high frequency transmission characteristics can be formed on the surface of or in the dielectric substrate. This balun transformer can be formed integrally with a high frequency circuit and is suitable for the high frequency circuit.
In forming the balun transformer of the invention described in Patent Document 3, the dielectric substrate typically a multi-layer dielectric substrate formed by stacking a plurality of dielectric layers, the first to third transmission lines 301 to 303 made of microstrip lines, strip lines, coplanar lines or the like, the unbalanced terminal IN, the balanced terminals OUT1 and OUT2, through conductors, terminal electrodes can be formed by using various materials and types used in well-known high frequency wiring substrates.
The following description is given in Patent Document 4: Japanese Patent Application Publication No. 2002-33216 (paragraphs 0008 to 0010) titled "Stacked Balun Transformer".
An object of the invention of Patent Document 4 is to provide a stacked balun transformer having good coupling in a broadband, particularly at a high frequency of 1 GHz or higher.
The stacked balun transformer of Patent Document 4 is a stacked balun transformer having at least two pairs of λ/4 strip lines electromagnetically coupled, and is characterized in that a non-magnetic layer containing polyvinyl benzyl ether compound is disposed between paired strip lines electromagnetically coupled, and that a magnetic layer made of polyvinyl benzyl ether compound dispersed with magnetic powders is disposed above and under a composite layer constituted of the paired strip lines and the non-magnetic layer.
Since the non-magnetic layer containing polyvinyl benzyl ether compound is disposed between paired strip lines, capacitive components between the strip lines can be reduced because the polyvinyl benzyl ether compound has a low relative dielectric constant of about 2.5 to 3.5. Furthermore, the number of crossed fluxes between strip lines can be increased because of non-magnetism so that a coupling coefficient increases. Polyvinyl benzyl ether compound can be manufactured easily by the epoxy resin manufacturing process. There is no problem of cracks and warps as in the case of baking ceramic.
The following description is given in Patent Document 5: Japanese Patent Application Publication No. 2005-306696 (paragraphs 0008 and 0009) titled "Magnetic Ferrite, Common Mode Noise Filter Using Magnetic Ferrite, and Chip Transformer".
The invention of Patent Document 5 uses magnetic ferrite having the main components of Fe, Co and Zn having compositions in the range of 39.5:53.0:7.5 mol %, 39.5:48.0:12.5 mol %, 20.0:67.5:12.5 mol %, and 20.0:55.0:25.0 added with copper oxide of 8 to 14 wt %.
The magnetic ferrite, a common mode noise filter and a chip transformer using the magnetic ferrite can realize magnetic ferrite which has a low loss in a high frequency band and can be baked together with silver electrodes, and can realize a high frequency common mode noise filter and chip transformer having a large coupling coefficient between two coils, by using the magnetic ferrite in stacked electronic components.

Balun transformer, mounting structure of balun transformer, and electronic apparatus having built-in mounting structure


A pulse generator circuit arrangement for the search for insulation faults in IT networks includes a rectifier circuit for transforming an IT network voltage into a DC intermediate circuit and switching elements having a trigger signal input for switching on and off a DC intermediate circuit voltage. A circuit device downstream of the switching elements generates a pulsed current to be supplied to the IT network. The circuit arrangement includes a control and evaluating logic for determining the insulation resistance of the IT network and also a circuit device for generating the pulsed current, which is formed as a current regulating device and allows a dynamic adjustment of the pulsed current depending on the determined insulation resistance.

To ensure a high availability and operating security of the electric power supply and to guarantee personal safety in the area of electric installations, power supply networks are being increasingly employed whose active components are separated from the earth potential. In this type of power supply network, called unearthed IT system, an active conductor can have an insulation fault without the running operation having to be interrupted since due to the ideally infinitely high impedance value between the conductor and earth in this first fault case no closed circuit can form. In this context, a faulty state of the IT system, in particular a fault to frame or an earth fault, meaning a conductive connection of inactive system parts to conductive operating parts or a conducting connection of an active conductor to the ground, are to be understood as an insulation fault.
It becomes clear from this point of view that the resistance in the network to be monitored, including all resistances of all connected operating parts to earth (insulation resistance), have to be monitored constantly because a possible further fault on another active conductor (second fault) could cause a fault loop and the fault current running therein in connection with an overcurrent protection circuit would result in a shut-down of the system. Through a constant insulation monitoring of the unearthed IT system a drop in the insulation resistance can be detected and reported in time.
According to the state of the art, the measuring processes for determining the insulation resistance are based in principle on the superposition of a measuring voltage, generated in an insulation monitoring device, between the conductors of the IT network and the ground so that a specific measuring current proportional to the insulation fault occurs, which causes a corresponding voltage drop on a measuring resistance of the insulation monitoring device. If the voltage drop exceeds a certain value as a result of a dropped insulation resistance and thus of a higher measuring current, a report is triggered. In order to prevent measurement distortions with regard to a reliable insulation monitoring in today's modern networks, in which a plurality of operating parts are equipped with electronic components, the distortions being caused for example by direct current components generated by inverters, the measuring methods have been continuously developed further. In pure alternating current networks without distorting direct current components, the method of superimposing a measuring DC voltage can be applied, whereas in faulty environments a controlled, specifically clocked measuring voltage for driving pulsed signals is employed.
When a drop of the insulation resistance has been detected, insulation fault location begins in that the insulation monitoring device or a separate testing device generates a test current and supplies it to the IT network. To be able to reliably detect insulation faults in a DC network and due to the available measuring technology, the test current supplied for insulation fault location preferably also has a pulse-shaped flow of alternating polarity (pulsed current) so that the test current flows through both conductors (L+ and L−) in an alternating manner. This test current signal is detected by all measuring current transformers which lie in the faulty cable outlet of the network and is analyzed and reported by an insulation fault analyzing device. By means of the allocation of measuring current transformer/circuit, respectively cable outlet, the fault position can be located.
In this approach common according to the state of the art it proves disadvantageous that the determination of the insulation resistance and the localization of insulation faults present two separate, self-contained processes. As a result, for example for making a new measurement of the insulation resistance during the already initiated fault search, the supplying of the test pulses has to be interrupted in order to be able to perform the insulation resistance measurement with a suitable measuring current. Thus, a simultaneous determination of the insulation resistance during the fault search is not possible in a simple manner.
Furthermore, devices according to the state of the art do offer the possibility to stabilize the test current in the fault search during the duration of the pulse by means of corresponding circuit devices, such as current regulators and to limit the test current to one or several maximum values, but these configurations only constitute a relatively crude adjustment of the pulsed current to the network conditions so that often an unnecessarily high pulsed current is generated. In the course of this, an excessive heat build-up can occur in the generator circuit, which so far was only counteracted by the use of large-scale cooling bodies or excess temperature deactivations. In a disadvantageous manner these countermeasures thus lead directly or indirectly to an increase in costs due to operation disruptions.
Furthermore, in shut-down IT systems which have to be inspected no voltage is available to drive the pulsed current. Here, consequently, the problem of a suitable voltage supply for generating the test current presents itself as a matter of principle.

Pulse generator circuit arrangement and method for generating pulsed signals for insulation fault location in IT networks


A system for transmitting power over a direct voltage network. A first power station connects one alternating voltage network to the direct voltage network. The first power station includes a converter for bidirectionally transferring power between the direct voltage network and the alternating voltage network. The converter maintains constant value of voltage on the network, or operates in a second alternative mode of controlling constant current between the alternating voltage network and the direct voltage network. When the voltage on the direct voltage network drops below a reference value, a second power station connected to the direct voltage network and to a remaining alternating voltage network takes over the voltage regulation function. The second power station prior to taking over the voltage regulating friction was in a current regulating function. In this way, when the first station reaches its limits of voltage regulation, the second station is enabled to take over the voltage regulating function switching out of a current regulating function.

The present invention relates to a system for transmitting electric power comprising a direct voltage network, and at least two alternating voltage networks which are connected to the direct voltage network through a respective power station. The power stations transfers power between the direct voltage network and the respective alternating voltage network, and has at least one VSC converter to convert direct voltage into alternating voltage, and conversely convert alternating voltage to a direct voltage. An apparatus in a first station controls the converter of the station to regulate the direct voltage of the direct voltage network and maintains the direct voltage at a predetermined nominal value. An apparatus of the other station controls the converter of that station for regulating the current flowing between the respective connected alternating voltage network and its connected station.
Such a system is known through the thesis "PWM and Control of Two and Three Level High Power Voltage Source Converters" by Anders Lindberg, Kungliga Tekniska Hogskolan, Stockholm, 1995, which describes a system for transmitting electric power through a direct voltage network for High Voltage Direct Current (HVDC). It is emphasized that the invention is not restricted to this application, but for purposes of illustration the invention will be described with respect to this known system.
Prior to the system described in the thesis, systems for transmitting electric power through a direct voltage network for High Voltage Direct Current have been based upon the use of line-commutated CSC (Current Source Converter) converters in the power stations. The development of IGBTs (Insulated Gate Bipolar Transistor=bipolar transistor having an insulated gate) for high voltage applications which may be easily turned on and turned off simultaneously, has made it possible to create valves for VSC (Voltage Source Converter) converters. VSC converters permit forced commutation as an alternative. This type of power transmission between a direct voltage network for High Voltage Direct Current and alternating voltage networks connected thereto offers several important advantages over the use of the prior art line-commutated CSCs used in HVDC. Th VSC (Voltage Source Converter) permits the consumption of active and reactive power to be controlled independently of each other, and there is no risk of commutation failures in the converter and no corresponding risk of transmitting commutation failures between different HVDC links, which may take place in line-commutated CSC. Furthermore, there is the possibility of feeding power to a weak alternating voltage network or a network which doesn't generate its own power (a "dead" alternating voltage network).
In a system of the type discussed above for HVDC with VSC converters, the direct voltage of the direct voltage network is determined in a first power station, and it is desirable to control the direct voltage level without any rapid telecommunication between a station having voltage-regulating apparatus and the other stations along the direct voltage network. Since each power unbalance results in a change of the direct voltage, which is then corrected by the voltage-regulating station, such a communication possibility will be superfluous. Should the power fed into the network drop as a consequence of limitations in an alternating voltage network for feeding power to a direct voltage network, or in the voltage-regulating station, or should the power fed out of the network exceed the available power fed in, the direct voltage of the direct voltage network will drop. The direct voltage will drop so much that the power fed out is reduced to such a level that power balance is reestablished. This means that the voltage-regulating station has arrived at its regulation limit and cannot maintain the direct voltage at said determined nominal value. This may result in collapse of the direct voltage and temporary disabling of parts of the HVDC system.

System for regulating the active power transferred into and out of direct voltage network by multiple power stations


A process is described for treating nitrogen-oxide containing gases at temperature in the range of 300-560.degree. C. in the presence of a cerium containing zeolite catalyst and an excess of an NH-containing compound such as ammonia or an aqueous urea solution as a reducing agent. Excess reducing agent is converted to nitrogen gas during the process. Selective catalytic reduction using ammonia water or an aqueous urea solution as a reducing agent is also described for converting nitrogen oxides in diesel exhaust gas and preventing oxidation of sulfur dioxide.

1. Field of the Invention
The invention relates to a process for treating nitrogen oxide-containing gas substantially having a temperature in the range of 300-560.degree. C., for instance exhaust gas of a diesel engine or the off-gas obtained from gas engines. More particularly, the invention relates to a process wherein nitrogen oxide-containing gas is passed over a zeolite-comprising catalyst system in the presence of a NH-containing compound as reducing agent, in order to obtain a gas containing as few environmentally objectionable or noxious compounds as possible.
Every year, more so-called "Total Energy" plants are installed in greenhouses. The most important source of energy for these plants is natural gas. Such plants are used for heating and for providing electric energy for lighting the greenhouses, for which reason these plants are called heat/power coupling plants. The off-gas of the plant, which has a temperature of up to about 450.degree. C. and which contains a high CO.sub.2 content, is essentially suitable to be utilized for fertilizing purposes if this gas is substantially free of nitrogen oxides.
More in detail, the amount of nitrogen oxides in the off-gas of a conventional gas engine will be of the order of 1500-2000 ppm. In order to limit the emission of NO.sub.x, typically so-called lean-burn natural gas engines are used in the greenhouses as heat/power coupling plant. These engines are operated with an excess of air to limit the NO.sub.x emission. More particularly, in this manner the NO.sub.x concentration in the off-gases can be reduced from about 1500-2000 ppm to 400-600 ppm. On the other hand, the efficiency of the engines is reduced by the use of an excess of air. Because the off-gases are used for CO.sub.2 fertilization in closed spaces, the absolute NO.sub.x concentration in these off-gases must meet high standards. The standard applying in this connection is a maximum of 25-50 ppm NO.sub.x. Meanwhile, different catalyst systems have been described which enable the effectuation of NO.sub.x conversions, in such a manner that the NO.sub.x concentration in test systems satisfies the standard mentioned.
The gas engines, however, only deliver a seemingly constant NO.sub.x signal. FIG. 1 shows the amount of NO which is emitted in time by a particular gas engine. At an average NO.sub.x emission level of about 1100 ppm, the signal is found to exhibit a fluctuation of an amplitude of some 100 ppm. This means that in the case or the stationary operation of a process in which NO.sub.x is reduced--which means that a constant stream of the NH-containing compounds is supplied to the off-gas--the standard of 25-50 ppm can only be achieved in the case where a highly complicated and costly control mechanism is employed. A second option, which involves working with an excess of the NH-compound containing reducing agent in order to ensure that a largest possible amount of NO.sub.x is converted is not attractive, since in that case NH-containing compounds slip through along with the treated off-gas. NH compounds are even more noxious than NO.sub.x compounds.
A similar problem presents itself in the treatment of exhaust or off-gases of, for instance, non-stationary diesel engines or other engines of equipments which are operated transiently. Such an engine will be operated highly dynamically, i.e., over time, depending on the load, the NO.sub.x concentration, the gas stream and the temperature of the exhaust gas fluctuate strongly. FIG. 2 gives an impression of these fluctuations. This figure shows a driving cycle or a truck. Plotted along the axes are couple and speed, which parameters can be translated by the skilled person to the gas stream and NO.sub.x concentration.
It will be clear that all this gives problems in regulating the amount of reducing agent which is to be supplied to the catalyst system. These problems could be overcome to a considerable extent if an excess of reducing agent can be used without environmental problems.
Accordingly, there is a need for a process for treating nitrogen oxide-containing gas, wherein nitrogen oxides are reduced in the presence of NH-containing compounds, without the occurrence of any emission (slip) of NH-containing compounds to the environment when these reducing agents are present in excess. More generally, slip of NH compounds is the problem with all known SCR (selective catalytic reduction) processes.
The present invention is directed to an aftertreatment process wherein use is made of a selective catalytic reduction in which a NH-containing compound or composition, for instance ammonia water or an aqueous urea solution, is used as reducing agent.
2. Description of the Related Art
European patent application 0 263 399 describes a method for the catalytic reduction of nitrogen oxides from off-gases coming from power plants and chemical plants. This method relates to a low-temperature deNO.sub.x process, since the nitrogen oxide reduction takes place in the range of 150-350.degree. C. and preferably of 150-280.degree. C. The catalyst which is used in this known method is of the zeolite-Y-type, and in particular of the ion-exchanged zeolite-Y-type. This catalyst is obtained by exchanging ions of sodium zeolite-Y for lithium and/or rare earth ions. One of the possibilities, which, for that matter, is not illustrated in detail, comprises the exchange with Ce ions. Any advantage associated with the use of specifically a CeY zeolite is neither mentioned nor suggested.

Process for treating nitrogen oxide-containing gas using a cerium zeolite


A transistor active bridge circuit (400) rectifies domestic AC mains (for example, 120V, 60 Hz) and/or foreign AC mains (for example, 230V, 50 Hz) with low power loss. The circuit includes first and second field effect transistors (102, 104) of a first channel type, and third and fourth field effect transistors (106, 108) of a second channel type that is different from the first channel type. A set of voltage dividers (110, 112, 114, 116, 118, 120, 122, 124) and voltage clamping devices (126, 128, 130, 132) permit the circuit (400) to efficiently operate over a wider range of input voltages, without potential damage to the field effect transistors. Shoot-through protection devices (420, 430) provide a means for preventing the first and second field effect transistors (102, 104) from conducting simultaneously. Shoot-through protection devices (440, 450) provide a means for preventing the third and fourth field effect transistors (106, 108) from conducting simultaneously.

1. Statement of the Technical Field
The inventive arrangements relate to MOSFET circuits, and more particularly to a circuit for AC voltage rectification and shoot-through current protection.
2. Description of the Related Art
Bridge rectifier type devices are typically used to convert an AC waveform into a DC waveform. Such bridge rectifier type devices often utilize diode components to perform the rectification function. After an AC signal is rectified, the output signal is often filtered to remove unwanted spectral content and to produce a DC voltage. A filtering device utilizing capacitor components, resistor components, and/or inductor components are typically used for this purpose.
Despite the various technologies known in the art, there remains a need for a MOSFET bridge rectifier type device that can rectify a domestic AC mains (for example, 120V, 60 Hz) and/or a foreign AC mains (for example, 230V, 50 Hz) with low power loss. However, rectification of an AC mains signal with a MOSFET type bridge rectifier can create potentially damaging current spikes in an input current. For example, a shoot-through current may result at a zero crossing of an input voltage. The shoot-through current can occur when MOSFETs conduct simultaneously during transitions. The shoot-through current can produce a current spike through the drain of each MOSFET component. This current spike causes a relatively large amount of stress on the MOSFET devices. As a result, at least one of the simultaneously conducting MOSFETs can be damaged. In this regard, a MOSFET bridge rectifier type device is also needed with a shoot-through protection circuit to eliminate the amount of stress on the MOSFET devices during transitions.

Low-loss rectifier with shoot-through current protection


A transmission line includes a post-wall waveguide which includes a dielectric substrate on which a pair of post-walls is formed and a first conductor layer and a second conductor layer opposed to each other with the dielectric substrate interposed therebetween and in which a region surrounded by the pair of post-walls, the first conductor layer, and the second conductor layer is a waveguide region, a waveguide tube having a hollow rectangular shape, being connected with the first conductor layer so as to cover an opening portion formed in a side wall, and in which an inside communicates with the waveguide region through an opening formed in the first conductor layer, and a wire member which is arranged such that through the opening, a first end is located inside the dielectric substrate and a second end is located in the waveguide tube.

Conventionally, a waveguide tube is used as a transmission line for transmitting a high-frequency signal in the microwave band (0.3 to 30 [GHz]) to the millimeter wave band (30 to 300 [GHz]). In recent years, a post-wall waveguide (PWW) has also been used as a transmission line for transmitting such a high-frequency signal. The post-wall waveguide is a square-shape waveguide formed by a pair of conductor layers formed on both surfaces of a dielectric substrate and a pair of post-walls formed by arranging a plurality of conductor posts to penetrate the dielectric substrate in two rows.
The above-mentioned waveguide tube and post-wall waveguide may be used singly; however, they may be used in combination. For example, in a communication module, a transmission line in which a waveguide tube and a post-wall waveguide are combined is used as a transmission line between a transmission-reception circuit and an antenna. In such a communication module, for example, the high-frequency signal output from the transmission-reception circuit is transmitted to the waveguide tube after being transmitted by the post-wall waveguide, and being transmitted from the antenna after being transmitted by the waveguide tube.
The following Patent Documents 1 to 7 disclose a conventional transmission line in which transmission lines of different types are combined. For example, the following Patent Documents 1 to 5 disclose a conventional transmission line in which a waveguide tube and a post-wall waveguide are combined. The following Patent Document 6 discloses a conventional transmission line in which a waveguide tube and a print circuit board are combined. The following Patent Document 7 discloses a conventional transmission line in which a microstrip line and a post-wall waveguide are combined.

Coupling comprising a conductive wire embedded in a post-wall waveguide and extending into a hollow tube waveguide