A bioleaching process is utilized for the extraction of metals from coal fly ash (CFA). The CFA is suspended in an acidic sea water based culture medium and the suspension is incubated with a microorganism culture comprising at least one strain of Thiobacillus thiooxidans capable of growing and producing sulfuric acid in the sea water based acidic culture medium and thereby facilitating the extraction of metals from the CFA. The extracted metals are separated from the CFA raffinate and microorganism cells and are fractionated to provide metal-enriched fractions. A selected Thiobacillus thiooxidans strain is described which has been designated as Thiobacillus thiooxidans ZYR1, a sample of which has been deposited under No. 40453 at the National Collections of Industrial and Marine Bacteria Ltd. (NCIMB) at Aberdeen, Scotland. This selected strain is particularly suitable for the bioleaching of metals from coal fly ash.

CFA is known to contain a variety of metals such as aluminium (Al), titanium (Ti), zinc (Zn), copper (Cu), cobalt (Co), molybdenum (Mo), selenium (Se), boron (B) and many others, usually in the form of insoluble metal-silicates or -oxides (Furuya, K. et al (1987), Environ. Sci. Technol. 21, p.898-903). Many of these metals are toxic to living organisms. Thus, when CFA is disposed of in landfills, in the sea or in other waterways, these metals may leach out of the CFA and enter sources of water for plants and animals including humans. Thus, the various metals contained in CFA represent a potential environmental and health hazard.
Globally, millions of tons of CFA are disposed of annually in industrialised countries, representing a serious potential for environmental pollution and subsequent public health hazard. Power-producing utilities using coal as the energy source are therefore required to safely dispose of the CFA produced as a by-product.
However, the conventional means for detoxifying CFA for the purposes of safely disposing it are both costly and may in themselves also lead to environmental pollution, for example the use of conventional chemical leaching, usually by way of strong acids and at high temperatures (Golden, D. M. (1986) Energy, vol. 11, No. 11/12, p. 1377-1387), requires both costly machinery and chemicals on the one hand, and on the other, chemical by-products, for example strong acids, are produced which must also be disposed of and as such also represent a potential environmental and health hazard.
It has therefore been a long-felt want to establish a process for the detoxification of CFA, by removing therefrom the toxic metals, which is both economically feasible, i.e. allows for the extraction of valuable metals, e.g. aluminium, titanium, cobalt, etc. in commercial quantities, and which does not itself lead to the generation of toxic by-products.
While it has been previously contemplated to use various acid producing bacteria, e.g. Thiobacillus strains in bioleaching methods to extract metals from various metal-bearing sources, none of these methods have been directed specifically to the bioleaching of CFA, nor have any of these methods been successful in generating safely disposable by-products, i.e. they all result in the generation of strong acids which require further expensive and time consuming neutralization treatments.
As noted above, CFA contains a number of toxic metals and thus microorganisms suitable for the bioleaching of CFA must be capable of growing in the presence of these toxic metals.
Furthermore, many coal-fired power stations world-wide are situated at coastal locations with the result that the CFA to be detoxified is often present in sea water, e.g. in consequence of dumping into sea water precipitation pools. Accordingly, microorganisms suitable for bioleaching this CFA must also be capable of growing in a sea water environment, i.e. in the presence of a relatively high salt concentration.
It has heretofore not been disclosed that an acid-producing microorganism suitable for the bioleaching of CFA, e.g. a Thiobacillus strain may be obtained that is capable of growing in a sea water based medium in the presence of CFA.

Bioleaching method for the extraction of metals from coal fly ash using thiobacillus


Injector deposits in a direct injection gasoline engine are reduced by providing as fuel for the operation of said direct injection engine a fuel composition comprising a fuel-soluble compound having the formula (I):

Over the years considerable work has been devoted to additives for controlling (preventing or reducing) deposit formation in the fuel induction systems of spark-ignition internal combustion engines. In particular, additives that can effectively control fuel injector deposits, intake valve deposits and combustion chamber deposits represent the focal point of considerable research activities in the field and despite these efforts, further improvements are desired.
Direct injection gasoline (DIG) technology is currently on a steep developmental curve because of its high potential for improved fuel economy and power. Environmentally, the fuel economy benefits translate directly into lower carbon dioxide emissions, a greenhouse gas that could contribute to possible global warming.
Conventional multi-port injection (MPI) engines form a homogeneous pre-mixture of gasoline and air by injecting gasoline into the intake port, while a direct injection gasoline engine injects gasoline directly into the combustion chamber like a diesel engine so that it becomes possible to form a stratified fuel mixture which contains greater than the stoichiometric amount of fuel in the neighborhood of the spark plug but highly lean in the entire combustion chamber. Due to the formation of such a stratified fuel mixture, combustion with the overall highly lean mixture can be achieved, leading to an improvement in fuel consumption approaching that of a diesel engine.
Injection timing is controlled to match load conditions. The fuel control provides combustion of an ultra lean mixture of gasoline and air for higher fuel efficiency than diesel engines. Also, a compression ratio of about 12.0 compared to that of about 10.5 for multi port injection engines delivers higher volumetric efficiency and response, surpassing conventional MPI engine performance.
There are a number of technical issues to be resolved with DIG technology, and one of them is injector performance with different gasoline fuels on the world market. Being located in the combustion chamber, DIG injectors are exposed to a much harsher environment than conventional spark-ignition engines with port fuel injectors (PFI). This more severe environment can accelerate fuel degradation and oxidation resulting in increased deposits.
DIG technology promises about a third less carbon dioxide emissions than comparable conventional multi-port injection. This is achieved with a 10–15% improvement in fuel consumption when operating in the homogeneous mode, and up to 35% when operating in the lean stratified mode. Fuel economy benefits also translate into fossil energy conservation and savings for the consumer. In addition, the DIG operation platform facilitates up to a 10% power increase for the same fuel burned in the equivalent MPI configuration.
Current generation DIG technologies have experienced deposit problems. Areas of concern include fuel rails, injectors, combustion chamber (CCD), crankcase soot loadings, and intake valves (IVD).
Fuel related deposits in DIG engines are an issue of current interest since this technology is now commercial in Japan and Europe. Fuel injector performance is at the forefront of this issue because the DIG combustion system relies heavily on fuel spray consistency to realize its advantages in fuel economy and power, and to minimize exhaust emissions. A consistent spray pattern enables more precise electronic control of the combustion event and the exhaust after-treatment system.
There is a desire in the petroleum industry to produce a fuel suitable for use in both MPI and DIG engines, that is a fuel having effective IVD control for a MPI engine as well as a fuel having effective injector deposit control suitable for a DIG engine. Additives useful in reducing or controlling intake valve deposits in a MPI engine may have little or no effect or even an adverse effect in controlling or reducing injector deposits in a DIG engine. Likewise, additives useful in controlling or reducing injector deposits in a DIG engine may have little or no effect or even an adverse effect in controlling or reducing intake valve deposits in a MPI engine. An object of the present invention is to provide fuel compositions that provide effective injector deposit control in DIG engines as well as providing fuel compositions which provide effective deposit control in both MPI and DIG engines.
There are references teaching fuel compositions containing amines and amine derivatives compounds, for example, U.S. Pat. Nos. 5,643,951; 5,725,612 and 6,176,886. However, none of these references teach the use of fuel compositions containing the amine compounds and derivatives of the present invention in direct injection gasoline engines or the impact such compounds have on deposits in these engines.

Fuels compositions for direct injection gasoline engines

Abstract: wherein R1 and R2 are independently C1-4 alkyl, R3 is a radical of the formula CmH2m wherein m is an integer of 2 to 6, R4 and R5 are each independently (i) hydrogen (ii) C1-4 alkyl,

Abstract: wherein R6 is selected from the group consisting of hydrogen and C1-4 alkyls and R7 is selected from the group consisting of hydrogen and C1-30 alkyl, (iv)

Abstract: wherein R8 is a saturated or unsaturated, linear, branched or cyclic, C7-23 hydrocarbyl group or (v) wherein R4 and R5 together with the nitrogen atom to which they are bonded, form a cyclic ring in which further hetero atoms.


A universal garbage pick-up tool includes a main body, an inner support tube, at least two guard members positioned between the main body and inner support tube, a pushing rod positioned within the inner support tube, a push button operatively connected to a proximal end of each guard member and a proximal end of the pushing rod, and a plurality of spring claws attached to a distal end of the pushing rod. The spring claws are positioned within the inner support tube, and the guard members and the spring claws are released upon the actuation of the push button, thereby allowing the spring claws to extend axially from a distal end of the main body. An adjustment ring may be attached to the distal end of the main body, including at least two pins circumferentially spaced apart. A magnet may be positioned within the push button of the pick-up tool.

1. Field of the Invention
This disclosure relates generally to a universal pick-up tool and, more particularly, to a universal garbage pick-up tool with multiple methods for grasping and releasing garbage and other materials.
2. Description of Related Art
Pick-up tools used in industrial, custodial, and/or household environments are well known and various in design. However, despite the increasing needs of the individuals using these pick-up tools and advances in pick-up tool configurations, the ease of use and the lack of methods for picking up materials has been a continuing problem.
Currently known pick-up tools include a main body, an actuating handle, and pincers for picking up and depositing hard-to-reach objects either stored on a high surface or left on the ground. Particularly, in the custodial environment, individuals spend a significant amount of time picking up refuse and/or small objects that have fallen to the ground. Quite often these pick-up tools are non-adjustable and are too short for the individual, so that they must bend over to pick up any objects, or these pick-up tools require a constant pressure to be applied to the handle to keep the object restrained in the pincers of the pick-up tool. Most of these pick-up tools are designed to pick up objects from two sides, which makes it difficult to grab flat and small objects. These problems can lead to back problems for the individuals or multiple attempts at picking up an object when moving it to a different location, such as a waste bin or garbage bag.
Another problem with current pick-up tools is the lack of methods available for an individual to pick up materials of different size, weight, and material. Current pick-up tools include a single pair of pincers, or a gripper used to grab objects from high or unreachable places. These pincers can often be unwieldy and difficult to maneuver because they are designed to pick up larger objects such as cans or boxes. However, it is difficult to pick up flat and small objects such as paper, cardboard, or metal objects without some difficulty in using the pincers of the pick-up tool. Additionally, most current pick-up tools fail to include more than one option for picking up objects. Often the pick-up tool will only include a pair of pincers, or only a magnet for picking up metal objects, or only a rod for the stabbing of different objects.


Methods and systems are provided for positioning a remote sensor within a target object. An articulated robotic system is coupled to the remote sensor. A positioning system determines a position of the target object to be inspected and determines a first position of the remote sensor. A control system calibrates a virtual representation of the target object with respect to the position of the target object, and tracks movement of the remote sensor relative to the target object.

The subject matter described herein relates generally to inspections and more particularly to methods and systems for placement of inspection sensors.
Known aircraft generally undergo routine inspection of various components. Numerous aircraft components typically are inspected, and the equipment used to perform such inspections can vary from component to component depending, for example, on the component type and/or location. Inspecting at least some components may be difficult because of various spatial restrictions. For example, access to at least some components may require disassembly of at least one occluding structure and/or removal of the component prior to inspection. Inspecting such components may be a tedious and time-consuming task.
To facilitate inspection of at least some of such components, articulated robot manipulator arms have been used to position inspection sensors within at least some limited access areas. Such articulated robot manipulator arms facilitate avoiding disassembly of portions of the aircraft in connection with performing inspections. Due to joint and link flexibility and high-degrees of freedom of such robot manipulator arms, accurate, real-time positioning and orientation tracking of such robot manipulator arms can be difficult. Further, positioning errors may build up the further down a chain of articulated segments a location is from a base. As such, the position of the end effector, i.e., the location of an inspection sensor, generally has the largest errors.

Methods and systems for inspection sensor placement


A floor console includes a climate control unit. A bracket of the floor console unit includes an interior surface facing the climate control unit and an exterior surface opposite the interior surface. An armrest is supported by the bracket and is moveable relative to the bracket. A gas spring extending from a first end connected to the armrest to a second end connected to the exterior surface of the bracket. The connection of the second end of the gas spring to the exterior surface of the bracket reduces packaging constraints for the climate control unit on the interior surface of the bracket.

The location or air registers in vehicles may be designed to maximize the effectiveness of the heating/ventilation/air condition (HVAC) of the vehicle and to direct air at a desired area of an occupant's body. A theoretical point in the vehicle that is referred to as the "H-point" may be used to identify the location of the air registers. The H-point is typically identified as the pivot point between the torso and upper legs of an occupant, i.e., through the hips, of a 50% male. As such, an occupant sits relatively higher in a vehicle that is designed to have a relatively high H-point and, conversely, an occupant sits relatively lower in a vehicle that is designed to have a relatively low H-point.
Since the locations of various areas of the occupant's body in the vehicle is dependent on the H-point, the most effective location of the air registers may be designed based on the H-point to provide the registers to be directed at the desired area of the occupant's body. However, the architecture of the vehicle and packaging of various components limits the location of the air registers and may prevent the placement of the air registers in the most effective location.
As one example, the vehicle may include a floor console between the driver seat and the front passenger seat. The floor console may include an armrest that is pivotable between an open position to expose a storage compartment in the floor console and a closed position to cover the storage compartment. The floor console may include an air register facing rearwardly into a rear passenger area of the vehicle. The H-points of the occupants in the rear passenger area may be used to determine the most effective location of the air register. However, the limited area between the driver seat and the front passenger seat, the location and design of the storage compartment, and the location and design of the arm rest are all limiting factors on placement of the air register. As such, there remains an opportunity to design a floor console that allows for effective placement of the air register.


A method of deciding the quality of a measurement value of the line width, the line interval or the like of a pattern on an object to-be-measured, including acquiring the signal intensity distribution of the pattern on the object to-be-measured, detecting the edge positions of the pattern from the acquired signal intensity distribution, detecting the taper widths of the edge parts of the pattern from the acquired signal intensity distribution, and deciding that the measurement value calculated on the basis of the detected edge positions is correct, when the detected taper widths fall within a predetermined range set beforehand. In this way, it is permitted to automatically decide the defective measurement of the line width of the pattern, or the like, attributed to an unclear image due to inferior focusing in an image photographing mode, an unclear image due to an image drift ascribable to charging-up, or the like.

1. Field of the Invention
The present invention relates to a method of deciding a measurement value, and, more particularly, for deciding the quality of the measurement value obtained by measuring the line width, the line interval or the like of a pattern on an object to-be-measured.
2. Description of the Related Art
Heretofore, an automatic measurement, which is performed with a SEM (scanning electron microscope) for the line width, the line interval or the like of a microscopic pattern that is formed on a mask for transferring the microscopic pattern onto a wafer, has sometimes turned out a failure from various causes. The "failure" termed here signifies that, although a numerical value being the result of the measurement is obtained, the value is incorrect by any cause. In the automatic measurement in the absence of an operator, it is often the case that the cause cannot be easily grasped. This situation occurs for reasons as stated below.
(1) Since the measurement value itself exhibits a variance, a correct value is not fixed.
(2) The measurement value sometimes deviates widely due to the failure of autofocusing in the SEM by any cause, or due to the deviation of an image attributed to charging-up. In some cases, the correct value is obtained by trying the autofocusing again.
(3) A pattern dimension sometimes deviates more than is expected. This dimension is correct as the measurement, and ought to be marked as an abnormal place.
It is required of an automatic measurement apparatus to automatically discriminate these reasons and perform appropriate processing.
An object to be measured here is-a length (width) which is measured along a certain direction (for example, X-direction or Y-direction) in a certain place of the pattern. The pattern is based on a line which has a finite width (including also the interval between lines, and termed "line" or "space"), and a rectangle which occupies a finite area (usually termed "contact hole" or "dot" in the pertinent technical field). In a case where the pattern has a complicated shape, the length (width) to be measured becomes the width of the pattern along a specified line. In case of the contact hole, it is also included to measure the area.
A signal intensity distribution along a designated direction is extracted from the SEM image of the pattern to-be-measured, and both the end edges of the pattern are detected from the signal intensity distribution, so as to calculate the width.
There are several methods for determining the positions of the edges on this occasion.
(1) Threshold value method: In a case where the intensity distribution in the vicinity of each edge is normalized and where the width between the minimum and the maximum is set at 1 (one), the point of an intensity having a threshold value x (1.0≧x≧0) is set as the edge position.
(2) Linear regression method: Regression lines are respectively obtained in a partial intensity distribution near the edge and in a partial intensity distribution near the minimum point, and the intersection point between the regression lines is set as the edge position.
(3) Peak method: A line width is calculated with tentative edges being the peak positions of intensity distributions in the vicinity of the edges, and it is corrected by calibration.
(4) Other (combination): An edge intensity distribution is subjected to a function approximation, and the edge position is determined in combination with the threshold method.
Whether or not the dimension measured by any of the above methods (1) through (3) is correct, has hitherto been decided by either of methods stated below.
(a) A person observes the image of the object to-be-measured, and decides whether or not the measurement proceeded correctly. (Automation is impossible.)
(b) A certain range of measurement values as centers round an expected dimension is set, and any measurement value outside the range is regarded as the failure of the measurement. (Automation is possible.)
Here, the method (a) has had the problems that the automation is impossible, and that individual differences ascribable to the deciders cannot be excluded.
On the other hand, in case of the method (b), the automation is possible, and the predetermined criterion is applied, so that objective data are obtained. This method, however, has had the problem that the simple setting of the range cannot cope with the variance of the object to-be-measured, a systematic change such as process bias, or the like.

Method of deciding the quality of the measurement value by the edge width


A dispensing closure system is provided with two or more dispensing apertures and two or more pivotable lids. Each lid can be selectively opened and retained in a fully opened orientation. In a preferred form of the invention, the lids are incorporated in a top that is snap-fitted into a closure body which defines the dispensing apertures.

There are a variety of types of conventional dispensing closures. One type of prior art dispensing closure system includes a body or base for being attached to the top of a container. The body defines a dispensing opening. The system further includes a lid which is hingedly mounted on the body and which can be lifted up to open the dispensing opening.
Dispensing closures are typically used for dispensing a fluent product from a container. With some types of fluent products, and in some applications, it may be desirable to have the body dispensing opening be substantially unobstructed around most, if not all, of the periphery when the lid is open. It is desirable for the lid to be held as far open as possible so that the lid does not hang down and interfere with the fluent product dispensing process. For example, when dispensing mustard or other fluent condiments from a container through the dispensing opening of a dispensing closure, the user does not want the open lid to contact the discharging product or contact the target area, such as a plate or food item onto which the fluent product is being dispensed.
It would be desirable to provide an improved system for maintaining a lid in an open position during the dispensing product. Further, in some applications, it may be desirable to provide a dispensing closure with multiple dispensing openings having different configurations for selectively dispensing discharge streams having different sizes or configurations. Preferably, if each separate dispensing opening has its own separate lid, a desired dispensing opening can be selected and opened by opening the associated lid while the remaining dispensing openings can remain closed with their own separate lids.
It would be desirable to provide a dispensing closure with multiple dispensing openings and multiple lids that could each be selectively and easily operated between a closed condition and a substantially wide open condition wherein the opened lid is maintained in a substantially wide open condition until the user re-closes the opened lid.
Such a multiple lid closure should accommodate ease of use. Preferably, such an improved multiple lid closure should also permit the area around the dispensing opening to be readily cleaned.
It would also be desirable to provide an improved dispensing closure system which would have components that can be easily manufactured and assembled.
It would also be beneficial if an improved dispensing closure system could readily accommodate its manufacture from a variety of different materials.
It would also be advantageous if such an improved dispensing closure system could accommodate bottles, containers, or packages which have a variety of shapes and which are constructed from a variety of materials.
Further, it would be desirable if such an improved system could accommodate efficient, high-quality, high-speed, large volume manufacturing techniques with a reduced product reject rate to produce products having consistent operating characteristics unit-to-unit with high reliability.

Multiple lid closure with open lid retention feature


Systems and methods for updating a user interface that indicates printing capabilities for a printing device read one or more first printing capabilities from first printing capabilities data, generate a user interface that includes a plurality of interface elements, read one or more second printing capabilities from second printing capabilities data, the one or more second printing capabilities including at least one printing capability different from the one or more first printing capabilities, generate delta printing capabilities data indicating changed printing capabilities based on the one or more first printing capabilities and the one or more second printing capabilities, wherein the delta printing capabilities data includes the at least one printing capability different from the one or more first printing capabilities, and update one or more interface elements associated with the changed printing capabilities indicated by the delta printing capabilities data.

1. Field of the Disclosure
The present disclosure relates generally to updating user interfaces for a printing device.
2. Description of the Related Art
In the field of print processing, it is a challenging task for Independent Software Vendors (also referred to herein as "ISVs") to provide a consistent user interface for receiving a desired print intent from a user while supporting private settings for the printers of multiple Independent Hardware Vendors (also referred to herein as "IHVs"). The communication between the Windows® print sub system, an IHV's plug-in driver, and an ISV's application causes part of the difficulties, because the communication is done thru indexed based binary DevMode and binary DevCaps.
Microsoft® introduced a new XML based print schema to address the problems associated with communication between the print subsystem and external applications. The print schema technology uses an XML based public schema to describe printer capabilities, device configuration, and job formatting settings. Applications can use the XML based schema to provide print dialogs to change print settings. Whenever a user changes a selected option for a setting, the changed setting and the respective option is added to a delta (also referred to herein as "Δ") PrintTicket and merged and validated with a specified base PrintTicket to produce a resulting PrintTicket, which is used to get a corresponding resulting PrintCapabilities document. The resulting PrintCapabilities document is then used to re-populate the user interface (also referred to herein as a "UI").

Systems and methods for updating a user interface for a printing device


A method for operating a terminal using reduced power consumption in a mobile communication system is provided. The method includes receiving a signal, determining whether the received signal corresponds to a Session Initiation Protocol (SIP) update request message, if the received signal corresponds to an SIP update request message, sending the SIP update request message to an SIP processor in a communication processor; and handling the SIP update request message by the SIP processor.

1. Field of the Invention
The present invention relates to a mobile communication system. More particularly, the present invention relates to a method and apparatus for consuming low power by a terminal in a mobile communication system.
2. Description of the Related Art
Mobile communication systems have been developed to provide voice services while ensuring the user's activity. However, the mobile communication systems have gradually expanded their respective services from voice services to include data services. At present, the mobile communication systems have evolved to provide high-speed data services. However, mobile communication systems according to the related art suffer from a lack of resources. More advanced wireless communication systems are required to meet the increasing users' demand for high-speed services.
To meet these needs, standardization for a Long Term Evolution (LTE) communication system, one of the next-generation wireless communication systems under development, is underway in 3rd Generation Partnership Project (3GPP). Because the LTE system basically supports only the packet services, the LTE standard has proposed a Circuit Switched FallBack (CSFB) service, in which in order to provide a voice call to a user, upon receiving an incoming voice call, a terminal camping on an LTE network drops its connection to the LTE network, and accesses the legacy 3rd Generation (3G) network (or Circuit Switched (CS) network) to provide a voice call service. In addition to CSFB, the LTE standard has proposed a Voice over LTE (VoLTE) service as technology for supporting a voice call service in the LTE network. According to the VoLTE service, a terminal converts the user's voice into packet data and transmits the packet data across the LTE network.
As the LTE system applies the voice call service that uses the legacy 3G CS network, to the Packet Switched (PS) data network, a protocol for voice call control between a terminal and the network is required. To this end, a Session Initiation Protocol (SIP) protocol is used. The SIP protocol provides multiple functions, such as a message delivery function of sending a call to the other party when a user makes a call, a function of receiving and responding to a call message upon receiving the call message from the other party, a function of accepting, rejecting or dropping the call depending on the user's input, and a function of determining whether the terminal is normally connected to the network.
FIG. 1 illustrates a structure of a terminal according to the related art.
Referring to FIG. 1, the terminal includes an Application Processor (AP) 100, a Session Inter-Process Communication (SIPC) 120, and a Communication Processor (CP) 130. The Session Inter-Process Communication (SIPC) 120 operates for interworking between the AP 100 and the CP 130.
In the terminal, the SIP protocol is implemented in the AP 100.
It is assumed that an SIP message and/or a voice packet are received at the terminal from a network.
Upon receiving a voice packet from the network, a Packet Data Convergence Protocol (PDCP) filter 134 in the CP 130 of the terminal transfers the voice packet to a voice engine 132 via a Transfer Control Protocol/Internet Protocol (TCP/IP) 136 in the CP 130, and the voice engine 132 processes the voice packet, allowing the user to hear the voice.
Upon receiving an SIP message from the network, the PDCP filter 134 in the CP 130 sends the SIP message to an SIP stack 115 in the AP 100, so that an appropriate operation is performed for each message. For example, upon receiving the SIP message from the network, the PDCP filter 134 in the CP 130 may send the SIP message to the SIP stack 115 in the AP 100 by way of the TCP/IP 105 in the AP 100. The AP 100 may include an IMS library 110 comprising the SIP stack 115.
FIG. 2 is a flowchart illustrating an operation of a terminal according to the related art.
Referring to FIG. 2, in step 201, the PDCP filter 134 of the CP 130 included in the terminal receives an SIP message in a situation in which there is no user input. In step 203, the PDCP filter 134 sends the received SIP message to the SIP stack 115 in the AP 100, which is responsible for processing an SIP protocol, even in the situation in which there is no user input. In step 205, the SIP stack 115 in the AP 100 handles the received SIP message.
Because the terminal attempts to ensure the maximum performance and run time within the terminal limitations (e.g., limited size, processing power, and the like), reduction of the power consumption of the terminal is very important. However, because the SIP stack 115 used to control VoLTE voice calls exists in the AP 100, the AP 100 is responsible for generating an SIP message and handling a received SIP message. When the user takes an action of making (sending) or receiving a voice call, the AP 100 is enabled in order to activate a User Interface (UI) of the terminal. Therefore, the terminal does not need to additionally enable the AP 100 when the terminal needs to handle an SIP message.
However, when there is a need to handle an SIP message in a situation in which there is no user input, the terminal should enable the AP 100 in order to handle the SIP message, thereby causing the terminal to consume relatively more power.
Therefore, a need exists for a method and apparatus for consuming low power by a terminal, in which when there is a need to process an Session Initiation Protocol (SIP) protocol in a situation in which there is no user input.
The above information is presented as background information only to assist with an understanding of the present disclosure. No determination has been made, and no assertion is made, as to whether any of the above might be applicable as prior art with regard to the present invention.

Method and apparatus for consuming low power by terminal in mobile communication system


A switching power circuit having a power factor improving circuit for a composite resonance type converter, wherein a switching pulse is fed back from a tertiary winding, which is coiled around an insulating converter transformer, via a series resonance capacitor. And a rectified current is turned on and off by a fast recovery diode in accordance with the feedback output, hence achieving power factor improvement. In this structure, a smoothing capacitor is charged with the resonance current even during an off-period of the fast recovery diode due to the resonance of a series resonance circuit including the series resonance capacitor. This circuit configuration eliminates the necessity of selection of a higher withstand voltage relative to the primary-side smoothing capacitor by suppressing rise of the DC input voltage in a no-load state.

The present invention relates to a switching power circuit equipped with a power factor improving circuit.
Previously to date the present applicant proposed a variety of power circuits each having a resonance type converter on its primary side, and also other various power circuits each having a power factor improving circuit to achieve improvement of the power factor for a resonance type converter.
FIG. 6 is a circuit diagram showing an exemplary switching power circuit of a configuration based on the invention filed previously by the present applicant. This power circuit is equipped with a power factor improving circuit to attain improvement of the power factor for a self-excited voltage resonance type switching converter.
In the switching power circuit shown in this diagram, there are provided a common mode choke coil CMC and an across capacitor CL which constitute a noise filter to remove the common mode noise with regard to an alternating current power AC.
The alternating current power AC is full-wave rectified by a bridge rectifier circuit Di consisting of four diodes, and the rectified output is supplied to charge a smoothing capacitor Ci via a power factor improving circuit 20. The circuit configuration of the power factor improving circuit 20 and the operation thereof will be described later.
In this diagram, the voltage resonance type switching converter has a switching element Q1 consisting, for example, of a high-voltage withstanding bipolar transistor. That is, this switching converter is in a single end form.
The base of the switching element Q1 is connected to the positive side of the smoothing capacitor Ci via a starting resistor RS, so that a base current at the start is obtained from a rectifier smoothing line. The base of the switching element Q1 is connected also to a switching drive circuit 2.
The switching drive circuit 2 consists of a self-excited oscillation driver for driving the switching element Q1 by self-excitation, and a switching frequency controller for stabilizing the voltage by varying the oscillation frequency (i.e., switching frequency) in the self-excited oscillation driver.
In a specific configuration of such switching drive circuit 2, as seen in the various power circuits proposed previously by the present applicant, the self-excited oscillation driver consists, for example, of a resonance circuit composed of a driving coil and a resonance capacitor, and a detection coil for transferring the alternating voltage to the driving coil. Although not shown here, the detection coil is connected practically in series to a primary winding N1 for example. That is, the switching element Q1 is driven through switching by the resonance output of the resonance circuit in the self-excited oscillation driver, and the resonance frequency thereof is used as a switching frequency.
The switching frequency controller has a structure adapted to vary the resonance frequency. For this purpose, a control transformer PRT is provided to vary the inductance of the driving coil for example. In this control transformer PRT, the driving coil and the detection coil for example are transformer-coupled to each other, and a control coil is wound in such a manner that the winding direction thereof is not coincident with that of the driving coil and the detection coil. A DC control current outputted from the control circuit 1 is supplied to the control coil.
In the control circuit 1, a control current of a level corresponding to a secondary side DC output voltage Eo is supplied to the control coil. In the control transformer PRT, the inductance of the driving coil is varied in accordance with the level of the control current flowing in the control coil. As the inductance of the driving coil is thus varied, the resonance frequency of the self-excited oscillation driver, i.e., the switching frequency, is also varied under control.
A detailed description will be given later on a constant voltage regulating action executed with such switching frequency control.
The collector of the switching element Q1 is connected to the positive terminal of the smoothing capacitor Ci via the primary winding N1 of the insulating converter transformer PIT, and the emitter thereof is grounded.
In this case, a clamp diode DD is connected between the collector and emitter of the switching element Q1, thereby forming a path where a damper current flows at the off-time of the switching element Q1.
A first resonance capacitor Cr constitutes a parallel resonance circuit in combination with a second resonance capacitor Cr1 in an undermentioned power factor improving circuit 2 and principally with the leakage inductance of the primary winding N1 of the insulating converter transformer PIT. Due to the action of this parallel resonance circuit, the switching operation of the switching element Q1 is performed in a voltage resonance mode. And the end voltage VCP between the collector and emitter of the switching element Q1 is obtained in a waveform of sinusoidal pulses during the off-period of the switching element.
The insulating converter transformer PIT transfers the switching output of the switching element Q1 to the secondary side.
As shown in FIG. 12, the insulating converter transformer PIT has an EE-shaped core where E-shaped cores CR1 and CR2 composed of ferrite for example are combined with each other in such a manner that magnetic legs thereof are opposed mutually, and the primary windings N1 and the secondary windings N2 thereof are coiled in a split state respectively by the use of a split bobbin B with regard to the center magnetic leg of the EE-shaped core. And a gap G is formed to the center magnetic leg as shown in the diagram, whereby loose coupling is attained with a required coupling coefficient.
The gap G can be formed by shaping the center magnetic leg of each of the E-shaped cores CR1 and CR2 to be shorter than the two outer magnetic legs thereof. The coupling coefficient k is set as, e.g., k≈0.85 suited to attain loose coupling, hence avoiding a saturated state correspondingly thereto.
One end of the primary winding N1 of the insulating converter transformer PIT is connected to the collector of the switching element Q1, while the other end thereof is connected to the positive side (rectified smoothed voltage Ei) of the smoothing capacitor Ci.
On the secondary side of the insulating converter transformer PIT, an alternating voltage induced by the primary winding N1 is generated in the secondary winding N2. In this case, since a secondary side parallel resonance capacitor C2 is connected to the secondary winding N2, a parallel resonance circuit is formed by the leakage inductance L2 of the secondary winding N2 and the capacitance of the secondary side parallel resonance capacitor C2. The alternating voltage thus produced in the secondary winding N2 is turned into a resonance voltage in the parallel resonance circuit. That is, a voltage resonance operation is performed on the secondary side.
More specifically, this power circuit has, on its primary side, a parallel resonance circuit to execute the switching operation in a voltage resonance mode, and also has, on its secondary side, another parallel resonance circuit to perform a voltage resonance operation in the rectifier circuit. In this specification, the switching converter of a configuration equipped with resonance circuits on its primary and secondary sides as mentioned above will be referred to as xe2x80x9ccomposite resonance type switching converterxe2x80x9d.
In the secondary side parallel resonance circuit formed as described, a center tap is provided for the secondary winding N2, and there is also provided a half-wave rectifier circuit consisting of a rectifier diode D0 and a smoothing capacitor Co. This half-wave rectifier circuit receives an input resonance voltage supplied from the secondary side parallel resonance circuit and delivers a DC output voltage Eo therefrom.
In the insulating converter transformer PIT, the mutual inductance M regarding the inductance L1 of the primary winding N1 and the inductance L2 of the secondary winding N2 becomes either +M or xe2x88x92M depending on the relation of the polarities (winding directions) of the primary winding N1 and the secondary winding N2 to the connection of the rectifier diode D0.
For example, if the connection is in a state of FIG. 13A, the mutual inductance becomes +M (forward mode). Meanwhile, if the connection is in a state of FIG. 13B, the mutual inductance becomes xe2x88x92M (flyback mode).
Applying the above to the secondary side operation of the power circuit shown in FIG. 6, when the alternating voltage obtained in the secondary winding N2 is positive for example, it is supposed that the operation with the rectified current flowing in the rectifier diode D0 is performed in the +M (forward) mode. That is, in the power circuit of FIG. 6, the mutual inductance functions in the +M (forward) mode every time the alternating voltage obtained in the secondary winding is turned to positive/negative.
In this configuration, the power is supplied to the load increased by the action of the secondary side parallel resonance circuit, so that the power supplied to the load is also increased correspondingly thereto to consequently enhance the increase rate of the maximum load power.
Such correspondence to the load condition can be realized due to the improved situation where a saturated state is not reached readily because of the loose coupling attained by a required coupling coefficient with the gap G formed in the insulating converter transformer PIT, as explained previously with reference to FIG. 12. For example, in case the gap G is not existent in the insulating converter transformer PIT, the operation will be abnormal with a high probability as the insulating converter transformer PIT is placed in its saturated state during the flyback, whereby proper execution of the rectification is rendered considerably difficult.
In the circuit of FIG. 6 where the switching frequency is varied for constant voltage control, the switching frequency variation is executed under control to vary the on-time of the switching element Q1 while maintaining the off-time thereof fixed. That is, in this power circuit, the constant voltage control is performed to vary the switching frequency under control to thereby control the resonance impedance with regard to the switching output, and simultaneously the conduction angle control (PWM control) of the switching element in the switching period is also performed. Such composite control operation is realized in a single set of control circuitry.
In executing such switching frequency control, when the secondary side output voltage is increased due to a trend of reduction of the load for example, the secondary side output is suppressed under control by raising the switching frequency.
The power factor is improved by the power factor improving circuit 20.
As shown in this diagram, the power factor improving circuit 20 has a series connected circuit of a choke coil Ls and a fast recovery diode D2 inserted between the positive output of a bridge rectifier circuit Di and the positive terminal of a smoothing capacitor Ci. The anode of the fast recovery diode D2 is connected to the choke coil Ls, while the cathode thereof is connected to the positive terminal of the smoothing capacitor Ci. The choke coil Ls functions as a load of the switching output fed back as will be described later.
And a filter capacitor CN is connected in parallel to the series connection of the choke coil Ls and the fact recovery diode D2. In this circuit, the choke coil Ls and the filter capacitor CN constitute a normal-mode LC low pass filter which prevents inflow of any switching high-frequency noise into the AC line.
The junction (voltage division point) in the aforementioned series connection of the first parallel resonance capacitor Cr and the second parallel resonance capacitor Cr1 is connected to the junction of the choke coil Ls and the fast recovery diode D2.
It is supposed here that the respective values are selectively set as the first parallel resonance capacitor Cr=8200 pF, second parallel resonance capacitor Cr1=0.027 xcexcF, choke coil Ls=75 xcexcH, and filter capacitor CN=1 xcexcF.
In the power factor improving circuit 20 of such a connected circuit configuration, a resonance pulse voltage Vcp obtained at the off-time during the switching operation of the switching element Q1 is divided by the series connection of the first parallel resonance capacitor Cr and the second parallel resonance capacitor Cr1, and then the divided voltage is impressed in such a manner as to be fed back to the junction of the choke coil Ls and the fast recovery diode D2.
When the resonance pulse voltage Vcp is 600 Vp for example, a voltage of approximately 150 vp obtained through voltage division at 3:1 or so is fed back to the junction of the choke coil Ls and the fast recovery diode D2.
At the timing when the alternating input voltage VAC reaches the vicinity of its positive or negative peak, the fast recovery diode D2 is turned on. At this time, a pulse current having a steep rise waveform comes to flow from the output terminal of the bridge rectifier circuit Di into the smoothing capacitor Ci to charge the same via the choke coil Ls and the fast recovery diode D2.
Meanwhile, in any other period than when the alternating input voltage VAC reaches the vicinity of its positive or negative peak, the fast recovery diode D2 repeats its switching operation in accordance with the resonance pulse voltage fed back as voltage V2, as mentioned. And at the timing when the fast recovery diode D2 is turned off during the switching operation, a parallel resonance current flows in a circuit consisting of the second parallel resonance capacitor Cr1, the choke coil Ls and the filter capacitor CN. Meanwhile, at the timing when the fast recovery diode D2 is turned on, a high-frequency charge current flows in the smoothing capacitor Ci from the alternating input voltage VAC via the choke coil Ls.
In this manner, utilizing the primary side voltage resonance pulse fed back to the rectified current path, the current to be caused to flow in the rectified current path is converted into a high-frequency current to attain an alternating action, hence widening the conduction angle of the alternating input current IAC to consequently improve the power factor.
FIG. 7 graphically shows characteristics of the power circuit having the configuration of FIG. 6, including changes of the power factor derived from load variations and also changes of the DC input voltage (rectified smoothed voltage Ei). This diagram represents a comparison between the characteristics (solid line) of the circuit equipped with the power factor improving circuit 20 of FIG. 6 and the characteristics of another circuit which is not equipped with the power factor improving circuit 20 of FIG. 6.
According to this graphic diagram, it is obvious that, in a range of the load power Po from 0 W to 200 W, the power factor PF is improved more in the circuit configuration with the power factor improving circuit 20 of FIG. 6 than in another circuit configuration without the power factor improving circuit. Particularly in the circuit shown in FIG. 6, there is attained such characteristic that the power factor indicates its peak value when the load power Po is 50 W or so.
It is also seen that the level of the rectified smoothed voltage Ei tends to become higher in accordance with reduction of the load power Po.
FIG. 8 graphically shows change characteristics of the power factor relative to variations of the alternating input voltage VAC and the DC input voltage (rectified smoothed voltage Ei). This diagram also represents a comparison between the characteristics (solid line) of the circuit equipped with the power factor improving circuit 20 of FIG. 6 and the characteristics of another circuit which is not equipped with the power factor improving circuit 20 of FIG. 6.
As shown in this diagram, the characteristic obtained is such that the power factor is lowered in the circuit configuration where none of power factor improvement is performed in accordance with a rise of the alternating input voltage VAC in a range of 80 V to 140 V, while the power factor PF can be enhanced in the circuit of FIG. 6, where the power factor PF is increased with a rise of the alternating input voltage VAC.
There is further achieved such characteristic that the rectified smoothed voltage Ei is raised with a rise of the alternating input voltage VAC.
FIG. 9 shows another example of a switching power circuit constituted on the basis of the invention proposed previously by the present applicant. In this power circuit also, a power factor improving circuit is included to achieve power factor improvement for a self-excited voltage resonance type switching converter. In this diagram, any component parts equivalent to those in FIG. 6 are denoted by the same reference numerals, and a repeated explanation thereof is omitted.
The power circuit shown in this diagram is equipped with a power factor improving circuit 21. In comparison with the aforementioned power factor improving circuit 20 of FIG. 6, this power factor improving circuit 21 is different in the point that the fast recovery diode D2 and the choke coil Ls therein are connected reversely. That is, the anode of the fast recovery diode D2 is connected to the positive output terminal of the bridge rectifier circuit Di, and the cathode thereof is connected to one end of the choke coil Ls. Meanwhile the other end of the choke coil Ls is connected to the positive terminal of the smoothing capacitor Ci. And resonance pulses voltage Vcp, which are obtained through voltage division by a first parallel resonance capacitor Cr and a second parallel resonance capacitor Cr1, are impressed to the junction of the fast recovery diode D2 and the choke coil Ls.
In such circuit configuration also, the fast recovery diode D2 is turned on at the timing when the alternating input voltage VAC reaches the vicinity of its positive or negative peak, and a pulse current having a steep rise waveform comes to flow from the output terminal of the bridge rectifier circuit Di into the smoothing capacitor Ci to charge the same via the fast recovery diode 2 and the choke coil Ls.
In this case, the fast recovery diode D2 is temporarily turned off when the absolute value of the alternating input voltage VAC has lowered to a certain level, and voltage resonance is induced at this time by a parallel resonance circuit consisting of the second parallel resonance capacitor Cr1 and the choke coil Ls. Due to such voltage resonance, a sine-wave pulse voltage is superposed on the cathode potential V2 (divided resonance pulse voltage) of the fast recovery diode D2. Subsequently the fast recovery diode D2 repeats its switching operation in response to the potential difference between the cathode potential V2 and the anode potential V1 of the fast recovery diode D2. And a charge current is caused to flow from the filter capacitor CN into the smoothing capacitor Ci during the on-time of the fast recovery diode D2 in such switching operation. This performance extends the conduction angle of the alternating input current IAC to thereby improve the power factor.
FIG. 10 graphically shows characteristics of the power circuit having the configuration of FIG. 9, including changes of the power factor derived from load variations and also changes of the DC input voltage (rectified smoothed voltage Ei). And FIG. 11 graphically shows change characteristics of the power factor relative to variations of the alternating input voltage and the DC input voltage (rectified smoothed voltage Ei). In view of a description to be given later, these diagrams represent the characteristics in one case where the constant of the second parallel resonance capacitor Cr1 is set to 0.033 xcexcF and in another case where the constant is set to 0.043 xcexcF.
First, as seen from FIG. 10, the power factor PF can be kept over 0.70 when the load power Po is substantially within a practical range of 50 W to 200 W. Regarding the rectified smoothed voltage Ei, the result obtained indicates that the voltage Ei tends to rise in accordance with reduction of the load power Po.
And according to the characteristics shown in FIG. 11, it is seen that the power factor PF can be kept over 0.7 with respect to variations of the alternating input voltage VAC ranging from 80 V to 140 V, and the rectified smoothed voltage Ei rises in accordance with rise of the alternating input voltage VAC.
Although the power factor PF can thus be enhanced by the provision of such power factor improving circuit 20 or 21 as shown in FIG. 6 or 9, it is known that the ripple component superposed on the DC input voltage (rectified smoothed voltage Ei) is increased due to the circuit configuration of the power factor improving circuit 20 or 21 where the switching output is fed back to the rectified current path.
In the circuit of FIG. 6 for example, the ripple component xcex94Ei of 9.2 V, which is superposed on the rectified smoothed voltage Ei in the configuration without the power factor improving circuit 20, increases to 35.3 V in the configuration equipped with the power factor improving circuit 20. Particularly in a no-load state, the ripple component xcex94Ei rises to 26 V or so.
The same result is attainable also in the power circuit of the configuration shown in FIG. 9.
Supposing now that, in the configuration of FIG. 9 for example, the respective values are selectively set as the first parallel resonance capacitor Cr=8200 pF, the second parallel resonance capacitor Cr1=0.027 xcexcF and the choke coil Ls=75 xcexcH, then the power factor PF can be kept over 0.73 with the load power Po ranging from 25 W to 200 W, but the ripple component xcex94Ei increases to 31.8 V.
In the circuit of FIG. 9, if the value of the second parallel resonance capacitor Cr1 is set to 0.033 xcexcF or 0.043 xcexcF for changing the voltage division ratio of the first parallel resonance capacitor Cr and the second parallel resonance capacitor Cr1 to adjust (reduce) the feedback quantity of the voltage resonance pulses, then ripple component xcex94Ei decreases to 25.3 V in the case of Cr1=0.033 xcexcF, or further decreases to 9.1 V in the case of Cr1=0.043 xcexcF.
Thus, it is possible to suppress the ripple component xcex94Ei by reducing the feedback quantity of the voltage resonance pulses. However, if the feedback quantity of the voltage resonance pulses is reduced, the power factor PF is lowered. For example, such characteristic is shown in FIGS. 10 and 11 as well, wherein a higher power factor is obtained in the case of Cr1=0.043 xcexcF than in the case of Cr1=0.033 xcexcF. Therefore, in the circuit of FIG. 9 for example, adjustment is so executed as to suppress the ripple component xcex94Ei and to obtain a practically satisfactory power factor PF with a limit of Cr1=0.043 xcexcF or so. The same may be said with regard to the circuit of FIG. 6 also.
In the circuits of FIGS. 6 and 9, the level of the DC input voltage (rectified smoothed voltage Ei) rises with reduction of the load power Po as shown in FIGS. 7 and 10 respectively, and its rise rate becomes high since the ripple component xcex94Ei increases particularly in accordance with approach to the no-load condition. This signifies an increase of the voltage variation rate in relation to any load variation.
Therefore, in an AC 100 V system, the required withstand voltage of the smoothing capacitor Ci for generating a DC input voltage is 200 V in a case without power factor improvement, but it needs to be 250 V in a configuration to execute power factor improvement. Further in an AC 200 V system, the required withstand voltage is 400 V in a case without power factor improvement, but it needs to be 500 V in a configuration to execute power factor improvement.
As a result, there exists a problem that the smoothing capacitor Ci is rendered dimensionally larger to eventually fail in downsizing the circuit and curtailing the production cost.
The smoothing capacitor Ci consists of an electrolytic capacitor for example, and if the selected withstand voltage of the electrolytic capacitor employed here has a higher value while the capacitance thereof is left unchanged, then its equivalent internal resistance increases to eventually increase also the amount of the self-generated heat. Therefore, the deterioration degree of the electrolytic capacitor due to its secular change becomes greater to consequently lower the reliability correspondingly thereto.
The present invention has been accomplished in view of the problems mentioned above.
According to the one aspect of the present invention, there is provided a switching power circuit comprises rectifying and smoothing means for generating a rectified smoothed voltage out of an input commercial AC power and outputting the same as a DC input voltage; an insulating converter transformer having a gap to obtain a required coupling coefficient for loose coupling and serving to transfer a primary output to a secondary side; switching means for outputting, to the primary winding of the insulating converter transformer, the switching output obtained through on/off control of the DC input voltage by a switching element; and a primary side parallel resonance circuit for actuating the switching means in a voltage resonance mode, wherein the resonance circuit consists at least of a leakage inductance component including the primary winding of the insulating converter transformer, and a capacitance of a parallel resonance capacitor.
The switching power circuit also comprises power factor improving means to improve a power factor by feeding back the switching output, which is obtained in the primary winding, to a rectified current path.
The switching power circuit further comprises a secondary side resonance circuit formed on the secondary side and consisting of a leakage inductance component of the secondary winding of the insulating converter transformer and a capacitance of a secondary side resonance capacitor; DC output voltage generating means formed inclusive of the secondary side resonance circuit and rectifying the input alternating voltage obtained from the secondary winding of the insulating converter transformer, thereby generating a secondary side DC output voltage; and constant voltage control means for executing constant voltage control of the secondary side DC output voltage in accordance with the level of the secondary side DC output voltage.
The power factor improving means consists at least of a tertiary winding coiled for the insulating converter transformer in such a manner as to wind up the primary winding; a resonance capacitor inserted for feeding back, to the rectified current path via the capacitance thereof, the switching output transferred from the primary winding to the tertiary winding; a switching element inserted in the rectified current path to execute a switching operation in accordance with the switching output fed back to the current path; and an inductor inserted in the rectified current path.
According to the configuration described above, the power factor improving circuit, which is included in the power circuit termed a composite resonance type converter, transfers to the tertiary winding the switching output obtained in the primary winding of the insulating converter transformer, and then feeds back the switching output from the tertiary winding to the rectified current path via the resonance capacitor. In this configuration, the switching output transferred via the tertiary winding serves to produce a period during which the resonance circuit composed of the resonance capacitor and the inductor in the power factor improving means performs its resonance operation.
The above and other features and advantages of the present invention will become apparent from the following description which will be given with reference to the illustrative accompanying drawings.

Power factor improving switching circuit


Distributed maximum power point tracking systems, structures, and processes are provided for power generation structures, such as for but not limited to a solar panel arrays. In an exemplary solar panel string structure, distributed maximum power point tracking (DMPPT) modules are provided, such as integrated into or retrofitted for each solar panel. The DMPPT modules provide panel level control for startup, operation, monitoring, and shutdown, and further provide flexible design and operation for strings of multiple panels. The strings are typically linked in parallel to a combiner box, and then toward and enhanced inverter module, which is typically connected to a power grid. Enhanced inverters are controllable either locally or remotely, wherein system status is readily determined, and operation of one or more sections of the system are readily controlled. The system provides increased operation time, and increased power production and efficiency, over a wide range of operating conditions.

Solar power is a clean renewable energy resource, and is becoming increasingly important for the future of this planet. Energy from the Sun is converted to electrical energy via the photoelectric effect using many photovoltaic cells in a photovoltaic (PV) panel. Power from a PV panel is direct current (DC), while modern utility grids require alternating current (AC) power. The DC power from the PV panel must be converted to AC power, of a suitable quality, and injected into the grid. A solar inverter accomplishes this task.
It would be advantageous to provide a structure, system and process to improve the efficiency of power inverters, such as for a solar panel system. Such a development would provide a significant technical advance.
To maximize the amount of power harvested, most solar inverters perform a maximum power point tracking (MPPT) algorithm. These algorithms treat an entire array of PV panels as a single entity, averaging all of the PV panels together, with a preference towards the weakest link.
It would therefore also be advantageous to provide a structure, system and process, to maximize efficiency and harvest capabilities of any solar PV system, to capitalize on profit and maximum return for the owner of the system.
Three specific examples of DC energy sources that currently have a role in distributed generation and sustainable energy systems are photovoltaic (PV) panels, fuel cell stacks, and batteries of various chemistries. These DC energy sources are all series and parallel connections of basic "cells". These cells all operate at a low DC voltage, ranging from less than a volt (for a PV cell) to three or four volts (for a Li-Ion cell). These low voltages do not interface well to existing higher power systems, so the cells are series connected, to create modules with higher terminal voltages. Paralleled modules then supply increased power levels to an inverter, for conversion to AC power.
These long strings of cells bring with them many complications. While the current exemplary discussion is focused on PV Panels, other power systems and devices are often similarly implemented for other sources of DC power.
A problem occurs when even a single cell in a PV array is shaded or obscured. The photocurrent generated in a shaded cell may drop to around 23.2% of the other cells. The shaded cell is reverse biased by the remaining cells in the string, while current continues to flow through the shaded cell, causing large localized power dissipation. This power is converted to heat, which in turn lowers the panel's output power capability. Bypass diodes, generally placed in parallel around each 24 cells (which may vary between manufacturers), limit the reverse bias voltage and hence the power dissipation in the shaded cell, to that generated by the surrounding half panel. However, all the power from that sub-string is lost, while current flows in the bypass diode. As well, the bypass diode wastes power from the entire string current, which flows through the panel. The output voltage of the entire string is also negatively affected, causing an even larger imbalance in the system.
Conventional module MPP currents may become unbalanced for other reasons. PV panels in a string are never identical. Because each PV panel in a series string is constrained to conduct the same current as the other PV panels in the string, the least efficient module sets the maximum string current, thereby reducing the overall efficiency of the array to the efficiency of this PV panel. For similar reasons, PV panels in a string are conventionally required to be mounted in the same orientation, and to be of identical size. This is not always possible or desirable, such as for aesthetic or other architectural reasons.
In standard solar array wiring, several series strings of solar panels are wired in parallel to each other to increase power. If there is an imbalance between these paralleled strings, current flows from the higher potential strings to the lower potential strings, instead of flowing to the inverter. Just as it is important to match the cells within a panel, it is also necessary to match the panels in a string, and then to match the strings, for maximum harvest from the solar array. If small fluctuations in environmental conditions occur, it can have a large impact on the system as a whole.
Solar inverters also "average" the entire array when they perform a conventional MPPT function. However, it is not a true average, since there is a preference that leans towards the weakest link in the system. This means that, even though some panels may be capable of supplying 100 percent of their rated power, the system will only harvest a fraction of that power, due to the averaging effect of the algorithm, and the current following through the weaker string, panel, and/or cells.
It would therefore be advantageous to provide a means for applying an algorithm that maximizes the harvest of power from a string, panel, and/or cells. Such an improvement would provide a significant advance to the efficiency and cost effectiveness of power cells structures, processes, and systems.

This patent is subject to a terminal disclaimer.

Distributed maximum power point tracking system, structure and process


The present invention relates to a system and method for customer retention. Historical transaction and customer data may be received from stores. Likewise, recent customer transaction data may be received from the stores. The transactions are linked to each customer. Attriters, historical customers who discontinued shopping, are identified. Next, risk factors for attrition may be identified by examining the attriters' transaction history for commonalities. From the risk factors a loss model may be generated. The loss model may be used, in conjunction with current transaction data, to generate the likelihood of loss for each of the current customers, which may then be reported. Retention measures may be generated for each customer by comparing the customer's transactions to the loss model and the risk factors. The retention measures may be outputted to the stores, and a price optimization system. Likewise, the retention measures may be validated by comparing actual customer loss to the loss model.

The present invention relates to a system and methods for a business tool for determining likelihood of customer attrition, and developing retention stratagems to prevent the customer loss. This business tool may be stand alone, or may be integrated into a pricing optimization system to provide more effective pricing of products. More particularly, the present customer attrition identifier and retainer system may predict a particular customer's likelihood of loss and develop measures which retain the customer before any significant financial loss is experienced from the customer's changing behaviors.
For a business to properly and profitably function there must be relatively constant customer base to ensure a steady revenue stream. For businesses that cater to short-lifespan consumer goods, profitability is only assured when there is repeated customer patronage. Examples of such businesses that rely upon repeated consumer visits include supermarket and food sellers, department stores, movie theaters, most restaurants, and all other "small item" sellers.
To ensure a constant consumer base, businesses may engage in campaigns intended to draw more customers. Additionally, businesses rely upon customer retention and loyalty to maintain existing customers.
It has been traditionally the case that retaining an existing customer is significantly less costly than getting a new customer. In many businesses, this expense discrepancy between getting a new customer and keeping an old customer may be as high as an order of magnitude. Thus, many companies and businesses have attempted to generate the best customer service economically possible, reduce prices and develop a pleasurable shopping experience in order to keep existing customers.
However, such global means of customer retention may not be adequate to retain all customers. All businesses have some level of customer attrition. In the supermarket industry, there may be a loss of roughly 3% to 20% of customers. This loss rate may vary on business locale, type, quality and business model. This customer loss may cost a business dearly over the long term in lost patronage, referrals, and costs associated with generating new customers.
Traditionally, to prevent this customer loss, or attrition, a business simply "tried its best" to ensure good customer relations, and when a disgruntled customer was identified, a manager or similar employee would spend individual attention with the upset customer to appease him, and hopefully maintain that customer's loyalty.
The problem with traditional customer retention practices is that it suffers from diminishing returns. Enhancing customer service greatly above industry standards may result in a reduction in customer loss, for example, from 6% to 4%; however, the costs of a global improvement in customer service may greatly outweigh these gains. Thus, most businesses maintain a level of customer service which optimally balances costs and retention. Further reduction in retention is uneconomical due to diminishing returns of global customer retention measures.
However, the cost of customer retention may be greatly reduced if the business is able to target the customer who is likely to leave. Thus, the upset customer may receive a discount, or "freebie", and enhanced employee attention in order to keep the customer. This level of customer service is uneconomical on a global scale; however, when an upset or disgruntled customer is identified, such more costly retention measures may be economically applied.
Unfortunately for businesses, determining the customers who are likely to leave traditionally required the customer to become upset enough to communicate their displeasure with the business. Alternatively, identification by the business of customers likely to leave has typically relied upon frequency measures of a customer's patronage. While these frequency measures are very accurate, leaving customers are only identified after loss has occurred. At this point, retaining the customer may not be possible.
Were the likelihood of attrition of the customer determinable before loss occurs, more effective retention measures would be able to be imposed.
It is therefore apparent that an urgent need exists for improved customer retention methods. This improved customer retention requires accurately predicting a customer's likelihood of attrition before significant customer loss has occurred. This customer retention system would be able to provide businesses with an advanced competitive tool to greatly reduce customer loss in a cost efficient manner.

Predicting likelihood of customer attrition and retention measures

International Business Machines Corporation


A micro-oscillator in which the dispersion of center frequency, the interference between adjacent oscillator elements and the like are controlled and the resonance characteristic is excellent, and a semiconductor device including the micro-oscillator as well as a communication apparatus using a band-pass filter including the micro-oscillator, are provided. The micro-oscillator includes: a plurality of beam-type first oscillator elements 33 connected in parallel and a non-resonance beam-type second oscillator element 34 arranged between the first oscillator elements 33 adjacent to each other.

1. Field of the Invention
The present invention relates to a micro-oscillator to be an element of a signal filter, mixer, resonator and the like, to a semiconductor device that includes the micro-oscillator, and to a communication apparatus in which a band-pass filter including the micro-oscillator is used.
2. Description of the Related Art
A micro-oscillator made by using the MEMS (Micro Electro Mechanical Systems) technology has been known. Since a micro-oscillator made by using semiconductor processes has such advantages as: an area occupied is small; a high Q value can be obtained; and integration with other semiconductor devices is possible, the micro-oscillator is proposed to be used as a high frequency filter within a radio communication device by the research institutes including the University of Michigan (refer to Non-patent Literature 1).
FIG. 1 shows a schematic view of a micro-oscillator, specifically a beam-type oscillator of electrostatic drive, constituting a high frequency filter described above. This oscillation element 1 includes: an input-side wiring layer 7 and an output electrode 4 which are, for example, made of polycrystalline silicon, formed on a semiconductor substrate 2 through an insulation film 3, and an electrode to be a oscillation plate, that is, a beam 6 formed to face the output electrode 4 separated by a space 5. The beam 6 straddles like a bridge to be connected to the input-side wiring layer 7 such that this beam is supported by anchor portions (support portions) 8 [8A, 8B] at the both ends. The beam 6 becomes an input electrode. An input terminal t1 is led out from the input-side wiring layer 7 and an output terminal t2 is led out from the output electrode 4. In this oscillator 1, a high frequency signal S1 is supplied through the input terminal t1 in a state in which a DC bias voltage V1 is applied between the beam 6 and the ground. When the DC bias voltage V1 and high frequency signal S1 are input to the input terminal 1, the beam 6 having a natural oscillation frequency determined by a length thereof oscillates by electrostatic power generated between the output electrode 4 and the beam 6. With this oscillation, a high frequency signal corresponding to temporal change of capacitance between the output electrode 4 and the beam 6 and the DC bias voltage is output from the output electrode 4 (therefore, from the output terminal t2 ). A signal corresponding to the natural oscillation frequency (natural frequency) of the beam 6 is output in a high frequency filter.
Non-patent Literature 1: C. T.-Nguyen, Micromechanical components for miniaturized low-power communications (invited plenary), proceedings, 1999 IEEE MTT-S International Microwave Symposium RF MEMS workshop, Jun. 18, 1999, pp 48-77.

Micro-oscillator, semiconductor device and communication apparatus


A current sensor comprises a magnetic module, whereby a primary conductor, a compensating winding and a magnetic field probe are magnetically coupled to each other. The primary conductor carries a current to be measured, with a driving circuit, for producing a triangular current, injected into the compensating winding. An evaluation circuit switches the output signal thereof from a first to a second output level and vice versa by a zero crossing of a signal, provided by the magnetic field probe, whereby the output signal is pulse-width modulated, depending on the intensity of the current to be measured.

For measuring direct current and alternating current, the compensation principle is used frequently, in which the magnetic field produced by a measurement current in a magnetic core is compensated by a compensation current in a secondary winding. For controlling the compensation current, a detector is provided in the magnetic circuit, which detector detects the deviation from the zero field. The secondary current is thus a precise image of the primary current to be measured. Compensation current sensors of such type are known by way of example from EP 0294590 B1 or EP 0960342 B1. The advantage of such current sensors is that they have a very high degree of accuracy and practically do not require any intervention in the electric circuit to be measured. On the other hand, the disadvantage is that compensation current sensors require relatively high expenditure.
Tests for battery management modules, which are mounted on the battery pole terminal and which are supposed to have a digital output for connection to data buses (e.g., LIN bus or CAN bus), have shown that the micro controller required in this case, with the analog/digital transducer, reference voltage and the high-precision load resistors represents a formidable expense factor.
However, in order to achieve the required precision, a micro controller would also be necessary in a solution with an analog output (e.g., voltage output) in the low current region particularly for hysteresis determination. In addition, an analog output is interference-prone and a precision reference is required on both the sides so that the output signal regions of the sensor and the analog/digital transducer are attuned to each other in the control unit processing these further.
Sensors having a pulse width-modulated output (PWM output) are also used. Here, a pulse width-modulated output signal (PWM output signal) is generated by converting a linear output signal into a pulse width-modulated signal (PWM signal). A PWM signal is very advantageous per se since it is fail-safe and can be evaluated very easily and cost-effectively in a controller of a control unit processing it further, there being particularly no requirement of any cost-intensive analog-digital converters and precision references. However, the approach for generating a pulse width-modulated output signal from a linear output signal by a corresponding conversion, is disadvantageous in many respects. Considerable additional costs are involved since an additional step, in which precision components are also used, is required for converting the linear output signal into a pulse width-modulated signal. Furthermore, said solution is also problematic in terms of reliability and security. Thus, for example, a fault is feasible in which the pulse width-modulated signal with a duty factor of 1:1 indicates a normal operating state and thus does not indicate any primary current although the sensor arranged in front has failed and there is a possibility of a very high primary current flowing.


The present invention provides a filter member. The filter member comprises: a filter for discriminating cells to be analyzed in a sample from other components; a first filter holding member which comprises a first through hole and has a plate-like shape; and a second filter holding member which comprises a second through hole and is fitted into the first filter holding member. When the first and second filter holding members are integrated by fitting the second filter holding member into the first filter holding member, the filter is sandwiched between the first filter holding member and the second filter holding member, and the first through hole is opposed to the second through hole through the filter. A first elastic body is formed on a surface of the first filter holding member, the surface being in contact with the filter. A second elastic body is formed on a surface of the second filter holding member, the surface being in contact with the filter.

Conventionally, a cell analyzer is known for analyzing cells contained in biological samples collected from a living body. For example, US Pub. No. 2008/108103 discloses a cell analyzer which determines the progression of canceration based on measurement results obtained by using a flow cytometer to measure epithelial cells contained in a sample collected from the cervix of a subject.
In this cell analyzer, it is preferable to use a large number of cells to be analyzed to increase the accuracy of analysis when performing analysis of individual cells. For example, US Pub. No. 2011/076755 discloses a sample preparation apparatus which is capable of increasing the number of cells per unit volume supplied for analysis by increasing the concentration of the cells contained in a sample.
This sample preparation apparatus has a storage chamber for accommodating a sample when the top surface is opened, a cylindrical piston which has a filter loaded at the bottom end surface and which is inserted into the storage chamber, a suction tube for suctioning a liquid that penetrates to the interior of the piston through the filter, and a stirrer disposed at the bottom of the storage chamber. In the process of concentrating the sample, the sample is first charged into the storage chamber. Thereafter, the piston is inserted in the storage chamber until the filter is immersed in the sample. At this time, the liquid leaking into the piston is suctioned by the suction tube and then removed from the storage chamber. The cells to be analyzed adhere to the bottom surface of the filter and do not pass through the filter. The cells adhered to the bottom surface of the filter are detached from the filter by operating the stirrer, if appropriate. The sample remaining in the storage chamber now contains a high concentration of cells to be analyzed.
In order to make replacement of the filter easy, it is contemplated that the filter is attached to a holding member, and then the member is detached from the apparatus.

Filter member and a method of obtaining cells using the same


An image forming apparatus includes a pair of side covers, a finger receiving portion, a connection member, and a fitting member. One of the pair of side covers defines one of right and left outer side-surfaces of the image forming apparatus and the other defines the other of the right and left outer side-surfaces of the image forming apparatus. The finger receiving portion is inwardly recessed in each of the side covers with respect to a right-left direction and comprises an upper wall that has an insertion opening penetrating through the upper wall with respect to an top-bottom direction. The connection member is configured to connect the side covers with each other. The fitting member is a separate part from the connection member and is fitted to each of the finger receiving portions from an inner side of each of the side covers. The fitting member comprises a protrusion that protrudes downward therefrom. The protrusion protrudes downward from the upper wall of the finger receiving portion via the insertion opening.

A known image forming apparatus includes a recessed finger receiving portion defined in a side surface of a housing thereof. In the known image forming apparatus, a nonslip member is fixed in each finger receiving portion by using an adhesive. With the provision of the nonslip members, the user hooks his/her fingers on the finger receiving portions when carrying the image forming apparatus, thereby reducing slipping of the user's fingers from the finger receiving portions.

Image forming apparatus having side cover including finger receiving portion