Embodiments of an AC coupled bus charging system are disclosed that may allow for different charging currents. The charging system may include a charging circuit and a control circuit. The charging circuit may be operable to controllably select different charging currents dependent upon the output of the control circuit.

1. Technical Field
This invention is related to the field of high-speed interface design, and more particularly to AC coupling techniques.
2. Description of the Related Art
Computing systems typically include a number of interconnected integrated circuits. In some cases, the integrated circuits may communicate through parallel interfaces, which simultaneously communicate multiple bits of data. In other cases, the integrated circuits may employ a serial interface, which sequentially communicates one bit of data at a time. For both parallel and serial interfaces, communicated data may be differentially encoded.
In a computing system, the integrated circuits may have different power supply requirements, which may result in different output voltages being coupled to the integrated circuits' respective communication ports. Furthermore, variations in the properties of wiring traces on circuit boards as well as differences in power supply performance, may further contribute to differences in the power supply voltages supplied to the integrated circuits.
In some cases, each integrated circuit may be coupled to an interface through a series capacitor to remove the DC component of a transmitted or received signal, allowing only the high frequency portion of the transmitted or received signal to pass. During power-up, it may be necessary to charge the series capacitor to a voltage level sufficient to transceiver circuits to operate properly.

Fast wake-up of differential receivers using common mode decoupling capacitors


When a code word sequence is generated by converting input data words of p bits into code words of q bits and concatenating adjacent ones of the code words with a merge bit sequence of r bits in order to obtain the best DSV value, according to one aspect, the adjacent code words are concatenated with the merge bit sequence of r bits which is selected, free from the restriction of the minimum run-length of (d+1)T and the maximum run-length of (k+1)T based on the run-length limiting rule RLL(d, k) but permitting the minimum run-length of (d+1)T and the maximum run-length of (k+2)T. According to another aspect, a merge bit sequence to be inserted after a current code word is selected by prefetching the current code word, a next code word, and a further next code word, temporarily concatenating these code words with merge bit sequences of r bits respectively to prepare code word sequence candidates free from the predetermined run-length limiting rule, calculating the DSV values of the code word sequence candidates, selecting one of the code word sequence candidates having a DSV value whose absolute value is closest to zero, and selecting the merge bit sequence between the current code word and the next code word of the selected merge bit sequence candidate. According to a further aspect, the input data words are encoded by a p-q modulation scheme after introducing for a predetermined period, as an input data word, specific data comprising alternating current signals or direct current signals which would cause a modulation device that prefetches only the next code word to output a code word sequence which includes particular frequency components.

1. Field of the Invention
The present invention is related to a modulation device, a modulation method, and a recording medium for preventing the copy of digital information signals that are recorded on an optical disc, a digital magnetic tape and the like recording medium.
2. Description of the Related Art
With the advent of the digital multimedia age, large amounts of digital information signals are recorded on optical discs, digital magnetic tapes and the like.
For example, a read-only optical disc, such as CD (Compact Disc) for recording music information, CD-ROM (CD-Read Only Memory) for recording computer data, comprises a disc substrate in the form of a platter in which spiral or concentric tracks are defined. A variety of digital information signals can be recorded on the tracks and quickly accessed from the tracks, while the discs are suited to mass-production at a low price, and therefore, such discs have been heavily used.
On the other hand, digital magnetic tapes for recording PCM music information are heavily utilized since these tapes can be played back for a longer time than optical discs.
Meanwhile, the recording medium illustrated in the following explanation as a medium for recording digital information signals is an optical disc on which digital information signals are recorded or from which digital information signals are reproduced by the use of an optical pickup. However, digital magnetic tapes are substantially different from optical discs only in that a magnetic head is used for reproducing digital information signals, and therefore the explanation of the case making use of a digital magnetic tape is dispensed with.
The optical disc such as CD, CD-ROM as described above is formed by converting digital information signals into a digital bit sequence in the form of concave pits and convex lands, engraving the bit sequence on spiral or concentric recording tracks of a stamper disc, placing the stamper disc formed with the recording tracks in an injection molding device, transferring the recording surface of the stamper disc having the recording tracks onto a transparent disc substrate in the form of a platter made of a transparent resin having an outer diameter of 120 mm or 80 mm, a central bore diameter of 15 mm and a thickness of 1.2 mm, and further forming a reflective film and a protection film, in this order, on the recording surface to provide a read only disc.
Then, during the readout operation from a read-only type optical disc, a laser beam for reading data is emitted from an optical pickup movably provided in an optical disc drive, projected onto the recording surface through the transparent optical disc substrate on the recording surface, reflected by the reflective film of the recording surface, and received by the optical disc drive for reproducing the signals of the recording surface carried by the laser beam as reflected.
Incidentally, the music information recorded on a CD and the computer data recorded on a CD-ROM are protected by a copyright law. However, since the information and the data are digital information, it is possible to copy the information in a CD-R (Compact Disc-Recordable) which can be written to once, CD-RW (Compact Disc-ReWritable) which can be written and rewritten several times and the like writable type optical disc.
While having the similar external appearance as a read-only type optical disc such as a CD, a CD-ROM or the like, a writable type optical disc such as a CD-R, a CD-RW is formed by forming concave grooves in the form of a spiral or concentric circles on a transparent optical disc, spin-coating an organic dye to form a recording layer on the concave groove, and further forming a reflective film and a protection film, in this order, on the organic dye, and is available at a low price on the market.
In this situation, when the music information recorded on a CD or the computer data recorded on a CD-ROM is recorded on a CD-R or a CD-RW, the signal format of the CD-R or the CD-RW is the same as the signal format of the CD or the CD-ROM, and therefore the infringement of a copyright occurs.
In what follows, the code word sequence recorded on a known CD will be explained.
FIG. 1 is a view for explaining the format of EFM signals of the music information recorded on a CD. FIG. 2 is a table for use in an 8–14 modulation. FIGS. 3A and 3B are views for explaining a DSV control scheme applied after the 8–14 modulation.
First, music information is recorded on a CD in a signal format in conformity with the CD format "Red Book standards", or the IEC (International Electrotechnical Commission) 908 standard.
In this case, generally speaking, the pit lengths of an optical disc have to satisfy a minimum run-length (a shortest pit length or a shortest land length) required under the physical restriction relating to the pit generation and the optical transmission characteristics for read/write operations, a maximum run-length (a longest pit length or a longest land length) required in order to facilitate clock regeneration, and further have to satisfy the modulation scheme requirement that the DC component and the low frequency components of recording signals as modulated are sufficiently suppressed for the purpose of securing the servo bandwidth and so forth.
The EFM (Eight to Fourteen Modulation: 8–14 modulation) scheme used for CDs is one of the modulation schemes conforming to the above restrictions and has a minimum run-length of 3T (T is the length of a channel bit) and a maximum run-length of 11T.
Namely, music original data AD to be recorded on a CD is digital data composed of a plurality of successive data units each of which comprises upper eight bits (one byte) plus lower eight bits (one byte) totaling to 16 bits (two bytes).
When the music original data AD is recorded on a glass master disc for mastering, the music original data AD is converted into a signal sequence suitable for recording in a signal format according to the EFM scheme. The EFM signals 1 are recorded on the glass master disc in the signal sequence as shown in FIG. 1. Then, a metallic master disc, a mother disc and a stamper disc are formed from the glass master disc in this order by electroforming, followed by placing the stamper disc in an injection molding device and transferring the recording surface of the stamper disc to a transparent optical disc to obtain a CD. Accordingly, the recording surface of the CD is equivalent to the recording surface of the glass master disc.
In this case, in accordance with the format of the EFM signals 1 as described above, the EFM signals 1 are prepared in the form of first and second code word sequences 1d and 1f as shown in FIG. 2 by dividing the input music original data AD into an input data word D of the upper eight bits and an input data word D of the lower eight bits, converting each of the respective input data words D of p bits (=eight bits) into run-length limited code of q bits (=eleven bits) (referred to as a code word C in the following description) while conforming to the run-length limiting rule of the minimum run-length of 3T and the maximum run-length of 11T with reference to a coding table as shown in FIG. 2, and concatenating each adjacent code words C converted as shown in FIG. 1 with an intervening merge bit sequence 1b of r bits (=three bits) for controlling the DSV (Digital Sum Value) while conforming to the run-length limiting rule.
At this time, when the predetermined run-length limiting rule is observed, the minimum number of successive 0's occurring between adjacent logic 1's is d (=2) according to the minimum run-length of 3T while the maximum number of successive 0's occurring between adjacent logic 1's is k (=10) according to the maximum run-length of 11T. In other words, when the run-length limiting rule RLL(d, k) (=RLL(2, 10)) is observed, the minimum run-length is set as (d+1)T=3T while the maximum run-length is set as (k+1)T=11T. The restriction of the minimum run-length of (d+1)T=3T and the maximum run-length of (k+1)T=11T is satisfied in the first and second code word sequences 1d and 1f which are obtained by concatenating adjacent code words C and C with an intervening merge bit sequence 1b of three bits. When the first and second code word sequences 1d and if are NRZI-converted, the minimum run-length 3T corresponds to the minimum inversion interval of the NRZI converted sequence while the maximum run-length 11T corresponds to the maximum inversion interval of the NRZI converted sequence.
Then, the EFM signals 1 as p-q modulated (=8–14 modulation) are arranged in order to decrease the DC component and the low frequency components of the EFM signals 1 while conforming to the run-length limiting rule RLL(d, k) (=RLL(2, 10)) of the minimum run-length 3T and the maximum run-length 11T.
As is well known in the art, the NRZI conversion provides a modulation scheme which inverts the signal in a "1" and leaves the signal unchanged for a "0". Since NRZI (Non Return to Zero Inverted) conversion is performed on the EFM signals 1 including the first and second code word sequences 1d and 1f, the waveform after the NRZI conversion is the waveform of the recording signals R on the glass master disc in which, for example, each L (low) level zone of the recording signals R is represented by a concave pit (or a convex land) while each H (high) level zone of the recording signals R is represented by a convex land (or a concave pit) to provide a bit sequence in combination.
Also, as illustrated in FIGS. 3A and 3B, the above described DSV is the integral of the EFM signals 1 from the start time point of the code word sequence to the current time point in which the H (high) level of the waveform of the EFM signals 1 as NRZI converted is calculated as "1" (positive sense) while the L (low) level thereof is calculated as "−1" (negative sense). At this time, since the polarity is inverted with a data bit of "1" in accordance with the NRZI conversion, a code word generates either of two DSV values dependent upon the state of the waveform obtained by NRZI-converting a code word immediately before the code word to be connected. For example, in the case where the input data word="002", the DSV value is inverted when the previous level is the L (low) level shown in FIG. 3A as compared with the DSV value when the previous level is the H (high) level shown in FIG. 3B. Namely, the absolute values of the DSV values as illustrated in FIGS. 3A and 3B are equal to each other in which an input data word (=002) and an input data word (=253) are concatenated with a merge bit sequence.
In this case, a merge bit sequence 1b of three bits is selected from among bit sequences of (000), (001), (010) and (100) in order that the absolute value of the DSV value approaches zero while conforming to the run-length limiting rule RLL(d, k) (=RLL(2, 10)). By such selection, H (high) level zones and L (low) level zones appear in the recording signals R approximately at the same frequency over a long period, while restricting to a low level the DC component of the waveform of the recording signals R. Accordingly, the DSV value is also controlled in order that concave pits and convex lands appear in the disc approximately at the same frequency.
Returning to FIG. 1, one frame of the EFM signals 1 as described above is composed of a synchronization signal 1a, a merge bit sequence 1b, a subcode 1c, a merge bit sequence 1b, a first code word sequence 1d, a merge bit sequence 1b, a C2 error correction code 1e, a merge bit sequence 1b, a second code word sequence 1f, a merge bit sequence 1b, a C1 error correction code 1g and a merge bit sequence 1b arranged in this order from the head, and therefore totals 588 channel bits.
In this case, the synchronization signal 1a arranged in the head is a 24 bit signal including three transitions of 11T, 11T and 2T indicative of the start of a frame and distinctive from the respective signals 1b to 1g as described above.
The subcode 1c arranged after the synchronization signal 1a with the intervening merge bit sequence 1b of three bits is a signal for controlling the playback operation of a CD.
The first code word sequence 1d arranged after the subcode 1c with the intervening merge bit sequence 1b of three bits is prepared by converting each input data word D (each music original data) of p bits (=8 bits) into a corresponding code word C with reference to the coding table as shown in FIG. 2 and concatenating adjacent code words C and C with an intervening merge bit sequence 1b of three bits, and therefore composed of 12 code words C (12 symbols) and 11 merge bit sequences 1b.
The C2 error correction code 1e arranged after the first code word sequence 1d with the intervening merge bit sequence 1b of three bits is used to perform error correction of the first code word sequence 1d and the second code word sequence if of the EFM signals 1 during the playback of a CD.
Further, the second code word sequence 1f arranged after the C2 error correction code 1e with the intervening merge bit sequence 1b of three bits is composed of 12 code words C (12 symbols) and 11 merge bit sequences 1b of three bits in the same manner as the first code word sequence 1d as described above.
Furthermore, the C1 error correction code 1g arranged after the second code word sequence 1f with the intervening merge bit sequence 1b of three bits is used to perform error correction of the first code word sequence 1d, the second code word sequence 1f and the C2 error correction code 1e of the EFM signals 1 during the playback of a CD.
One block as a unit of music corresponding to a 1/75 second is then composed of successive 98 frames each of which is formed by NRZI-converting one frame of the EFM signals 1 as described above.
Incidentally, the above explanation is applicable to the case of a CD-ROM for storing computer data only by replacing the music original data as shown in FIG. 1 with computer original data, and therefore redundant explanation is not repeated.
Next, a conventional modulation device will be explained with reference to FIG. 4 and FIGS. 5A through 5C.
FIG. 4 is a block diagram schematically showing a conventional modulation device. FIGS. 5A through 5C are views for explaining the calculation of the DSV values for a plurality of the code word sequences temporarily prepared. Each code word sequence is generated in the conventional modulation device by inserting one of the merge bit sequences (000), (001), (010) and (100) between a current code word and the next code word while conforming to a predetermined run-length limiting rule.
The conventional modulation device 20 as shown in FIG. 4 is included in a glass master disc recording apparatus (not shown in the figure) or a CD-R drive which can be used for copying the music information of a CD to a CD-R disc, and composed generally of an 8–14 modulation circuit 21, a merge bit inserting circuit 22, a DSV value calculation circuit 23, a DSV value comparing circuit and merge bit sequence selecting circuit 24.
The conventional modulation device 20 divides music original data AD of 16 bits into upper eight bits and lower eight bits as input data words and then converts the respective input data words D of eight bits into the respective code words C of 14 bits. Then, the conventional modulation device 20 temporarily concatenates, for example, a current code word Cx and a next code word Cy just subsequent thereto with all the intervening merge bit sequences of three bits 1b that satisfy the run-length limiting rule RLL(2, 10) to generate a plurality of code word sequences. Then, the conventional modulation device 20 selects one sequence, whose absolute DSV value is closest to zero, from among the plurality of code word sequences as the final single code word sequence.
More specifically explaining, in the case of the conventional modulation device 20, the music original data AD of 16 bits is input to the 8–14 modulation circuit 21 in chronological order.
In the 8–14 modulation circuit 21 described above, the music original data AD as input is divided into an input data word D of upper eight bits and an input data word D of lower eight bits to generate a series of input data words D of eight bits in chronological order, as explained with reference to FIG. 1, followed by successively converting the respective input data words D of eight bits into code words C of 14 bits with reference to the coding table as shown in FIG. 2, in which for example a current code word Cx and a next code word Cy just subsequent thereto are read in sequence. Then, the current code word Cx and the next code word Cy are input to the merge bit inserting circuit 22 from the 8–14 modulation circuit 21.
Next, the merge bit inserting circuit 22 serves to insert a merge bit sequence of three bits 1b between adjacent code words C and C while conforming to the restriction of the minimum run-length 3T and the maximum run-length 11T in accordance with the run-length limiting rule RLL(2, 10) of the CD standards. Four bit sequences of (000), (001), (010) and (100) are prepared in this merge bit inserting circuit 22 as candidates of the merge bit sequence of three bits 1b. Incidentally, while there are eight sequences of three bits as combinations of "0" and "1", the remaining four sequences, i.e., (011), (101), (110) and (111) can not satisfy the run-length limiting rule RLL(2, 10) because two or more 1's appear successively or with an intervening "0", and therefore are not available.
Then, the four merge bit sequences (000), (001), (010) and (100) are temporarily inserted respectively between the code words Cx and Cy as successively input to the merge bit inserting circuit 22 to generate a plurality of code word sequences.
In this case, as illustrated in FIGS. 5A to 5B, for example, the current code word Cx has "010" from the 12th bit to the 14th bit thereof while the next code word Cy is "00100010000010". On the other hand, the current code word Cx has "1" at the 13th bit position while the next code word Cy has "1" at the third bit position. Thereby, out of the four merge bit sequences as described above, the fourth merge bit sequence (100) does not conform to the run-length limiting rule RLL(2, 10), while the first to third merge bit sequences (000), (001) and (010) conform to the run-length limiting rule RLL(2, 10), and therefore the fourth merge bit sequence (100) is determined not to be inserted.
After inserting the three merge bit sequences (000), (001) and (010) respectively between the code words Cx and Cy, the resultant three code word sequences {Cx(000)Cy}, {Cx(001)Cy} and {Cx(010)Cy} are input to the DSV value calculation circuit 23 to calculate the respective DSV values of the three code word sequences. In the case 1 as shown in FIG. 5A in which the merge bit sequence (000) is inserted between the code words Cx and Cy, the DSV value of the code word sequence {Cx(001)Cy} is +2. Also, in the case 2 as shown in FIG. 5B in which the merge bit sequence (001) is inserted between the code words Cx and Cy, the DSV value of the code word sequence {Cx(001)Cy} is −4. Similarly, in the case 3 as shown in FIG. 5C in which the merge bit sequence (010) is inserted between the code words Cx and Cy, the DSV value of the code word sequence {Cx(010)Cy} is −6.
Thereafter, the respective DSV values of the three code word sequences are input to the DSV value comparing circuit and merge bit selecting circuit 24 from the DSV value calculation circuit 23. The code word sequence {Cx(000)Cy} is then selected by and output from the DSV value comparing circuit and merge bit selecting circuit 24 as a final single code word sequence having the DSV value (=+2) closest to zero from among the three code word sequences. In other words, the DSV value comparing circuit and merge bit selecting circuit 24 serves to select the merge bit sequence (000) corresponding to the final single code word sequence {Cx(000)Cy} having the DSV value closest to zero. The above described procedure is repeated with the next code word Cy as the next current code word and the code word just after the code word Cy as the next next code word to obtain a final single code word sequence {Cx(000)Cy . . . }.
Thereafter, the recording signals R (FIG. 1) suitable for recording is generated from the final single code word sequence {Cx(000)Cy . . . } of which the DSV value is controlled. Then, the generated recording signals R is recorded on a glass master disc for CD or a CD-R by a laser beam.
The glass master disc for CD is used to prepare a stamper disc (not shown in the figure) which in turn is used to produce a CD.
In view of the above, utilizing a software for copy stored in a hard disk (not shown) in a personal computer (not shown), a user can play back a CD on which music information that is desired to be copied by the user is recorded, with a CD drive (not shown) and then input the music information that is outputted from the CD drive and is desired to be copied on a CD-R, into a CD-R drive (not shown), and accordingly can copy the music information desired to be copied, onto the CD-R as it is by means of the conventional modulation apparatus 20 provided in the CD-R drive without authorization of the owner of the copyright.
In other words, when the music original data AD of 16 bits as output from the CD drive is encoded by the conventional modulation device 20 in the CD-R drive, the music information recorded on the CD-R is identical to the music information recorded on the CD in terms of the EFM signals. The CD-R as duplicated can be used to copy the music information onto another CD-R again without the original CD so that the music information is distributed in large quantities in the world.
Taking into consideration the situation, an exemplary copy-protected optical disc is proposed which can be used to prevent the music information recorded on a CD or the computer data recorded on a CD-ROM from being copied onto a recordable CD-R or CD-RW (for example, disclosed in Japanese Patent Application Laid-open No.2001-357536, pages 4–5, FIG. 4).
FIG. 6 is a longitudinal cross sectional view showing an optical disc, in which copy-protection technology is incorporated, as an exemplary conventional technique.
The conventional optical disc 100 as shown in FIG. 6 is one described in the above Japanese Patent Application Laid-open No. 2001-357536. Referring to the same document, in the conventional optical disc 100 designed by incorporating the copy-protection technology in an optical disc such as CD-ROM, DVD-ROM, convex and concave portions are formed with lengths ranging from 3T to 14T (T is 0.133 μm) based on the run-length limiting rule (referred to as the run-length limited encoding scheme in the same publication). However, this technique is characterized in that the sequence of the convex and concave portions further includes convex or concave portions having each length shorter than the minimum run-length based on the run-length limiting rule.
Specifically, as shown in FIG. 6, a pit A is convexly formed with a length of 1T to 2T while a pit B is concavely formed with a length of 1T to 2T located apart from the pit A by X. The lengths of these pits A and B do not satisfy the run-length limiting rule.
Accordingly, the shortest pit length (or the shortest land length) of the conventional optical disc 100 is smaller than the normal value by setting a minimum run-length of 1T to 2T without satisfying the requirement of the minimum run-length 3T out of the run-length limiting rule comprising the minimum run-length 3T and the maximum run-length 14T.
In order to implement the technical concept of the conventional optical disc 100 as described above within a known CD on which convex and concave portions (pit sequence) are formed with lengths between 3T to 11T conforming to the run-length limiting rule RLL (2, 10) included in the CD standards to modify the signal sequence recorded on a CD, a code word C such as "00100110010010" is used as one corresponding an input data word D (=255) to introduce a short convex or concave portion (pit sequence) of 1T instead of "00100000010010" in the coding table shown in FIG. 2.
When playing the modified CD with a commercially available optical disc drive, it is impossible to judge whether or not the optical disc as played is legally-distributed because the verification pit having a length of 1T to 2T in the data as read out is shorter than a normal pit having a pit length (land length) of 3T to 11T and therefore the RF signal as read out by an optical pickup does not reach a sufficient bright level or a sufficient dark level so that the binary signals obtained from the RF signal contains no signal indicative of the verification pit having a length of 1T to 2T. Also, it is possible without trouble to copy the music information recorded on the modified CD by reproducing the music information with a commercially available optical disc drive and inputting the reproduced music information to a CD-R drive.
Accordingly, under the present circumstance in which a number of players and CD-R drives have already been distributed on the market, the above copy-protection mechanism is not effective because of its assumption of the spread of a new player such as the optical disc 100 capable of detecting the verification pit.
Furthermore, in the same manner as optical discs, digital magnetic tapes have the same problem that digital information signals recorded therein are copied.

Modulation device, modulation method and recording medium


A method is disclosed use with a circuit device that includes a circuit having a predetermined voltage-current characteristic and a detector configured to detect a voltage-current relation of the circuit. The method includes using the detector to detect the voltage-current relation of the circuit, and indicating if the detected voltage-current relation differs from the predetermined voltage-current characteristic. A circuit device includes a circuit having a predetermined voltage-current characteristic, and a detector configured to detect a voltage-current relation of the circuit. The circuit device is configured to indicate if the detected voltage-current relation differs from the predetermined voltage-current characteristic.

Electrical, electronic, or semiconductor devices (hereinafter referred to as 'device under test' or 'DUT') suffer from various defects and malfunctionings. The DUT must be comprehensively tested during the manufacturing process to limit any structural faults or process faults. A manufacturing process variation or a manufacturing defect can cause a process fault in the DUT e.g. an open, short, or a shift in the operating point of a transistor.
In addition to tests carried out during manufacturing, regular monitoring of DUT during operation is also necessary for optimum working. Generally, electrical or electronic or semiconductor devices may suffer degradation due to continued use. Moreover, defects may arise due to unwanted events such as voltage fluctuations or such.
To ensure proper functioning of the DUT, complex parameters such as mixer noise, phase noise, conversion gain needs to be monitored. As an example, the operating point of a transistor can be simply measured by direct current (DC) parameters such as biasing currents, reference currents, or reference voltages (depending on the actual circuit). Similarly, radar MMICs (Monolithic Microwave Integrated Circuits) need testing of complex low frequency (LF) or radio frequency (RF) parameters such as radio frequency receiver (RF-RX) conversion gain, radio frequency transmitter (RF-TX) phase noise at different offset frequencies, mixer noise tests, signal-to-noise ratio (SNR), etc. Such parameters can also be measured using DC parameters.
The measuring and monitoring of DC parameters require sophisticated equipment such as an Automatic Test Equipment ('ATE'). However, due to ATE limitations, monitoring and measuring of DC parameters consume a lot of test time and may cause potential yield loss.
Circuits configured to self-assess (Built-In-Self-Test, 'BIST') require additional chip area for such self-test and self-monitoring circuits.
Hence, an improved arrangement to measure and monitor DC parameters for assessing the proper operation of DUT may be desired.


A selective call receiver (100) comprises a receiver (104) for receiving a message and a vibrator (116) capable of vibrating at a selected one of at least two selectable frequencies for alerting a user of a received message. The vibrator (116) also has a selector (120) or a tuning element (130) for varying the frequency of the vibrator (116).

Electronic devices such as selective call receivers have different methods of alerting a user that a message has been received. One such method of alert is a tactile alert (e.g., vibrational alert), which is conveniently used in business meetings, libraries, and other places where it may be inappropriate to use an audio alert. However, in conventional selective call receivers, the frequency of the vibrator device is usually fixed at some pre-determined frequency. Although the frequency of vibration is fixed, a large variation in the frequency results from the manufacturing process. This causes some users, however, to consider the vibratory mode to be either too high or too low, and as a consequence, a number of these users may avoid using the vibratory alert mode.
Regrettably, however, a selective call receiver having a variable frequency tactile alert has been heretofore unavailable, thus failing to satisfy the varied needs of different users of selective call receivers. Accordingly, a need exits for a tactile alert having a variable frequency of vibration.

Selective call receiver having a variable frequency vibrator


A multi-port processor architecture having a first bus, a second bus and a central processing unit. The central processing unit having a first and second ports coupled to first and second busses respectively. A first bus to second bus bi-directional interface couples the first bus to the second bus. Optionally, the first bus or the second bus can be connected to a memory. The architecture can include a third bus with a third bus to first bus bi-directional interface connecting the third bus to the first bus and a third bus to second bus bi-directional interface connecting the third bus to the second bus. If there are additional bus systems, the Nth port (where N is an integer greater than 2) is connected to the Nth port. The buses use bi-directional interfaces to communicate with each other without using CPU or memory resources, reducing memory access latency.

The present invention relates generally to computer bus architectures and to system-on-a-chip architectures with multi-port processors, including but not limited to embedded processors, application specific integrated circuits (ASICS), Field Programmable Arrays (FPGAs) and other programmable devices.
System-on-a-chip (SoC) design allows a designer to create complex silicon systems from smaller working blocks or systems. By providing a method for easily supporting proprietary functionality in a larger context that in a larger context that includes many existing design pieces, SoC design facilitates the use of silicon design for many systems. There are three views of traffic for a design which are important to differentiate, a memory centric view, a processor centric view and an input/output (I/O) view. Traditionally, prior art systems tend to be processor centric and not balanced. It is desirable that an SoC does not compromise one view over another and provides equal optimization. If all three traffic aspects of an SoC are fully scaleable, the applications for this SoC can be unlimited.
The typical SoC design includes a central processing unit (CPU), memory and peripherals communicating over a fast bus (for the CPU and memory) and a slow bus (for the peripherals). Because the CPU, memory, and peripherals (when accessing memory) share the same bus, bus latency can be problematic. When using a single port processor, the processor must compete with the rest of the SoC system for the bus and memory resources. This latency can be even more problematic in hierarchical bus systems. For example a first peripheral can send data to a second peripheral by writing the data to memory, which is then read by the second peripheral. During the time data is being written or read, neither the CPU nor other peripherals can access the memory or the bus providing access to the memory. A bus arbiter can be employed to control access to the bus. However, the bus arbiter adds to the overhead in accessing the bus and can cause even more latency.
One solution to the aforementioned problems is to use larger caches. Another solution is to increase the clock speed (frequency) of the bus system. Yet another solution is to provide dedicated memory interfaces for the critical design parts of the SoC. However, these approaches are expensive. Furthermore, these approaches can introduce other problems, e.g. increasing the clock speed (frequency) of the system bus requires more power and generates additional heat.
There are three views of SoC traffic that should be differentiated, that is the memory centric view, the processor centric view, and the input/output (I/O) view. Preferably, a SoC doesn't compromise one view over another and provides equal optimization. The application for a SoC with equal optimization can be unlimited if all three traffic aspects are fully scaleable.
Thus it is desirable to minimize latency for accessing memory, while operating the memory bus at the lowest possible clock speed and yet provide a high data transfer rate.

Multi-port processor architecture with bidirectional interfaces between busses

Toshiba America Electronic Components, Inc.


A steering mechanism connects the shaft of an actuator with a piston rod of a hydraulic cylinder and provides a spool valve in which the spool valve housing is attached to the hydraulic cylinder and the shaft of the actuator extends through a cylindrical opening in a spool of the spool valve. The connector is connectable to a steering arm of a marine propulsion device and the spool valve housing is connectable to a transom of a marine vessel.

1. Field of the Invention
The present invention is generally related to a marine steering system and, more particularly, to an actuator which combines a linear actuator and a spool valve in a compact structure for use in a steering system of a marine propulsion device.
2. Description of the Related Art
Those skilled in the art of marine propulsion systems are aware of many different steering devices that can be used to cause the rotation of a marine propulsion device about a generally vertical steering axis. Typically, a cable system is incorporated in the steering system and connects a steering arm of a marine propulsion device to a manually controllable steering mechanism, such as a steering wheel. Other types of steering systems incorporate hydraulically assisted components which use pressurized hydraulic fluid to provide force in order to assist the operator of a marine vessel in accomplishing steering maneuvers. Some hydraulic steering systems use a pump mechanically attached to a steering wheel and a hydraulic actuator attached to the marine propulsion device. Other types of hydraulic steering systems use a mechanically or electrically driven hydraulic pump to provide pressurized hydraulic fluid that is then ported, by suitable valves, to actuators that effect the steering maneuvers.
In certain marine steering systems, two or more marine propulsion devices can be individually rotated about their respective steering axes independently so that complicated maneuvers can be accomplished by selectively directing the propeller thrusts of the marine propulsion devices in selected directions while also controlling the forward and reverse rotation of the propellers in order to provide suitable thrust vectors that allow the marine vessel to be maneuvered. These types of systems typically use a joystick associated with a microprocessor to interpret commands from the operator of a marine vessel and calculate the necessary individual thrust vectors necessary to accomplish those commanded maneuvers.
U.S. Pat. No. 3,645,296, which issued to Adams on Feb. 29, 1972, describes a power assisted steering system. A power assisted rack and pinion steering system includes a housing, relatively rotatable torque input and output shafts mounted for rotation in the housing, a pinion mounted for joint rotation on the torque output shaft, a rack engaging the pinion and a fluid valve assembly for controlling the flow of fluid to and from the opposite ends of a double-acting servomotor also connected to the rack for assisting in the movement thereof. The valve assembly comprises a circumferentially grooved spool valve connected to one of the shafts for axial movement, such movement occurring when the shafts are rotated relative to one another. Axial movement of the spool valve establishes fluid communication between a power fluid pump and the servomotor for powered movement of the servomotor and hence the rack.
U.S. Pat. No. 3,712,582, which issued to Moesta on Jan. 23, 1973, describes a fluid flow control valve and linear actuator therefore. A support housing having a cylindrical bore in which a complimentary cylindrical spool valve is carried and screw-threadedly engaged with the housing is described. The valve is rotated by a drive motor for linear movement of the valve in the bore. An inlet port and an outlet port open to the bore so that communication therebetween is accurately controlled by the linear positioning of the spool valve. A pulse drum structure is connected with and rotates with the spool valve and has sensor points thereon which, as the pulse drum rotates with the valve, pass by a sensing device which is thus enabled to sense linear change of position of the drum and hence its associated valve.
U.S. Pat. No. 4,200,030, which issued to Elser on Apr. 29, 1980, describes a servo steering gear. A power steering gear mechanism is disclosed having conventional elements such as a double acting cylinder in a housing, a piston with a gear rack geared to a gear sector, and threaded bore in the piston having a worm shaft, wherein a steering shaft operates a rotary valve spool with which it is integral, in rotation relative a fixed valve sleeve carried by the worm shaft and wherein a torque rod connects the worm shaft to the steering spindle and passes through the worm shaft.
U.S. Pat. No. 4,841,790, which issued to Williston et al. on Jun. 27, 1989, describes an electromechanical actuator. The actuator is particularly attractive for vehicle steering applications and includes a case having a cover part rigidly attached to a housing part and an output rod supported on the case for linear shiftable movement along a primary axis of the case. An electric motor is mounted on the housing part of the case with a shaft of the motor supporting in cantilever fashion a pinion in a gear chamber of the case between the housing and covered parts.
U.S. Pat. No. 5,947,155, which issued to Miki et al. on Sep. 7, 1999, describes a linear solenoid valve. The valve is composed of a pressure regulating section and an actuator section. In the pressure regulating section, a valve spool is slidably disposed and is biased in one direction by a single elastic member. The actuator section generates a thrust force and transmits that generated thrust force in an opposite direction to the pressure regulating section via a shaft.
U.S. Pat. No. 6,065,451, which issued to Lebrun on May 23, 2000, describes a bypass valve with a constant force-versus-position actuator. A control arrangement for a fuel system having a fuel pump for supplying fuel through a variable orifice flow metering valve to an engine main fuel control is described. The control portion controls the fuel pressure differential across an orifice of the metering valve. A head sensor includes a movable diaphragm, a bypass valve for diverting fuel from the fuel pump away from the metering valve, and a coupling between the diaphragm and the bypass valve whereby the bypass valve opens and closes in response to diaphragm motion.
U.S. Pat. No. 6,234,853, which issued to Lanyi et al. on May 22, 2001, discloses a simplified docking method and apparatus for a multiple engine marine vessel. The system is provided which utilizes the marine propulsion unit of a marine vessel, under the control of an engine control unit that receives command signals from a joystick or push button device, to respond to a maneuver command from the marine operator. The docking system does not require additional propulsion devices other than those normally used to operate the marine vessel under normal conditions. The docking or maneuvering system of the invention uses two marine propulsion units to respond to an operator's command signal and allows the operator to select forward or reverse commands in combination with clockwise or counter-clockwise rotational commands either in combination with each other or alone.
U.S. Pat. No. 6,354,184, which issued to Hansen et al. on Mar. 12, 2002, describes a power machine with valve mount for valve assembly. A power machine or a skid steer loader that is driven by an engine and has a hydraulic pump, hydraulic fluid conduit, a hydraulic motor in fluid communication with a hydraulic fluid conduit and a valve that is operated or actuated by linear actuator such that the linear actuator is mounted directly on the valve block is described.
U.S. Reissued Pat. RE39,032, which issued to Gonring et al. on Mar. 21, 2006, discloses a multi-purpose control mechanism for a marine vessel. The mechanism allows the operator of a marine vessel to use the mechanism as both a standard throttle and gear selection device and, alternatively, as a multi-axes joystick command device. The control mechanism comprises a base portion and a level that is movable relative to the base portion along with a distal member that is attached to the lever for rotation about a central axis of the lever. A primary control signal is provided by the multi-purpose control mechanism when the marine vessel is operated in a first mode in which the control signal provides information relating to engine speed and gear selection. The mechanism can also operate in a second or docking mode and provide first, second and third secondary control signals relating to desired maneuvers of the marine vessel.
U.S. Pat. No. 7,131,385, which issued to Ehlers et al. on Nov. 7, 2006, discloses a method for braking a vessel with two marine propulsion devices. The method comprises steps that rotate two marine propulsion devices about their respective axes in order to increase the hydrodynamic resistance of the marine propulsion devices as they move through the water with the marine vessel. This increased resistance exerts a braking thrust on the marine vessel. Various techniques and procedures can be used to determine the absolute magnitudes of the angular magnitudes by which the marine propulsion devices are rotated.
U.S. Pat. No. 7,168,360, which issued to Massaccesi et al. on Jan. 30, 2007, describes a steering system actuator for a vehicle with at least three steered wheels. A linear actuator for vehicle powered steering systems with at least three steered wheels of a double-acting type that comprises a cylindrical body, closed and open ends, is disclosed. It also comprises a piston, accommodated inside the cylindrical body axially slidable between the ends, and a stem which is rigidly associated with the piston, coaxial to the cylindrical body, and protruding from at least one of the ends. A piston divides the cylindrical body into two chambers. Each chamber is provided with an inflow/outflow opening formed at the two opposite ends. At least one pair of one-way valves, provided in the piston with a respective inlet connected to a respective chamber and outlets mutually connected, each valve having a step slidably accommodated in the respective inlet with one end associated with a respective flow control element and the opposite end that protrudes externally from the piston, so as to open a respective valve.
U.S. patent application Ser. No. 11/602,532, which was filed by Heitzer on Nov. 21, 2006, describes a valve device for a hydraulic servo steering arrangement. It includes two valve elements which can be rotated from a neutral position relative to each other in order to thereby achieve the superimposition of an additional steering moment. The valve device further includes a linear actuator and a gear coupling the two valve elements to each other. The gear converts a linear stroke of the linear actuator into rotation. The gear includes a first cog wheel with teeth inclined in a first direction in relation to the actual direction of the cog wheel. The first cog wheel is coupled to the first valve element. The gear further includes a second cog wheel with teeth inclined in a second direction opposed to the first direction. The second cog wheel is axially displaceable by the linear actuator.
The patents described above are hereby expressly incorporated by reference in the description of the present invention.
It would be significantly beneficial if a compact device could be provided which provides a marine steering system with inherent mechanical feedback that coordinates the movement of a hydraulic actuator and a hydraulic valve under the control of the linear actuator which, in turn, is controlled by signals received from a microprocessor.


At a vehicle seat 10, a cushion material 18 is provided at a frame 14 for a sitting portion of a seat frame 12, such that a seat cushion 20 is formed. An upper cushion member (three-dimensional solid knit fabric) 86, which is a surface layer portion of the cushion material 18, is stretched at the frame 14 for the sitting portion, and is layered on a cloth spring material 18 which is a lower layer portion of the cushion material 18. When the cloth spring material 68 is pressed and flexes downward due to pushing-against force which is based on body weight of a seated person at a time of sitting on the seat cushion 20, at regions of the cloth spring material 68 which are pushed by ischial tuberosities of the seated person, tensile forces of extension coil springs 80, which are forces in the pushing direction, act, and directions of tension of the cushion material 18 are in three dimensions.

There is conventionally known, as a vehicle seat, a vehicle seat having a cushion material formed from polyurethane foam (hereinafter called urethane). As the cushion structure of such a vehicle seat, a structure is widely used in which a cushion material made of urethane is placed on a plate or a spring material, such as a contour mat (trade name) or the like provided at a seat frame or a seat back frame, and these are wrapped in a fabric material.
Therefore, it is known that the shape (the design shape) and the elastic characteristic of the cushion material have a great effect on the body pressure dispersability of the seated person and the vibration absorbability. Further, by structuring the cushion material by layering urethanes which have various characteristics, a cushion material can be obtained which has a spring characteristic (elastic characteristic) which is near the spring characteristic of the muscles of the buttocks or the like of the seated person. However, in such a structure, there are the problems that there is the sensation that the restoring force is insufficient and that the weight is heavy.
Thus, a seat has been conceived of in which, as the cushion material taking the place of urethane, a cushion structure is structured by stretching, over a seat frame, a pair of ground knit fabrics and a two-dimensional knit fabric or a three-dimensional solid knit fabric formed by connecting threads which are disposed between the ground fabrics (see, for example, Japanese Patent No. 5013089). The cushion material formed from this three-dimensional solid knit fabric or two-dimensional fabric is an elastic structure which is difficult to weaken, and is thinner than urethane, and exhibits an elastic characteristic in place of urethane.
However, in a conventional vehicle seat using such a three-dimensional solid knit fabric or two-dimensional fabric as the cushion material, the two-dimensional knit fabric is stretched over the seat frame at a tension such that the elongation is in the range of from 5% to 20%, and the three-dimensional solid knit fabric is stretched at a tension such that the elongation is less than 5%. Therefore, when a person sits down, large forces arise due to tension at the portions where the convex portions of the human body, such as the ischia, the coccyx, the shoulder blades and the like, contact the cushion material (clothes are ignored). Therefore, this becomes a cause of the supporting pressure becoming strong and a sensation that a foreign object exists arising. Further, if this acts over a long time period, there is the problem that pain arises in the muscles at the peripheries of the aforementioned ischia, coccyx, shoulder blades and the like. In particular, the muscles and the blood vessels in the peripheries beneath the ischial tuberosities, which support the majority of the body weight of the human body, are compressed, and there are cases in which pain or numbness due to interruption in blood circulation arises.
Further, in the above-described conventional seat, the two-dimensional knit fabric is stretched directly over the frame. Therefore, the problem is known that it is easy for there to arise a phenomenon, which is the so-called hammock sensation phenomenon, in which it is easy for the seated person to move in the front-rear and left-right directions within the frame, and due to the input of vibration at the time when the vehicle travels for example, the seated posture of the seated person changes or the seated person slides forward on the seat.


A user-generated graphical representation can be sent into a generative network to generate a synthetic image of an area including a road, the user-generated graphical representation including at least three different colors and each color from the at least three different colors representing a feature from a plurality of features. A determination can be made that a discrimination network fails to distinguish between the synthetic image and a sensor detected image. The synthetic image can be sent, in response to determining that the discrimination network fails to distinguish between the synthetic image and the sensor-detected image, into an object detector to generate a non-user-generated graphical representation. An objective function can be determined based on a comparison between the user-generated graphical representation and the non-user-generated graphical representation. A perception model can be trained using the synthetic image in response to determining that the objective function is within a predetermined acceptable range.

Images are sometimes used as training data for software models (e.g., a machine learning model). Images depicting certain scenarios, however, can be expensive and/or challenging to obtain. For example, a vehicle (e.g., an autonomous vehicle) may rely on a machine learning model(s) to perform autonomous driving. In such a scenario, it can be desirable for the machine learning model(s) to be trained/tested using images depicting various scenarios, including scenarios showing atypical scenes. Images depicting some scenarios (e.g., emergency situations, unusual road patterns, animals blocking roads, etc.), however, can be relatively more expensive and/or challenging to obtain compared to images depicting more common scenarios (e.g., non-emergency situations, typical road patterns, etc.). As such, a cost-effective and simple technique to generate images depicting specific scenarios can be desirable.

Navigating a vehicle based on data processing using synthetically generated images


A vapor chamber, in which a condensable fluid, which evaporates and condenses depending on a state of input and radiation of a heat, is encapsulated in a hollow and flat sealed receptacle as a liquid phase working fluid; and in which the wick for creating the capillary pressure by moistening by the working fluid is arranged in said sealed receptacle, comprising: a wick for creating a great capillary pressure by being moistened by said working fluid, which is arranged on the evaporating part side where the heat is input from outside; and a wick having a small flow resistance against the moistening working fluid, which is arranged on the condensing part side where the heat is radiated to outside.

1. Field of the Invention
The present invention relates to a heat pipe for transporting heat as latent heat of a working fluid or a condensable fluid, and relates especially to a vapor chamber in which a sealed receptacle is shaped into a tabular shape, i.e., a flat rectangular plate, and which is constructed to create a pumping force for refluxing a liquid phase working fluid to a portion where it evaporates, by means of a capillary pressure.
2. Discussion of the Related Art
In the customary way, a heat pipe for transporting heat in the form of latent heat of a working fluid is well known in the prior art. The heat pipe of this kind is a heat conducting element encapsulating a condensable fluid such as water in a sealed receptacle (container) after evacuating an air therefrom. Such a heat pipe is constructed to transport the heat as latent heat of a working fluid by evaporating the working fluid, with the heat input from outside, and by condensing a vapor by radiating the heat after the vapor flows to a condensing part of a low temperature and a low pressure. Accordingly, since the heat is transported in the form of latent heat of the working fluid, the heat pipe has more than ten times to several hundred times of heat transporting capacity in comparison with that of copper which is known to have the highest heat conductivity.
According to a heat pipe of this kind, the heat is transported by means of flowing the evaporated vapor phase working fluid to a condensing part in a low temperature and low pressure side, and, after the heat transportation, the condensed liquid phase working fluid is refluxed to the evaporating part (i.e., a heat inputting part) by the capillary pressure of a wick.
The wick is, in short, a member for creating a capillary pressure, and therefore, it is preferable that it be excellent in hydrophilicity with the working fluid, and it is preferable that its effective radius of a capillary tube as small as possible at a meniscus formed on a liquid surface of the liquid phase working fluid. Accordingly, a porous sintered compound or a bundle of extremely thin wires generally is employed as a wick. Among those wick members according to the prior art, the porous sintered compound may create great capillary pressure (i.e., a pumping force to the liquid phase working fluid) because the opening dimensions of its cavities are smaller than that of other wicks. Also, the porous sintered compound may be formed into a sheet shape so that it may be employed easily on a flat plate type heat pipe or the like, called a vapor chamber, which has been attracting attention in recent days. Accordingly, the porous sintered compound is a preferable wick material in light of those points of view.
The heat transporting characteristics of the heat pipe including the vapor chamber is thus improved as a result of an improvement of a wick material and so on, and miniaturization is also attempted in connection with this. At the same time, the cooling of a personal computer, a server, or a portable electronics device, which are enhanced in compactness and capacity, has been becoming a problem in recent days. The heat pipe has been garnering the attention as a means for solving this problem, and it has been employed more frequently. Examples of employing such downsized and thin-shaped heat pipe are disclosed in Japanese Patent Nos. 2,794,154 and 3,067,399, and Japanese Patent Laid-Open No. 2000-49266.
As described above, it is possible to increase the capillary pressure for refluxing the liquid phase working fluid if a porous body is employed as a wick to be built into the heat pipe. This is advantageous for downsizing the vapor chamber. However, a flow path is formed by the cavity created among the fine powders as the material of a porous body, so that the flow cross-sectional area of the flow path has to be small and as intricate as a maze. Therefore, it is possible to enhance the capillary pressure which functions as the pumping force for refluxing the liquid phase working fluid to a portion where it evaporates. However, on the other hand, there is a disadvantage because the flow resistance against the liquid phase working fluid is relatively high. For this reason, if the input amount of heat from outside increases suddenly and drastically, for example, the wick may dry out due to a shortage of the liquid phase working fluid to be fed to the portion where the evaporation of the working fluid takes place.

International Business Machines Corporation


One embodiment of the present invention is an organic electroluminescence element, including: an anode; a cathode; an organic light emitting medium layer including a buffer layer and an organic light emitting layer, the organic light emitting medium layer being between the anode and the cathode, and the buffer layer comprising at least two kinds of inorganic material.

1. Field of the Invention
The present invention is related to an organic electroluminescence (light emitting) element and a display having the element. In particular, the present invention is related to an organic electroluminescence element having an organic light emitting medium layer of a layered product structure comprised of a polymer compound and an inorganic compound and a display having the element.
2. Description of the Related Art
In organic electroluminescence (organic EL) elements, a voltage is applied to an electrically conductive organic light emitting medium layer, and thus electrons injected from a cathode and holes from an anode are allowed to recombine, whereby an organic light emitting material which makes up the organic light emitting layer is allowed to emit light upon this recombination. (Here, an organic light emitting layer with a hole transport layer, a hole injection layer, an electron transport layer or an electron injection layer is called an organic light emitting medium layer.) For extracting the light outside concurrently with applying the voltage to the organic light emitting layer, a construction including a first electrode and a second electrode placed on both sides of the organic light emitting medium layer is provided. This device is constructed by sequentially laminating the first electrode, the organic light emitting medium layer and the second electrode on a transparent board. In general, the first electrode formed on the board is used as an anode, while the second electrode formed on the organic light emitting medium layer is used as a cathode.
An exemplary organic light emitting medium layer may include copper phthalocyanine used as a hole injection layer, N,N′-di(1-naphthyl)-N,N′-diphenyl-1,1′-biphenyl-4,4′-diamine used as a hole transport layer, and tris(8-quinolinol) aluminum used as a luminescent layer, respectively. Furthermore, in an attempt to increase light emitting efficiency, the construction of an organic EL element is often made by providing the hole transport layer and the hole injection layer between the anode and the organic light emitting layer, or the electron transport layer and the electron injection layer between the organic light emitting layer and the cathode, which may be selected ad libitum. Any of the substances which constitute the organic light emitting medium layer and allow the layer to function (light emitting medium material) is a low molecular compound, each layer having a thickness of approximately 1 to 100 nm, and deposited by a vacuum evaporation method such as resistance heating.
To the contrary, there are polymer organic EL elements in which a polymer material is used as the organic light emitting medium layer. In the light emitting layer, a low molecular light-emitting material dissolved in a polymer such as polystyrene, polymethyl methacrylate or polyvinyl carbazole, as well as a polymer light emitter such as a polyphenylenevinylene derivative (PPV), a polyalkylfluorene derivative (PAF) or the like may be used. These polymer materials can be subjected to film formation by a wet method such as a coating method or a printing method through dissolving or dispersing in a solvent. Therefore, it is advantageous in that film production is enabled under an ambient air pressure with low equipment costs as compared to the organic EL element in which a low molecular material is used.
In the polymer organic EL element, a hole transport layer is generally provided for the purpose of lowering the voltage to be applied. In typical examples, film formation is carried out using a polymer material ink of a donating molecule and an accepting molecule aggregate which were dispersed in water. It is known that the hole transport layer shows superior charge injection properties. However, in a hole transport layer comprised of a polymer material, since the resistance of the film is high, the film is highly loaded in a high voltage region. Thereby the material itself deteriorates. Therefore, there is a problem in that luminance and electric current density are limited. In this way, the element using the hole transport layer comprised of a polymer material has a resistance problem and there are concern points such as deterioration of light emitting characteristics or reduced life-time.
In addition, it has been proposed that inorganic products such as an oxide, a nitride and an oxynitride of a transition metal, and a p-type compound semiconductor are used for a hole transport layer. In this case, more stable characteristics are obtained than in the case using a polymer material especially in the case of a high voltage and a high luminance region. However, an electron blocking layer comprised of a polymer material between a hole injection layer and a light emitting layer is necessary in order to achieve a high efficiency. (Patent Document 1)
Here, layers such as the above-mentioned hole transport layer, the hole injection layer and the electron blocking layer, the layers being between an electrode and an organic light emitting layer and the layer provided for improving characteristics, are called buffer layers.
Further, in general, the thickness of the electron blocking layer is thinner than the thickness of an organic light emitting medium layer so that an increase in the applied voltage is prevented. Especially, in the case where a display having pixels sectioned for a pixel is manufactured, there are many problems to be solved in order to realize a uniformity of films both inside and outside a pixel when a polymer material is used.
In view of the above-mentioned problems, the object of the present invention is to provide a buffer layer without ununiformity, and to further provide a polymer organic EL element having a high reliability by using a buffer layer having a good resistance and a high stability.
Hereinafter, a known related art is described.
[Patent Document 1] JP-A-2006-114759

Organic electroluminescence element and display using the same


A decorative adjustable fabric plant pot sleeve for covering various sized plant pots is provided in which a non-elastic fabric covering is integrated with an elastic lattice structure so as to provide an adjustable plant pot sleeve without sacrificing the quality of the fabric covering that is to be used.

Plant pots have been manufactured to be both waterproof and decorative. In many cases, it is desirable to attempt to match the appearance of a plant pot to its surroundings. In the case of house plants, home owners may find it very difficult to find a plant pot which matches their furniture upholstery, wall colors and/or general room appearance. While plant pots are manufactured in a host of solid colors and even a few patterns, it is not cost effective for manufacturers to produce plant pots in a multitude of decorative designs.
One possible way to match the appearance of a plant pot to its surroundings has been to cover the plant pot with a patterned fabric cover. However, this approach has had a significant drawback caused by the fact that pots are typically designed with holes to protect the plant from over watering. Thus, plant pots tend to routinely leak water and, hence, would tend to damage such fabric coverings.
Additionally, existing fabric covers suffer from being usable only with particular sized plant pots. That is, the fabric must be cut and sewn to fit a particular size, thereby limiting their usefulness in connection with varying sized plant pots.
Thus, there is a need for an adjustable fabric plant pot sleeve or cover usable in connection with a range of plant pot sizes, which optionally may be used in conjunction with a waterproof plant pot holder so as to minimize the adjustable fabric cover's exposure to water damage.


This invention relates to the antibiotic feglymycin, as well as processes for its preparation and use. Feglymycin is represented by the structural formula (SEQ ID NO:1): ##STR1##

The present invention relates to the novel antibiotic feglymycin, processes for its preparation and its use.
A large number of antibiotics have been employed therapeutically for the treatment of bacterial infectious diseases. The pathogens, however, are becoming increasingly resistant to the pharmaceuticals used, and there is even the threat of great danger due to so-called multiresistant bacteria, which have become resistant not only to individual groups of antibiotics, such as, for example, .beta.-lactam antibiotics or glycopeptides or macrolides, but simultaneously carry several resistances. There are even pathogens which have become resistant to all commercially available antibiotics, and infectious diseases which are caused by such bacteria can no longer be treated. There is therefore a great need for new agents which can be employed against resistant bacteria. Indeed, many thousands of antibiotics have been described in the literature, which, however, are mostly too toxic to be able to be employed as pharmaceuticals.
The development of resistance also presents a problem in the control of immunodeficiency, the so-called AIDS condition, which is caused by the new type of virus, the "human immunodeficiency virus" (HIV). There is still no medicament for curing an AIDS condition. The agents which have been employed until now can admittedly prolong the life expectancy of HIV-infected persons, but due to the formation of resistant viruses, medicine urgently needs novel, nontoxic virostatics.

Antibiotic, feglymycin, processes for its preparation and its use


A computer enclosure includes a case comprising a drive bracket housing a number of compact disc drives and a storage device module mounted in the drive bracket in the absence of installed disk drives. The storage device module includes a supporting frame fixed in the drive bracket, a backboard, and a number of data storage devices arranged in the supporting frame. The backboard provides connection of the data storage devices to a motherboard of the case.

1. Technical Field
The present disclosure relates to computer enclosures and, particularly, to a computer enclosure with a module receiving data storage devices.
2. Description of Related Art
A computer enclosure may include a drive bracket capable of housing three or more compact disc (CD) drives. However, more often than not, only one CD drive is installed, thus wasting space in the enclosure.

Computer enclosure and storage device module thereof

Hong Fu Jin Precision Industry (ShenZhen) Co., Ltd.


A system of fans ventilates heated air from within an IHS (Information Handling System), such as a rack-mounted server, when operated during normal conditions at a rated fan speed. A controller detects a failure of a fan of this fan system and identifies the functioning fans of the system. One or more of the functioning fans are selected for boosting by operation of a fan failure compensation circuit that has been configured for delivery of additional power to the selected boost fans. The fan failure compensation circuit delivers an output voltage that boost the airflow output of the system to compensate for the failed fan. By increasing the output voltage by approximately twenty percent, the boosted fans operate at approximately fifteen percent above rated speeds, which has been demonstrated to compensate for a failed fan while avoiding further failures during the expected lifespan of the fan system.

As the value and use of information continues to increase, individuals and businesses seek additional ways to process and store information. One option is an Information Handling System (IHS). An IHS generally processes, compiles, stores, and/or communicates information or data for business, personal, or other purposes. Because technology and information handling needs and requirements may vary between different applications, IHSs may also vary regarding what information is handled, how the information is handled, how much information is processed, stored, or communicated, and how quickly and efficiently the information may be processed, stored, or communicated. The variations in IHSs allow for IHSs to be general or configured for a specific user or specific use such as financial transaction processing, airline reservations, enterprise data storage, global communications, etc. In addition, IHSs may include a variety of hardware and software components that may be configured to process, store, and communicate information and may include one or more computer systems, data storage systems, and networking systems.
Components of an IHS consume electrical power and can generate significant amounts of heat. Heat within an IHS may degrade the reliability and performance of IHS components, possibly resulting in costly malfunctions and component failures. In order to dissipate generated heat, an IHS may include a cooling fan, or one or more sets of cooling fans that are organized and operated as an airflow cooling system. Data centers may house large numbers of IHSs, such as servers that are stacked and installed within racks. Supporting airflow cooling within a rack-mounted IHS that is installed within a data center is complicated by the constraints posed by the densely packed racks that are prevalent in data centers. As a result, the airflow cooling systems of such rack-mounted IHSs are specialized for operation within densely packed data center environments.


An autostereoscopic projection screen with projection displays a stereoscopic image for receiving parallax images of right eye and left eye. The autostereoscopic projection screen includes a polarization-reserved diffuser, a microretarder, a polarizer, and a parallax element. Parallax images of right eye and left eye pass through the polarization-reserved diffuser and the microretarder for transferring their polarization states. Parallax images of right eye and left eye with specific polarization states will pass the polarizer and parallax element for dividing images of right eye and left eye from parallax images. The individual images separately enter viewing zones of right eye and left eye to generate the stereoscopic-image for viewers.

1. Field of Invention
The invention relates to an autostereoscopic screen and, in particular, to an autostereoscopic projection screen.
2. Related Art
The 3D display technology is considered the most research direction after planarization of the displays. The 3D visual effect is to enable a viewer to perceive from a two-dimensional source three-dimensional images as in daily life, i.e. perceiving depths and levels of objects. To display a 3D image, one has to provide two sets of overlapped images in one screen to simulate what two eyes perceive. The two eyes then receive the two sets of images via polarized glasses or gratings. However, the use of polarized glasses brings a lot of inconvenience in practice. To improve the image quality and to achieve the 3D display for naked eyes, many autostereoscopic screens have been invented to directly transmit two sets of images to the left and right eyes separately.
There are many ways to implement a stereoscopic display. A normal stereoscopic projection display uses two projectors to simultaneously provide two sets of images for the left and right eyes, respectively. The images are projected onto a screen with a Fresnel lens that has planar converging power. The action of the Fresnel lens is to deflect tilted incident light from the projector to be perpendicular to the screen. This prevents light from having different incident angles at different positions on the screen; otherwise, it may result in "hot spots" that are bright in the center but dark at the boundary. The two sets of images are then separately guided to the left and right eyes of the viewer to form a 3D image. However, this type of projection equipment does not have a good image quality. Moreover, the size of the structure is large. It is not easy to make a large-size projection screen and may involve a higher cost.
A double lenticular screen in the autostereoscopic projection screen can produce 3D effects too. In this case, both sides of a light diffuser are connected with a lenticular screen. Two projectors simultaneously transmit two sets of images for the left and right eyes, respectively. The image for the left eye passes through the double lenticular screen and enters completely into the left eye. Likewise, the image for the right eye has to be projected only to the right eye of the viewer. To achieve this effect, one had to impose a very stringent requirement on the double lenticular screen. The lenticular screens on both sides have to be completely symmetric. It takes a higher cost and difficult manufacturing process to achieve such a precision.

Industrial Technology Research Institute


Provided is a semiconductor integrated circuit including: a differential driver that is disposed between a first power supply and a second power supply and drives differential input signals to generate differential output signals; and a control signal generation circuit that generates a first control signal for controlling a voltage level of each of the differential output signals. When each of a pair of output signals forming the differential output signals is changed from a voltage level corresponding to the first power supply to a voltage level corresponding to the second power supply, an amount of change in the voltage level of the corresponding output signal is controlled based on the first power supply.

1. Field of the Invention
The present invention relates to a semiconductor integrated circuit, and more particularly, to a driver circuit including a slew rate control circuit.
2. Description of Related Art
USB (Universal Serial Bus) interfaces are used with a wide range of peripheral devices. Examples of standard peripheral devices using USB interfaces include a mouse, a keyboard, a disk drive, a printer, and audio/video equipment.
In order to transfer highly reliable information through a USB interface, it is important to improve the quality of the waveform of signals to be transmitted to and received from a transceiver. When communications are conducted at full speed and low speed, for example, even if a power supply voltage for driving the transceiver fluctuates in a range of 3.0 V to 3.6 V, a voltage level at which a pair of differential output signals to be transmitted and received cross each other (hereinafter, referred to as "crossover voltage") is required to meet specifications in a range of 1.3 V to 2.0 V.
FIG. 5 is a circuit configuration diagram showing a differential driver 4 and a constant current source TD for driving the differential driver 4, which is disclosed in Japanese Unexamined Patent Application Publication No. 2003-309460. The constant current source TD includes a constant current circuit TD1 and constant current transistors TrD1 to TrD4. The differential driver 4 includes drivers 4a and 4b. The drivers 4a and 4b output signals with inverted phases. Specifically, the differential driver 4 outputs differential input signals, which are received at input terminals DIN and DINB, as differential output signals from output terminals D+ and D− through the drivers 4a and 4b.
The circuit configuration of the driver 4a provided in the differential driver 4 will now be described. The driver 4a includes transistors MP1 to MP4 which are P-channel MOS transistors, transistors MN1 to MN4 which are N-channel MOS transistors, and capacitors C1 and C2 which are mirror capacitors.
One end of the transistor MP1 is supplied with a power supply voltage VDD. The diode-connected transistor MP2 is disposed between another end of the transistor MP1 and one end of the transistor MN1.
The one end of the transistor MN1 is also connected to the gate of the transistor MP4 and one end of the capacitor C1. A reference potential VSS is applied to another end of the transistor MN1 through the constant current transistor TrD1. Further, the power supply voltage VDD is applied to one end of the transistor MP3 through the constant current transistor TrD2. The diode-connected transistor MN2 is disposed between another end of the transistor MP3 and one end of the transistor MN3.
The another end of the transistor MP3 is also connected to one end of the capacitor C2 and the gate of the transistor MN4. The reference potential VSS is applied to another end of the transistor MN3. The gates of the transistors MP1, MN1, MP3, and MN3 are connected together to receive a single end signal through the input terminal DIN.
The power supply voltage VDD is applied to one end of the transistor MP4. Another end of the transistor MP4 is connected to one end of the transistor MN4, another end of the capacitor C1, and another end of the capacitor C2. The reference potential VSS is applied to another end of the transistor MN4. In this case, the transistor MP4 and the transistor MN4 constitute an output circuit. That is, an output signal from the output circuit corresponds to an output signal of the driver 4a.
As described above, the constant current source TD includes the constant current circuit TD1, which generates a predetermined constant current, and the constant current transistors TrD1 to TrD4. The constant current generated by the constant current circuit TD1 is applied to the gates of the constant current transistors TrD1 to TrD4. Thus, the constant current transistors TrD1 to TrD4 are driven.
As described above, the driver 4a includes the transistors MP1 to MP4, the transistors MN1 to MN4, and the capacitors C1 and C2. Meanwhile, the driver 4b includes transistors MP5 to MP8 which are P-channel MOS transistors, transistors MN5 to MN8 which are N-channel MOS transistors, and capacitors C3 and C4 which are mirror capacitors. The connection configuration of the driver 4b is the same as that of the driver 4a, so the description thereof is omitted.
As shown in FIG. 5, the driver 4a has a circuit configuration including the constant current transistors TrD1 and TrD2. As with the driver 4a, the driver 4b has a circuit configuration including the constant current transistors TrD3 and TrD4.
The constant current circuit TD1 includes transistors MP9, MP10, and MP14 which are P-channel MOS transistors, and a transistor MN9 which is an N-channel MOS transistor. The transistor MP9 and the transistor MP10 constitute a current mirror circuit. The source of the transistor MP9 and the source of the transistor MP10 are each connected to the power supply voltage VDD. The drain of the transistor MP9 is connected to the gate of the transistor MP9, the gate of the transistor MP10, the source of the transistor MP14, the gate of the constant current transistor TrD2, and the gate of the constant current transistor TrD4. The drain of the transistor MP14 is connected to the gate of the transistor MP14, the source of the transistor MN9, and the reference potential VSS. The drain of the transistor MP10 is connected to the drain and gate of the transistor MN9, the gate of the constant current transistor TrD1, and the gate of the constant current transistor TrD3.
An output current of the transistor MP10 is supplied to the transistor MN9. The transistor MP9 forms a current mirror circuit with the constant current transistor TrD2 and the constant current transistor TrD4. The transistor MN9 forms a current mirror circuit with the constant current transistor TrD1 and the constant current transistor TrD3. Thus, a current generated in the constant current circuit TD1 is supplied to the driver 4a and the driver 4b.
In the case of the circuit shown in FIG. 5, however, the crossover voltage of the differential output signals (i.e., output signals from the output terminals D+ and D−) fluctuates depending on the power supply voltage VDD. That is, if the power supply voltage VDD fluctuates for some reason, a fluctuation range of the crossover voltage may not meet the design specifications such as the USB specification. Note that Japanese Unexamined Patent Application Publication No. 2003-309460 fails to disclose a variation in the crossover voltage due to a variation in the power supply voltage VDD.
The reason why the above problem arises will be described below. First, a description is given of the case where an input signal DIN of the driver 4a shown in FIG. 5 changes from H level to L level. It is assumed that a drive current flowing through the constant current transistor TrD2 is denoted by i15 and the feedback capacitance of the capacitor C2 is denoted by C2. In this case, the drive current i15 flows to cause electric charges to be stored in the capacitor C2, thereby controlling a voltage Vdp of an output signal D+. That is, the voltage Vdp can be represented by the following expression (1).Vdp=−(1/C2)∫i15dt  (1)Accordingly, the output signal D+ changes from H level to L level.
Next, a description is given of the case where the input signal DIN changes from L level to H level. It is assumed that a drive current flowing through the constant current transistor TrD1 is denoted by i14 and the feedback capacitance of the capacitor C1 is denoted by C1. In this case, the drive current i14 flows to cause the electric charges accumulated in the capacitor C1 to be discharged, thereby controlling the voltage Vdp of the output signal D+. Thus, the output signal D+ changes from L level to H level. Since the driver 4b has the same circuit configuration as the driver 4a, the output signal D+ of the driver 4a has a phase opposite to that of an output signal D− of the driver 4b.
It is assumed herein that the ON-resistance of the transistor MP14 is denoted by RP14 and the gate-source voltage of the transistor MP9 is denoted by Vgs9. In this case, a current i18 flowing between the source and drain of the transistor MP14 can be represented by the following expression (2).i18=(VDD−Vgs9)/RP14  (2)
Note that the current i18 serves as a reference current of the current mirror circuit which is formed of the transistors MP9 and MP10 and the constant current transistors TrD2 and TrD4. Specifically, the current i15 corresponding to the current i18 flows through the constant current transistor TrD2 as a drive current of a predriver 4c. Further, a current i17 corresponding to the current i18 flows through the constant current transistor TrD4 as a drive current of a predriver 4d.
The output current of the transistor MP10 serves as a reference current of the current mirror circuit which is formed of the transistor MN9 and the constant current transistors TrD1 and TrD3. Specifically, the current i14 corresponding to the output current of the transistor MP10 flows through the constant current transistor TrD1 as the drive current of the predriver 4c. Further, a current i16 corresponding the output current of the transistor MP10 flows through the constant current transistor TrD3 as the drive current i16 of the predriver 4d.
In this case, when the power supply voltage VDD is high, the drive currents i14 to i17 increase. That is, the drive currents of the predrivers 4c and 4d increase. As a result, a slew rate (gradient of a signal waveform) of each of the output signals D+ and D− increases. Meanwhile, when the power supply voltage VDD is low, the drive currents i14 to i17 decrease. As a result, the slew rate of each of the output signals D+ and D− decreases.
Assuming that the capacitors C1 to C4, which are provided in the drivers 4a and 4b, the transistors MP1 to MP8, and the transistors MN1 to MN8 have the same characteristics, respectively, and that the drive currents i14 to i17 have the same current value, for example, the rise (rising edge) and fall (falling edge) of the output signal D+ have the same gradient. Similarly, the rise and fall of the output signal D− have the same gradient. This is because the drive currents are supplied through the same current path even when the power supply voltage VDD fluctuates. In this circuit configuration, the crossover voltage is high when the power supply voltage VDD is high, while the crossover voltage is low when the power supply voltage VDD is low. This poses a problem that, if the power supply voltage VDD fluctuates for some reason, the fluctuation range of the crossover voltage may not meet the design specifications such as the USB specification.


A trailing arm bush may include a cylindrical outer pipe, an inner pipe inserted to a central portion of the outer pipe at an interval, a first bush rubber unit, a second bush rubber unit and a third bush rubber unit that connect between an inner peripheral surface of the outer pipe and an outer peripheral surface of the inner pipe, respectively, a hollow void part formed between the inner peripheral surface of the outer pipe and the outer peripheral surface of the inner pipe, and a stopper attached to the inner peripheral surface of the outer pipe and disposed among the first bush rubber unit, the second bush rubber unit and the third bush rubber unit.

Field of the Invention
The present invention relates to a trailing arm bush for CTBA that connects between a pair of trailing arms supported by a torsion beam disposed in a vehicle width direction and a vehicle body, and more particularly, to a trailing arm bush for CTBA in which by forming three bush rubber units for connecting between an inner peripheral surface of an outer pipe and an outer peripheral surface of the inner pipe, a bush rubber unit can have characteristics of a non-linear spring when the inner pipe moves back and forth by external vibration of the vehicle, and a gap between the inner pipe and a stopper is secured to significantly improve an abnormal noise generation phenomenon.
Description of Related Art
In general, a suspension system of the vehicle is constituted by various devices for improving the riding comfort of the vehicle, such as, a chassis spring that connects an axle and a vehicle body to alleviate impact receiving from a road surface during running, a shock absorber for absorbing a free vibration of the spring, and a stabilizer for preventing the vehicle from rolling from side to side.
Such a suspension system is classified into a front wheel suspension system and a rear wheel suspension system depending on mounting parts of the vehicle, and is classified into an integral axle suspension type in which left and right wheels are connected to each other by one axle, and an independent suspension type that is connected to the left and right wheels so as to be independently operable.
Since the independent suspension type is able to lighten the lower weight of the spring and lower the bottom of the vehicle body, riding comfort is good, and grounding characteristics and steering stability are excellent. Thus, it is mainly widely used in passenger cars or the like.
Meanwhile, in recent years, as the suspension systems of medium and small-sized cars, application of a Coupled Torsion Beam Axle (CTBA) type suspension system which has a simple structure, can be reduced in weight, has the small number of required components, and has excellent workability has expanded.
Generally, the CTBA type suspension system is a type of a torsion beam axle, and is called a twist beam suspension or a coupled link.
Such a CTBA type suspension system is constituted by a trailing arm which is treated as a rigid link and on which all the parts are mounted, a torsion beam that mainly controls the effect on the rolling behavior of a vehicle and serves to restrain the movement of the trailing arm relative to roll stiffness and left and right lateral force, and a trailing arm bush for CTBA that alleviates the vibration and shock from the ground surface.
The CTBA type suspension system having such a configuration is characterized in that there are two supporting points connected to the vehicle body smaller than other suspension systems, but directions of the input load are diverse, and values of relatively large sizes are input.
Therefore, there are great changes in performance of the vehicle depending on the performance of the trailing arm bush for CTBA, and the trailing arm bush for CTBA will occupy an important role in terms of riding comfort and driving stability of the vehicle.
As shown in FIGS. 1 and 2, the structure of the trailing arm bush for CTBA according to the related art has a form in which a bush rubber unit 3 and a void part 4 are provided between the outer pipe 1 and the inner pipe 2, and a stopper 5 is attached to the inner peripheral surface of the outer pipe 1.
As shown in FIG. 1, a so-called two-bridge type trailing arm bush for CTBA configured to connect two parts between the outer pipe 1 and the inner pipe 2 has good characteristics in terms of handling of the vehicle and durability of the bush, but there is a disadvantage in that riding comfort of the vehicle is lowered to induce Impact harshness.
Meanwhile, as shown in FIG. 2, a so-called four-bridge type trailing arm bush for CTBA configured to connect four parts between the outer pipe 1 and the inner pipe 2 has an advantage in that the riding comfort is excellent as compared to the two-bridge type, but has a disadvantage in terms of handling of the vehicle and durability of the bush.
That is, since handling and riding comfort of the vehicle are inversely proportional to the trailing arm bush for CTBA, there is a need for trade-off between two characteristics at the time of actual design, but there is a problem in that it is very difficult to optimize the trailing arm bush for CTBA while satisfying both two characteristics.
Thus, there are problems such as prolonged development period and consumption of extra development costs due to the extra number of tests, when developing a trailing arm bush for CTBA depending on the design of the conventional trailing arm bush for CTBA.
Furthermore, as shown in FIG. 2, since the conventional trailing arm bush for CTBA is primarily designed so that a very small gap 6 of 0.5 mm is formed between the stopper 5 and the inner pipe 2, and the four-bridge type trailing arm bush for CTBA has the spring characteristics of the six-bridge type, there is a problem in that a lot of abnormal noises occur.
The information disclosed in this Background of the Invention section is only for enhancement of understanding of the general background of the invention and should not be taken as an acknowledgement or any form of suggestion that this information forms the prior art already known to a person skilled in the art.

Trailing arm bush for coupled torsion beam axle