A method for manufacturing a SOI wafer, including a step of performing a thickness reducing adjustment to a SOI layer of the SOI wafer by carrying out a sacrificial oxidation to the SOI wafer for effecting thermal oxidation to a surface of the SOI layer and removing a formed thermal oxide film, wherein, when the thermal oxidation in the sacrificial oxidation treatment is carried out with the use of a batch processing heat treatment furnace during the rising of a temperature and/or the falling of a temperature, a substantially concentric oxide film thickness distribution is formed on the surface of the SOI layer. The result is a method for manufacturing a SOI wafer that enables manufacturing a SOI wafer that has improved radial film thickness distribution with good productivity by performing the sacrificial oxidation treatment for forming a substantially concentric oxide film and removing the formed thermal oxide film.

In recent years, as a method for manufacturing an SOI wafer, a method for manufacturing an SOI wafer by bonding an ion-implanted bond wafer and then delaminating the same (an ion implantation delamination method: a technology that is also called a smart cut method (a registered trademark)) has newly begun to attract attention. This ion implantation delamination method is a technology for, e.g., forming an oxide film (an insulator film) on at least one of two wafers, implanting gas ions such as hydrogen ions or rare gas ions from an upper surface of one silicon wafer (a bond wafer), forming a micro bubble layer (a sealed layer) in the wafer, then adhering the ion implanted surface to the other silicon wafer (a base wafer) through the oxide film, subsequently applying a heat treatment (a delamination heat treatment) to delaminate one wafer (the bond wafer) into a thin film form with the use of the micro bubble layer as a cleavage surface, and further applying a heat treatment (a bonding heat treatment) to achieve firm bonding, thereby providing an SOI wafer (see Patent Literature 1). According to this method, the cleavage surface (a delamination surface) is an excellent mirror surface, and the SOI wafer having high film thickness uniformity of an SOI layer can be relatively easily obtained.
However, in case of fabricating an SOI wafer based on the ion implantation delamination method, a damage layer formed due to the ion implantation is present on a surface of the SOI wafer after the delamination, and surface roughness is considerable as compared with a mirror surface of a regular product level silicon wafer. Therefore, according to the ion implantation delamination method, it is necessary to remove such a damage layer and the surface roughness.
In the prior art, to remove this damage layer and others, mirror polishing (a stock removal: approximately 100 nm) with a very small stock removal that is called touch polishing is carried out in a final process after the bonding heat treatment.
However, when polishing including a machining element is performed with respect to the SOI layer, since the stock removal of the polishing is not uniform, there occurs a problem that film thickness uniformity of the SOI layer achieved by implantation and delamination of hydrogen ions and others is deteriorated.
As a method for solving such a problem, there has been carried a flattening treatment for performing a high-temperature heat treatment in place of the touch polishing to improve surface roughness.
For example, Patent Literature 2 suggests adding a heat treatment (a rapid heating/rapid cooling heat treatment (an PTA treatment)) in a reducing atmosphere containing hydrogen without polishing a surface of an SOI layer after a delamination heat treatment (or a bonding heat treatment). Further, Patent Literature 3 suggests forming an oxide film on an SOI layer by a heat treatment in an oxidizing atmosphere after the delamination heat treatment (or the bonding heat treatment), then removing the oxide film, and subsequently adding a heat treatment (the rapid heating/rapid cooling heat treatment (the RTA treatment)) in a reducing atmosphere.
Furthermore, in Patent Literature 4, a sacrificial oxidation treatment is performed with respect to a delaminated SOI wafer after a flattening heat treatment in an inert gas, a hydrogen gas, or a mixed gas atmosphere containing these gases, whereby flattening of a cleavage surface and avoidance of OSFs can be achieved at the same time.
As described above, since the high-temperature heat treatment is carried out in place of the touch polishing and the flattening treatment for improving the surface roughness is effected, SOI wafers each having a diameter of 300 mm and excellent film thickness uniformity that a film thickness Range (a value obtained by subtracting a minimum value from a maximum value in a radial direction) of each SOI layer is within 3 nm can be obtained in a high-volume production level by the ion implantation delamination method.


In a radio system which operates using code division multiplex (CDMA) the interference in the training sequences, for example interblock sequences, of all the K subscribers in the received signal is overcome before data detection at the receiving end. The interference in the training sequences of all K subscribers is modeled using the estimated channel pulse responses and, finally, is subtracted from the received signal. The method and apparatus can be used in CDMA mobile radio systems, in particular with joint detection.

The present invention relates to a method for radio transmission of digital signals, as well as, a system for radio transmission of digital signals.
A digital telecommunications system using burst transmission and code division multiplex has already been disclosed in German reference DE 43 29 317 A1. Digital mobile radio may be regarded, in particular, as an application for such a telecommunications system. In mobile radio systems, a multiplicity of mobile subscribers access the radio channel transmission medium. The multiple access problem resulting from this can be solved using the elementary multiple access methods "frequency division multiplex" (Frequency Division Multiple Access, FDMA), "time division multiplex" (Time Division Multiple Access, TDMA) or "code division multiplex" (Code Division Multiple Access, CDMA), or using combinations of these methods. In CDMA mobile radio systems, a plurality of subscribers transmit in the same frequency band at the same time. For this reason, the entire received signal is governed by the elements from a plurality of subscribers. The various subscriber signals can be separated, and the data transmitted by the individual subscribers determined, by the use of optimal estimation algorithms. In order that the said estimation algorithms can be used, it is necessary for the channel pulse responses of the radio channels of the individual subscribers to be known. As a rule, it is made possible for the receiver to obtain this information by overlaying into the transmitted signals signal sections which have been agreed in advance with the receiver and are thus known in the receiver, so that the receiver determines the channel pulse responses from the response of the channel to these known signal sections. The overlaid signal sections for determining the channel pulse responses are called training sequences. It is assumed that the signal transmission takes place in blocks, a transmitted block being called a burst. Such a burst is in each case composed, for example, of a training sequence in the form of a specific interblock sequence for channel estimation and of two data blocks which surround this interblock sequence. The burst can also be composed of in each case one training sequence in the form of a specific preamble for channel estimation and a data block which follows this preamble. Alternatively, a burst may in each case be composed, for example, of a training sequence in the form of a specific postscript to the channel estimation and of a data block which precedes this postscript. The training sequence can also be of any other nature within a burst.
Symbol interference can occur in the received signal as a result of components of the training sequences, that is to say there are values of the received signal which are governed both by data symbols and by the training sequences. This interference which is caused by training sequence components is produced, for example, when using an interblock sequence as the training sequence at the end of the data block which is in each case transmitted in a burst before the interblock sequence, and at the start of the data block which is in each case transmitted in a burst after the interblock sequence. This interference leads to a coded bit error rate of more than 10.sup.-2 in the subsequent data detection, even when a high signal-to-noise ratio is present.

Method and system for radio transmission of digital signals


A circuit for measuring the duration of a cut-off period in the power supply to an electronic system, for example the control system of a motor vehicle starter, comprises a voltage splitting bridge and a processing unit receiving the output of the splitting bridge. The bridge supply voltage is derived from the power supply to the electronic system, and the bridge has a branch which includes a temperature variable resistor. The processing unit determines the duration of the cut-off period as a function of the value of the output voltage from the splitting bridge at the end of a cut-off period.

Such a circuit has particular advantages when applied in apparatus for controlling the power supply to the electric motors of motor vehicle starters. Conventionally, such a control device controls the cut-off of the power supply of the electric motor of a starter once the heat engine of the vehicle has been started, or, in the case of failure to start, at the end of a predetermined period of time, so as to avoid any damage to the vehicle engine or an undue drain on the battery.
When the driver of the vehicle, having operated the ignition key, without success, turns it afresh to attempt once again to start the engine, it is desirable that the control device should prevent the starter from being supplied with power if this fresh attempt to start is made too soon. The control device must then include means which enable it to determine, when it is supplied with power again by closing of the contact by the driver, how much time has elapsed between interruption of the starter power supply and the new attempt to start.
The absence of power supplied to the control device during this dead period makes it impossible to provide an internal timer for this purpose in the control device.
Circuits known up to this time for the purpose of measuring the cut-off time of a circuit are generally RC type circuits, the capacitor of which charges when the circuit is supplied with power and discharges when the supply is cut off. When the circuit is once more energized, the measurement of the voltage across the capacitor of the circuit enables a value of the cut-off time to be determined. However, this type of circuit is severely limited as to the lengths of time which it can determine. At best, it only enables determination of time periods of the order of a fraction of a second, because of the leakage currents. In particular, the temperature stability of this type of circuit is not satisfactory, as the leakage currents are very high at high temperatures.
Equally, these RC circuits make it necessary to provide components having high values of capacitance and resistance, the values of which are such as to prevent them from being mounted within the starter casing.

Circuit for measuring the cut-off time of an electronic system


A flammable tube has a plurality of air passages formed along the length of the flammable tube. A support member is positioned in an interior of the flammable tube. The support member is spaced apart from the lower end of the flammable tube. Solid fuel is positioned on the support member. A flame is introduced to the solid fuel which is within the interior of the tube which ignites the solid fuel, such as charcoal. The charcoal burns away the flammable tube and the support member. The flammable tube may be placed within a grill of the type used to cook food or other container that is nonflammable, and which provides a receptacle for the burning solid fuel without the need of a specialized grilling apparatus.

Solid fuels such as charcoal may be ignited and used as sources for heat. Commonly, charcoal is used for cooking food. The solid fuel is ignited, and food is placed over the fuel which provides heat for cooking food. Charcoal and other solid fuels may also be used as a heat source for other purposes, including heating for living spaces.
Charcoal and other solid carbon based fuels are frequently messy to handle. There is a need for a package for charcoal and other solid fuels that is convenient and provides an easy way to ignite the solid fuel, but does not require physical handling of the solid fuel.


The invention relates to an apparatus for generating proofs of print signatures composed of first and second flats printed on opposite sides of a sheet comprises first and second digital printing units; a feeder mechanism for feeding a substrate having opposite sides to the first printing unit; a first input for feeding to the first printing unit digital data representative of an image of the first flat to imprint one side of the substrate with the image of the first flat; a marker for providing the substrate with a registration mark at a predetermined location on the substrate; a conveyor for conveying the imprinted substrate from the first printing unit to the second printing unit and feeding same thereto; and a mark sensor for detecting the location of the registration mark on the substrate and causing actuation of the second printing unit. The apparatus of the invention further includes a second input for feeding to the second printing unit digital data representative of an image of the second flat to imprint the other side of the substrate with the image of the second flat positioned with respect to the detected location of the registration mark such that the image of the second flat registers with the image of the first flat, thereby obtaining a proof of a print signature; and an outlet for discharging the proof of print signature from the second printing unit. Such an apparatus enables one to avoid generating films from the digital data representative of both flats and preparing a proof from such films.

The present invention pertains to improvements in the field of offset lithography. More particularly, the invention is concerned with an apparatus for generating proofs of print signatures.
The process of offset printing from digitally generated information requires many steps that result in composite images and text on film. This film is used to make offset printing plates. The plates are then mounted on a printing press to produce multiple impressions on paper. Prior to committing the result of such a complex process to the press, that is to commence printing thousands of impressions, it is necessary to make one impression as a proof for obtaining approval of the customer prior to printing.
Printers print multiple page images on both sides of a large sheet of paper. Such a printed sheet is called a print signature. A single printed side, on the other hand, is called a flat. Thus, a print signature is composed of two flats printed on opposite sides of a sheet. The page images on each flat are positioned in a manner such that they are in the correct sequence after folding the print signature. The proof that a printer requires must have is the proof of the print signature.
Proofs of print signatures are prepared from the films, and if corrections have to be made, new films incorporating the necessary corrections have to be generated again. This results in extra manpower and cost of generating new films and new proofs for each and every iteration.
Technology has made it possible to generate offset printing plates directly without the intermediate steps of generating a film and then the plate from the film. This makes it impossible to generate proofs prior to printing. As most printers are unwilling to print without obtaining the approval of a proof by their customer, they are unable to use such a new technology.

Method of generating proofs of print signatures


A current is provided from a power source to a load through a pass circuit that is series coupled to a sense resistor. A current trip-point detection circuit is arranged to detect a change in the current that is provided to a load. The current trip-point detection circuit includes at least two resistors that are series coupled from the sense resistor to a current source. A comparator compares a sense voltage to a tap-point between the two resistors such that the comparator asserts a trip-point detection signal when the current to the load reaches a predetermined threshold. The sense voltage can correspond to the voltage across the load or some other voltage that is proportional to the voltage across the load. The circuit arrangement has a simplified design that sets the trip-point as a percentage of the maximum output current. The current level trip-point can be temperature compensated.

Demand for portable electronic devices is increasing each year. Example portable electronic devices include: laptop computers, personal data assistants (PDAs), cellular telephones, and electronic pagers. Portable electronic devices place high importance on total weight, size, and battery life for the devices.
Most portable electronic devices employ rechargeable batteries. Commonly used rechargeable batteries include Nickel-Cadmium (NiCad), Nickel-Metal-Hydride (NiMHi), Lithium-Ion (Li-Ion), and Lithium-Polymer based technologies. Charger circuits are commonly available for each of these types of battery technologies.
Example battery charger circuits typically have two operating modes: a constant current mode, and a constant voltage mode. In the constant current mode, a charging current (I) is delivered to the battery (or load) via a regulator that maintains a regulated charging current. As the voltage level of the battery approaches the desired final voltage, the circuit switches to a constant voltage operating mode. In the constant voltage mode, the output voltage is regulated while a trip-point detection circuit monitors the charging current that is delivered to the battery. The trip-point detection circuit initiates a trip point signal when the charging current indicates that the battery has reached a fully charged state (e.g., 10% of the maximum charging current in the constant voltage mode).
FIG. 6 is an illustration of a conventional trip-point detection circuit (600). Trip-point detection circuit 600 includes two amplifiers (AMP1, AMP2), a comparator (CMP), three resistors (R601, R601, and RSNS), a resistor ladder, and a transistor (MP). Amplifier AMP1 evaluates the voltage drop across resistors RSNS and R601, and includes a trim adjustment control (TRIM) for adjusting the offset in the amplifier. Transistor MP is responsive to the output of amplifier AMP1 such that the current through resistor R602 is responsive to changes in the output current level (IOUT). Amplifier AMP2 receives a reference voltage (VREF) and is arranged in a feedback loop with the resistor ladder to provide an adjustable comparison level (VTRIP). The resistor ladder is configured with trimming adjustments (TRIM LEVEL) to accommodate for process related inaccuracies in the ladder network, as well as a trip level selection (TRIP LEVEL) to change the comparison level (VTRIP). Comparator CMP compares VTRIP to the voltage across resistor R602, which is related to the output current level (IOUT), and asserts the trip signal when the output current level drops below a predetermined level set by VTRIP.


A cue light device may comprise one or more connection interfaces configured for electrical coupling to a video switcher via a cable; a microcontroller configured to obtain and analyze data from the video switcher via the cable and the one or more connection interfaces; a multi-position switch configured to selectively permit a segment of the data to be processed by the microcontroller; and a light source electrically coupled to the microcontroller and configured to selectively illuminate based on a configuration of the multi-position switch.

During live events, when multiple devices having potential source displays (e.g., for broadcasting, presenting, or streaming) are present, it may be difficult to know which device is currently "live," or being presented to an audience. Additionally, operators of the devices may need to make last minute changes or adjustments to presentation materials during the live events, and it is imperative that the operators make these changes or adjustments on devices when the devices are not in operation so the ongoing events are not interrupted.
The present disclosure is directed to addressing one or more of the above-referenced challenges. Unless otherwise indicated herein, the materials described in this section are not prior art to the claims in this application and are not admitted to be prior art, or suggestions of the prior art, by inclusion in this section. This section is for the purpose of generally presenting the context of the disclosure.

Methods and systems for controlling a light source of a cue light device


A zoom lens having, in order from an object side to an image side, a first lens unit of negative refractive power, a second lens unit of positive refractive power and a third lens unit of negative refractive power, the first lens unit and the second lens unit being axially moved to effect zooming, wherein the first lens unit comprises, in order from the object side to the image side, a positive first lens, a negative second lens of meniscus form having a strong concave surface facing the image side, a negative third lens of bi-concave form and a positive fourth lens of meniscus form having a convex surface facing the object side, and the third lens unit comprises, in order from the object side to the image side, a negative first lens of bi-concave form and a positive second lens, and wherein the zoom lens satisfies the following conditions: EQU 0.8<.beta..sub.2W .multidot..beta..sub.2T <1.2 EQU 0.45<.vertline.f.sub.1 .vertline./f.sub.T <0.59 EQU 0.37<f.sub.2 /f.sub.T <0.43. where .beta..sub.2W is an image magnification of the second lens unit in a wide-angle end, .beta..sub.2T is an image magnification of the second lens unit in a telephoto end, f.sub.T is a focal length of the zoom lens in the telephoto end, f.sub.1 is a focal length of the first lens unit, and f.sub.2 is a focal length of the second lens unit.

1. Field of the Invention
This invention relates to zoom lenses and, more particularly, to zoom lenses having a high optical performance throughout the entire zooming range suited to photographic cameras or video cameras. Still more particularly, it relates to wide-angle zoom lenses of the negative-lens-unit lead type having three lens units with a relatively high range or a zoom ratio of about 2.5 to 3, while shortening the total length of the entire lens system to a compact form.
2. Description of Related Art
It has been known to provide a method of improving the compact form of the lens system by assuring a shortening of the total length of the entire lens system and a reduction of the diameter of the outer lens barrel. Zoom lenses for photography which employ such a method are disclosed in, for example, Japanese Laid-Open Patent Applications Nos. Hei 4-19706, Hei 5-127084 and Hei 7-77655.
Any of these zoom lenses is constructed with three lens units in total, comprising, in order from the object side, a first lens unit of negative refractive power, a second lens unit of positive refractive power and a third lens unit of negative refractive power. The first and second lens units are made movable for varying the focal length of the entire lens system.
Of these zoom lenses, the ones disclosed in Japanese Laid-Open Patent applications Nos. Hei 4-19706 and Hei 5-127084 have their ranges in a zoom ratio of about 2 strong, and, therefore, cannot be said to be the high range zoom lens. With the lens configuration remaining unchanged, when the range is extended, a great increase of the total length of the entire lens system results, so that a compact zoom lens could not be obtained.
Meanwhile, the one disclosed in Japanese Laid-Open Patent Application No. Hei 7-77655 has as high a range as about 3, while still shortening the total length to a compact form. However, the rules of lens design are not satisfactory. Therefore, this zoom lens cannot be said to have good enough optical performance.


Described herein is a multi-color radiation detector that comprises a mesa-type multi-layered mercury-cadmium-telluride detector structure monolithically integrated on a substrate. The detector is responsive to three or more discrete wavelength ranges and means is provided whereby each of the wavelength ranges can be detected independently or in combination with others of the ranges.

High performance, infrared photon detectors are commonly made from the narrow bandgap semiconductor mercury-cadmium-telluride (HgCdTe) which generates electron-hole pairs when struck by infrared radiation. In this material, the bandgap is dependent on the ratio of cadmium to mercury. For example, a detector made from Hg1−xCdxTe with x=0.3 would respond, at a temperature of 80K, to all wavelengths up to 5 μm. In practice a lower limit is set, either intentionally or unintentionally, by the presence of some other component in the optical path. For example, the lower limit could be set by using an optical filter that cut-on at 3 μm so that the combination of filter and detector would then respond to all wavelengths between 3 μm and 5 μm. Such a conventional detector gives a signal proportional to the integrated photon flux in the wavelength band. However, the spectral distribution of emissions from a source can give information about the source and many applications require the ability to image a scene at infrared wavelengths in two or more different spectral bands, a capability commonly called, where two spectral bands are used, "dual colour thermal imaging". Such applications include rejection of background clutter, target discrimination and remote sensing for temperature determination and pollution monitoring.
Such dual-band HgCdTe detector arrays comprise two separate photovoltaic detectors within each unit cell, one on top of the other. The photodiode with the shorter cut-off wavelength acts as a long-wavelength-pass filter for the longer cut-off photodiode. The use of two spatially coincident detectors that respond in different wavelength bands, the so-called two-colour detector, gives useful information about the source.
There are two principal types of HgCdTe two-colour detectors-the metal-insulator-semiconductor (MIS) heterojunction detector and the triple layer heterojunction diode. The MIS heterojunction includes a thin wide bandgap n-type layer over a thick narrow bandgap n-type layer. The structure can detect radiation consistent with the wide bandgap layer or wide plus narrow bandgap layer, depending upon the voltage across the layers. However this structure requires precise control of both the layer thickness and the carrier concentration. It also only detects narrow and wide bandgap radiation separately.
The triple layer heterojunction diode includes back-to-back n-p-n diodes, one photodiode of long wavelength, LW, the other of mid wavelength, MW, for example. Operated by biasing between two terminals, one bias polarity results in the top (long wavelength, LW) photodiode of the bias-selectable detector being reverse-biased. The photocurrent of the MW photodiode is shunted by the low impedance of the forward-biased MW photodiode and the only photocurrent to emerge in the external circuit is the LW photocurrent. When the bias voltage is reversed, the situation reverses. The LW photodiode is then forward-biased and the MW photodiode is reverse-biased. In this case the LW photocurrent is shunted and only the MW photocurrent is seen in the external circuit. This provides detection in two adjacent wavebands within each unit cell, with the optical areas of the two photodiodes spatially registered and co-located. Such co-location improves the accuracy of any calculation which assumes a single source for the two wavelengths of radiation. Even though the bias-selectable dual-band HgCdTe detector affords spatial co-location of the two detectors, it does not allow temporal simultaneity of detection. Either one or other of the photodiodes is functioning, depending on the bias polarity applied across the back-to-back diode pair. Other problems also arise from the fact that it does not allow independent selection of the optimum bias for each photodiode and that there can be substantial MW cross-talk in the LW detector.
Some applications require simultaneity of detection in the two spectral bands. This has been achieved in an independently accessible two-colour IR detector, which provides independent electrical access to each of two spatially co-located back-to-back photodiodes. The p-n-n-p structure was formed by two Hg1−xCdxTe layers grown sequentially onto a cadmium-zinc-telluride, CdZnTe, substrate.
However, previously available two-colour detectors are responsive in two overlapping wavelength bands. There is a need for two-colour detectors that respond in two non-adjacent wavelength bands, i.e. a detector in which two wavelength bands produce a signal, the two wavelength bands being separated by a wavelength band that does not produce a signal.
In our co-pending UK patent application no. 0412942.5 and international patent application no. PCT/GB2005/050083 there is disclosed an electromagnetic radiation detector that is responsive to two discrete wavelength ranges, thus allowing the response of the detector to be matched to discrete atmospheric transmission windows that are separated by wavelength bands in which infrared radiation does not easily propagate. Complete separation or large spacing of the detection bands leads to an improved ability to characterise the temperature or wavelength of an external source, enabling machine intelligence to make a better assessment of the physical nature of the source. Applications of such a detector include clutter rejection and target identification. The detector described in the UK patent application above comprises a plurality of layers of semiconductor material formed on a substrate substantially transparent to electromagnetic radiation having wavelengths in a desired wavelength range. A first layer, doped to provide a first type of electrical conductivity, has a bandgap selected for absorbing radiation up to a first wavelength; a second layer, doped to provide a second type of electrical conductivity, has a bandgap selected for absorbing radiation up to a second wavelength that is longer than the first wavelength; and a third layer, doped to provide the first type of electrical conductivity, has a bandgap selected for absorbing radiation up a third wavelength that is longer than the second wavelength. Sandwiched between these absorbing layers are thin barrier layers that are doped to provide the same type of electrical conductivity as the second layer but have a bandgap substantially greater than the second layer. The purpose of these barrier layers is to prevent minority carriers generated in the second layer from reaching the junctions; instead they recombine with majority carriers in the second layer. Thus radiation with wavelengths between the first and second wavelengths will not give rise to a signal in the external circuit.

Selex Sensors and Airborne Systems Limited


A wiper blade for windshields of motor vehicles, has an elongated wiper strip having a constant diameter, which is held by a support frame and loaded toward the windshield to be wiped is movable over the windshield transversely to its longitudinal extension, wherein, viewed in cross section, the wiper strip has a tip held by a support frame and consisting of synthetic caoutchouc and a skirting strip connected with it, on whose side facing away from the tip a movable wiper lip strip resting on the windshield is attached by means of an elongated tilting bar. A wiper blade, which is dependable in operation over time and can be produced in a cost-effective manner results in that at least a portion of the areas forming the outer contour of the skirting strip consists of natural caoutchouc with a low coefficient of friction.

The invention relates to a wiper blade for cleaning windshields of motor vehicles.
The wiper strips which are a part of the wiper blade which serves to remove water drops from the windshield of a motor vehicle, for example, and which are attached to the wiper blades of a wiper blade device that move back and forth in front of the windshield, are customarily produced, in that a previously compounded and vulcanized initial rubber material, therefore an un-vulcanized synthetic caoutchouc, is shaped in a metal mold and vulcanized. Subsequently the surface of the thus obtained rubber wiper strip is post-treated in order to reduce the friction resistance on the windshield to be wiped in accordance with the requirements, or to improve the slidability of the rubberized wiper strip on the windshield to be wiped. At a temperature t of 23.degree..+-.5.degree. C. and a relative humidity of 50.+-.3%, the desired coefficient of friction A may not exceed the value of 2.0. This post-treatment of the surface consists for example of a hardening of the surface of the rubberized wiper strip by chlorination or of a coating, in order to achieve a surface layer of the wiper strip which contains a fine, lubricating powder, for example powder-like molybdenum sulfide. Even though the chlorination reduces the friction resistance and improves the slidability, the necessary durability for wear and tear is still missing. The application of a lubricating surface layer containing powder presents the disadvantage in that it is scraped off after the wiper strip has been in use for a short period of time, thus lacking the necessary durability.
Incidentally, it should be considered that the improvement of the sliding properties of the wiper strips because of the reduced friction coefficient between the wiper strip and the glass surface of the windshield presents difficulties in that they do not tilt in the tilting bar when the wiper blade reverses directions during the operation of the wiper blade device which is normally embodied as pendular wiping device, so that the wiper strip is not dragged but pushed. A flawless, noiseless operation of the wiper blade device is thus ruled out.
To overcome this problem, in connection with a known wiper blade (DE 34 40 677 A1) of the species in question, the areas of the wiper strip which come into contact with the windshield during the wiper blade operation were made of a lubricating synthetic rubber, for example urethane rubber, styrene butadiene rubber, fluoro rubber, chlorinated sulfonized rubber or a mixture of these materials. However, such wiper strips are not, or are only insufficiently halogenizable, so that the desired coefficient of friction can hardly be reached.


A method for managing data traffic in nodes in a fabric network, each node having internally-coupled ports, follows the steps of establishing a managed queuing system comprising one or more queues associated with each port, for managing incoming data traffic; and accepting or discarding data directed to a queue according to the quantity of data in the queue relative to queue capacity. In one preferred embodiment the managed system accepts all data directed to a queue less than full, and discards all data directed to a queue that is full. In some alternative embodiments the queue manager monitors quantity of data in a queue relative to queue capacity, and begins to discard data at a predetermined rate when the quantity of queued data reaches the threshold. In other cases the queue manager increases the rate of discarding as the quantity of queued data increases above the preset threshold, discarding all data traffic when the queue is full.

With the advent and continued development of the well-known Internet network, and of similar data-packet networks, much attention has been paid to computing machines for receiving, processing, and forwarding data packets. Such machines, known as routers in the art, typically have multiple interfaces for receiving and sending packets, and circuitry at each interface, including typically a processor, for handling and processing packets. The circuitry at the interfaces is implemented on modules known as line cards in the art. In some routers the line cards are interconnected through what is known as the internal fabric, which comprises interconnected fabric cards handling transmissions through the fabric. Fabric interconnection has not always been a part of routers in the art, and is a fairly recent innovation and addition for packet routers.
FIG. 1, labeled prior art, illustrates a number of interconnected fabric nodes, labeled in this example A through J, each node of which may be fairly considered to comprise a fabric card in a switching fabric in a router. It will be apparent to the skilled artisan that FIG. 1 is an exemplary and partial representation of nodes and interconnections in a switching fabric, and that there are typically many more nodes and interconnections than those shown.
One purpose of FIG. 1 in this context is to illustrate that there are a wide variety of alternative paths that data may take within a switching fabric. For example, transmission from node E to node J may proceed either via path E-F-H-G-J, or alternatively via E-F-D-G-J. The skilled artisan will also recognize that the nodes and interconnections shown are but a tiny fraction of the nodes and interconnections that might be extant in a practical system.
In conventional switching fabric at the time of the present patent application fabric nodes in such a structure are implemented on fabric cards or chips that do Flow Control. Such Flow Control is very well-known in the art, and comprises a process of monitoring ports for real or potential traffic overflow, and notifying an upstream port to stop or slow sending of further data. That is, if node G as shown in FIG. 1, becomes overloaded at a particular input port, for example, the port from D, the Flow Control at G will notify D to restrict or suspend traffic to G In this example, D may receive traffic from upstream neighbors that it cannot forward to G, and it may then have to notify these neighbors to suspend sending traffic to D. This example illustrates how Flow Control may cause traffic changes made by nodes as a result of an overflow condition at a downstream node to propagate further upstream affecting further nodes, and further stopping or diverting traffic. In FIG. 1 arrows between nodes are indicative of Flow Control indicators passed, and the skilled artisan will also understand that traffic may be in any direction, and that Flow Control indicators are therefore passed in both directions as well.
A serious problem with Flow Control as conventionally practiced is that the upstream notifications, inherent in flow control, propagate further upstream and hinder or stop traffic that there is no need to stop, partly because the interconnections of nodes may be quite complicated and the alternative paths quite numerous. Further, a node that has been informed of a downstream overload condition cannot select to stop or divert traffic just for that particular link, but only to stop or divert all traffic. These effects, because of the complexity and interconnection of nodes in a fabric, can result in complete stultification of parts of a system, or of an entire network.
There have been in the art several attempts to improve upon flow control, but all such solutions have only been partly successful, and still use upstream propagation of control indicators, which always still have a good chance of causing unwanted difficulty.
What is clearly needed is a way to deal with temporary overloads at fabric nodes without resorting to problematic upstream messaging without impacting traffic that does not need to use the overloaded link.

This patent is subject to a terminal disclaimer.


Phosphites which are useful as a deterioration inhibitor for organic material and are represented by the following formula: ##STR1## wherein R.sup.1, R.sup.2, R.sup.5 and R.sup.6 represent a hydrogen atom, an alkyl group, a cycloalkyl group, an alkylcycloalkyl group, an aralkyl group or a phenyl group;. R.sup.3 represents hydrogen atom or an alkyl group; PA1 R.sup.4 represents a hydrogen atom, an alkyl group, a cycloalkyl group, an alkylcycloalkyl group, an aralkyl group or a phenyl group, or the two R.sup.4 together form a direct bond, a group represented by --S-- or an optionally substituted methylene group; PA1 A represents an alkylene group; PA1 W represents a group represented by --O-- or a group represented by --NR.sup.7 PA1 B represents an alkylene group;. wherein R.sup.7 represents a hydrogen atom, an alkyl group, etc.;. and one of Y and Z represents a hydroxyl group, an alkoxy group or an aralkyloxy group, and the other one represents hydrogen atom or an alkyl group.

It has been known that organic materials such as thermoplastic resin, thermosetting resin, natural or synthetic rubber, mineral oil, lubricating oil, adhesive, paint, etc. are deteriorated by the action of, for example, heat, oxygen, etc. on production, processing and use, resulting in lowering of the strength of the organic material due to a phenomenon (e.g. molecular cleavage, molecular crosslinking, etc.), change in flow properties, coloring, deterioration of surface physical properties, etc., which results in a decrease in a commercial value. It has hitherto been known that organic materials may be stabilized by containing various phenol and phosphorous antioxidants for the purpose of solving these problems about heat deterioration and oxidation deterioration.
As the phosphorous antioxidant, for example, tris(2,4-di-t-butylphenyl)phosphite is used.
However, these known phosphorous antioxidants had a problem that the stabilizing effect to heat deterioration and oxidation deterioration is insufficient.
On the other hand, as those for solving the problem of the phosphorous antioxidant, there is suggested, for example, a cyclic phosphite having a carbonyloxy alkylene group, such as 2,10-dimethyl-4,8-di-t-butyl-6-{2-3-(3-t-butyl-4-hydroxy-5-methylphenyl)p ropionyloxy!ethoxy}-12H-dibenzod,g!1,3,2!dioxaphosphosine, etc. (JP-A-5-86084).
Although these cyclic phosphite exhibits improved stabilizing effects to heat deterioration and oxidation deterioration, these effects are not fully satisfactory. Accordingly, more efficient antioxidant has been desired.
The present inventors have produced various phosphorous compounds and studied intensively. As a result, it has been found that specific cyclic phosphites having an aminoalkylene or oxyalkylene group in place of a carbonyloxy alkylene group exhibits excellent stabilizing effect. It has also been found that specific cyclic phosphites having an oxyalkylene group in place of a carbonyloxy alkylene group exhibits excellent discoloration-resistant effect. Thus, the present invention has been accomplished.

Phosphites, process for producing them and their use


A stethoscope for reducing background noise comprising a housing having a receiver portion and an audio output means; the receiver portion having a plurality of noise ports; a microphone isolator located within the receiver portion; a noise canceling microphone having a front end and a back end enclosed by the microphone isolator; an acoustical tube having an acoustical waveguide connected to the microphone isolator for channeling an input signal; a chest piece having a sound diaphragm pickup for receiving the input sound and noise signal connected to acoustic tube to permit a pressure gradient noise porting placed at the back end of the microphone and internally behind the noise port.

As is to be appreciated, in numerous situations, the presence of background acoustic noise is undesirable for a physician attempting to listen to a heartbeat or systolic murmur from a rapid heart beat of a patient to make an immediate determination or diagnosis of the patient's condition. As an example, consider the situation in which a doctor or paramedic is trying to listen with the use of a stethoscope to a heart rate of a sick person to determine the heart condition of the individual in an ambulance with a siren blaring.
In this situation, loud acoustic background noise from the siren or from any other ambient noise in the vicinity is received in a standard microphone, usually a omnidirectional microphone, located in the stethoscope housing. The noise and the sound signal are then converted to an electrical signal by the circuitry contained within the housing of a standard stethoscope. The electrical signal is then amplified and supplied to the ear of the attendant checking out the condition of the patient and is converted thereat to an acoustic signal. This resulting signal is a distorted reading of the patient's heart rate as background noise is include in the sound conveyed to a physician's ear or to a computer recording the sound of the heart rate.
As a result, the physician fails to obtain an accurate reading of the patient's heart rate because of the transmission of background noise, when utilizing a conventional stethoscope in an ambulance or noisy emergency room. Even more critical a situation is when a person has suffered a heart attack and a correct reading of the heart attack patient's heart rate could mean life or death in the next step to save the person's life. Moreover, the sound of the heart combined with the background noise may make it difficult for the doctor or nurse to monitor the heart rate to determine whether shock treatment is necessary.
Conventional or state-of-the art stethoscopes, such as the Analyst available from Heartsounds in Ontario, Canada, do not reduce or cancel background noise to improve performance of stethoscope utilized in a noisy environment or the like. Rather, the standard microphone utilized in such conventional stethoscopes are omnidirectional microphones. These standard microphones accept background and sound signals and convey an electrical signal, which is degraded by ambient noise to the electrical processing means within the stethoscope. Furthermore, an omnidirectional microphone accepts signals in all directions, including ambient noise propagating in more than one direction which is transmitted as an input signal to the microphone together with the sounds obtained from listening to the heart.
Thus, the utilization of the omnidirectional microphone in the standard stethoscope does not prevent heart sounds, especially at low frequencies, from being distorted in a noisy environment or when utilizing digital means to convey sound signal when using stethoscope. Support that the heart rate sounds are distort when using omnidirectional microphones in stethoscopes is shown in the comparative testing performed by Andrea Electronics Corporation of an Analyst stethoscope and a stethoscope made in accordance with the present invention.
For instance, the Analyst stethoscope at low frequencies that are under 1 kHz detects or picks up unwanted background noise when processing the digital heart rate received from the patient in a noisy environment, which in turns degrades the heart rate calculation. Furthermore, the Analyst is used in connection with computer software that samples the heart rate at low frequencies or at narrower bandwidths. Therefore, it is desirable to cancel noise before it is transmitted to the software sampling to prevent an inaccurate software heart rate sampling.
Conventional omnidirectional microphones located in prior art stethoscopes cannot simply be replaced with noise canceling microphones having pressure sensitive surfaces with a low gain to enhance noise canceling without typically having to reconfigure the entire stethoscope. Simple replacement of the type of microphone does not solve the problem. Rather, as will be discussed in the present invention, the mechanical/acoustical arrangement of the microphone within the necessary input ports of the microphone isolator acoustic coupler must take place so that noise cancellation occurs. This is because the mechanical/acoustical arrangement of the noise canceling microphone allows for sound equalization of the noise received from the noise port to achieve performance in calculating the number of beats per minute of the patient's heart, as such, would be relatively expensive.
Thus, the prior art has failed to provide a relatively low-cost means for reducing or canceling background noise to achieve an accurate heart rate of a patient by mechanically/acoustically diffraction means, and a cost-effective means for enabling existing stethoscope that does or does not use digital network to sample heart rates by computer means or manually by listening and recording the rate on the patient's chart.

Noise canceling improvement to stethoscope


An apparatus and method is provided for processing and rewinding a web made of easily stretchably deformable plastic film. The web is drawn from a supply roll assembly by a series of synchronously, positively driven draw and transfer rolls and directly delivered to a rewind spindle. The rewind spindle is positively driven at a speed greater than the speed imparted to the web by the draw and transfer rolls. However, the rewind spindle is in peripheral contact with a transfer drum which is the last of the series of draw and transfer rolls so that the processed web is immediately transferred from the transfer drum to the rewind spindle. The transfer drum exerts a drag on the rewind spindle to control and match the speed of the rewind spindle to the speed of the moving web.

The intermediate processing of stock is known as converting. The basic function of the converting industry is to intermediately process flexible materials, such as paper, plastic, cardboard, or light foil for subsequent use in, for example, the packaging industry. A large volume of the stock material to be converted in is roll form. The conversion of these materials includes, for example, printing, slitting, and trimming as the material is conveyed from a supply roll onto a rewind roll. For certain applications, the conversion process may simply comprise rewinding selected lengths of material from a supply roll onto a rewind roll in preparation for further processing. The stock material is often converted using rewinding machines equipped with devices to perform one or more of the selected intermediate processes.
There are two conventional types of rewinders in general use for converting thin, flexible materials such as plastic film. Both types of conventional rewinders have a set of positively driven primary draw rollers which initially draw the thin web of material from a supply roll. The web is then drawn by a rewinding spindle or core from the primary draw rollers over a series of idler rolls which smooth and guide the web onto the spindle or core. One or more converting processes may be performed on the material before it is rewound on the rewind spindle or core. The two conventional types of rewinders differ, however, in the manner by which the material is drawn from the primary draw rollers and transferred to the rewind roll.
The first type of conventional rewinders are known as surface driven rewinders which include one or more positively driven rollers whose surface contacts the outside layer of material being applied to a freely rotatable rewind core. The friction force created by the rotating surface drive rollers on the outer layer of material on the freely rotatable rewind core simultaneously creates a positive pull on the material and rotates the rewind core. The surface drive rollers are driven at a speed slightly greater than the speed of the moving web so as to create a positive pull on the material.
Some materials have a very smooth and slippable surface. To create a friction force of sufficient magnitude for the conventional surface rewind apparatus to draw this type of material from the supply roll and to turn the rewind core, the surface drive rollers must forcibly contact the outer layer of material on the core. Another reason the surface drive rollers must forcibly contact the rewind core is to prevent the accumulation of air in between successive layers of rewound film. The core is mounted in a "floating" axis of rotation above the surface driven rollers. A portion of the contact force results from the weight of the core and the weight of the accumulated material on the core. However, for successful surface-driven rewinding it is still often necessary to provide a mechanical, pneumatic or hydraulic device which sufficiently increases the contact force between the rewind core and the surface drive rollers beyond the force created by the combined weight of the core and rewound material, particularly at the beginning of the rewind process when the weight of the material on the rewind core is not significant.
Another problem with surface driven rewinders is that the aforementioned device for increasing the contact force between the drive rollers and the rewind core must be continuously adjusted during the converting process. As material is continuously applied to the rewind core, the diameter and weight of the roll steadily increases thereby steadily increasing the contact force on the surface drive rollers. Consequently much more air is squeezed out of the outer layers of material than out of the inner layers of material which results in a rewound roll having a soft interior. This phenomenon may cause further problems when the rewound roll is processed or rewound again. Additionally, the rewound roll may have a telescopic or other irregular shape. Thus, an additional mechanical, pneumatic or hydraulic adjustment mechanism must be provided to compensate for the steady increase in the contact force exerted on the surface drive rollers. This adjustment mechanism also adds to the complexity and cost of the surface driven rewinder.
The second type of conventional rewinders are center-driven rewinders which include a positively driven spindle on which the material is wound to produce the rewound roll. The shaft of the spindle is driven by a motor independent of any initial or intermediate draw rolls. The web is pulled by the rotating spindle which continuously winds successive layers of material onto the spindle.
One problem associated with center-driven rewinders is maintaining a constant tension on the web as the weight and diameter of the rewind roll steadily increase. As the diameter of the rewind roll increases, the tangential velocity of the roll also increases. Further, as the weight of the roll increases, an increase in motor torque is required to rotate the spindle. To compensate for these changing conditions, the angular velocity of the spindle must be reduced but the motor torque must be increased.
Few, if any, constant horsepower motors have heretofore been able to provide a constant horsepower output throughout the build-up range of the rewind roll. The motor will, at times, exert excessive tension on the web causing plastic deformation of the web. Conventional center-driven rewinders also exert excessive tension on the web by design to prevent the accumulation of air in between successive layers of material in the rewind roll. While some center-driven rewinders use a freely-rotatable doctor roll contacting the rewinding roll to prevent entrapment of air in between successive layers of material, excessive tension is still created on the web which causes stretching and plastic deformation. Thus, center-driven rewinders are often impractical for use with thin, plastic material.

Machine for rewinding and intermediately processing thin flexible material using a conveyor


Methods, systems, and apparatus for a low-latency network interface. One of the methods includes receiving a signal having encoded data. A bit stream is generated from the received signal. Bits of the bit stream are shifted into a shift register until a feedback signal generated by a synchronization decoder is received. After the feedback signal is received, output of the shift register is descrambled to generate descrambled data. The descrambled data is stored in a first parallel register when the synchronization decoder determines that the data in the shift register is aligned to a word boundary. If the data in the first parallel register is properly aligned, the output is stored in a second parallel register.

This specification relates to network interface devices.
The physical layer of conventional network protocol stacks include components that serialize and deserialize bit streams, scramble and descramble data, and perform synchronization to align the data to word boundaries.
For example, the IEEE 802.3 Ethernet standard defines a Physical Medium Attachment (PMA) layer and a Physical Coding Sublayer (PCS). These two layers lie between the communication medium at the lowest level and the Gigabit Media Independent Interface (GMII) or extended GMII (XGMII) layers.
The PMA layer receives a serialized bit stream, recovers the clock, and deserializes the data. The PCS layer descrambles the data and performs synchronization to determine the word boundaries of the data.


Disclosed is a hand-held percussion musical instrument in the form of a rigid tubular ring, which includes a plurality of elongate hollow tubes, the tubes having rigid tubular walls and opposite end walls defining closed hollow tube interiors. Steel shot is loosely contained within the hollow interiors of the tubes, whereby the ring may be hand manipulated to cause the shot to impact the walls to create audible percussion sounds.

Examples of percussion musical instruments designed to be held in one hand by a performer for lending motion and percussion sound emphasis to music, singing and/or dancing include the tambourine and the maraca. Typically the tambourine is a shallow one-headed drum with loose metallic discs at the sides and which is played by shaking, striking with the hand, or striking the instrument against other portions of the body. The typical maraca is a dried gourd or the like, as on a handle, the gourd being hollow and containing dried seeds or pebbles. In either case, such conventional instruments may be held in one hand and are used to lend emphasis to the body and arm movements of a singer or dancer, as well as to lend percussion sound emphasis to music whether or not accompanied by visual body movements of a singer or dancer.
The instrument of the present invention, albeit different in material respects, falls within this same general class of percussion instruments.
Accordingly, the principal object of the present invention is to provide a new and unique hand-held musical percussion instrument, also suitable as an attractive prop for a singer or dancer, and which is convenient to manipulate and capable of producing unique percussion sounds and sound combinations.

Hand-held percussion musical instrument comprising elongate tube shaped as a ring, incorporating dividers, and incoporating contained sound-generating elements


In aspects of the invention, a multilevel conversion circuit can include a configuration for linking capacitors, including diodes, reverse-blocking semiconductor switches, and resistors, and a circuit for clamping the capacitor voltage at a specified voltage. Such a configuration can serve to reduce the number of capacitors that need detection of the voltages thereof and appropriate changing-over operation of semiconductor switches to control the capacitor voltage to a desired value. By way of aspects of the invention, desired voltages can be provided to the capacitors.

1. Field of the Invention
Embodiments of the invention relate to multilevel conversion circuits that deliver multilevel voltages.
2. Description of the Related Art
FIG. 10 shows an example of a five-level conversion circuit using flying capacitors disclosed in Japanese Unexamined Patent Application Publication No. 2012-182974. This conversion circuit delivers five levels of voltage from a DC power supply composed of series-connected two DC single power supplies DP and DN having three terminals: positive terminal P, a zero terminal M, and a negative terminal N. A series circuit of semiconductor switches S1 through S4, each composed of antiparallel-connected diode and an IGBT, is connected between the positive terminal P and the negative terminal N of the DC power supply. In parallel to a series circuit of the semiconductor switches S2 and S3 connected are a series circuit of the semiconductor switches S5 and S6 and a capacitor C1 called a flying capacitor. An AC switch composed of reverse blocking IGBTs S15 and S16 that exhibits withstand voltage in a reversed direction is connected between the connection point between the semiconductor switches S5 and S6 and the zero terminal M that is a middle potential point of the DC power supply. An AC terminal U is the connection point between the semiconductor switches S2 and S3.
When the voltage Edcp and Edcn of the respective DC single power supplies DP and DN are each 2E and the voltage Vc1 across the capacitor C1 is controlled at E, the circuit having the construction described above delivers five levels of voltage at the AC terminal U. For instance, when the semiconductor switches S1, S2, S6, and S16 are in the ON state, a voltage 2E is delivered from the AC terminal U; when the semiconductor switches S1, S3, S6, and S16 are in the ON state, or the semiconductor switches S2 and S6 and the AC switch Sac are in the ON state, a voltage E is delivered; when the semiconductor switches S3 and S6 and the AC switch Sac are in the ON state, or the semiconductor switches S2 and S5 and the AC switch Sac are in the ON state, a voltage zero is delivered; when the semiconductor switches S2, S4, S5, and S15 are in the ON state, or the semiconductor switches S3 and S5 and the AC switch Sac are in the ON state, a voltage −E is delivered; and when the semiconductor switches S3, S4, S5, and S15 are in the ON state, a voltage −2E is delivered at the AC terminal U.
In this operation, there are two modes for deliver a voltage E from the AC terminal U in the direction of current toward the load. One of them is through a path 1: the semiconductor switch S1→the capacitor C1→the semiconductor switch S3; the other is through a path 2: the AC switch Sac→the semiconductor switch S6→the capacitor C1→the semiconductor switch S2. The capacitor C1 is charged through the path 1 and discharged through the path 2. The average voltage of the capacitor C1 can be controlled at the value E by detecting the voltage of the capacitor C1 and appropriately selecting the paths in order for the average value of the voltage to be E. There are similarly two paths for the mode to deliver a voltage −E from the AC terminal U, and the average voltage of the capacitor C1 can be controlled at the value E.
FIG. 11 shows an example of conversion circuit that is an extended conversion circuit of seven levels from the conversion circuit of five levels shown in FIG. 10. The seven level conversion circuit of FIG. 11 has a circuit construction to deliver seven levels of voltage from a DC power supply composed of DC single power supplies DP and DN and having three terminals of a positive terminal P, a zero terminal M, and a negative terminal N. Between the positive terminal P and the negative terminal N connected is a series circuit of semiconductor switches S1 through S6 each consisting of a diode and an IGBT antiparallel-connected with each other. In parallel to the series circuit of semiconductor switches S2 through S5 connected are a capacitor C2 and a series circuit of the semiconductor switches S7 and S8. In parallel to the series circuit of semiconductor switches S3 and S4 connected is a capacitor C1. Between the connection point between the semiconductor switches S7 and S8 and the zero terminal M, i.e. the middle potential point of the DC power supply, connected is an AC switch Sac consisting of antiparallel-connected reverse-blocking IGBTs S15 and S16 each exhibiting a withstand voltage in the reverse direction. The connection point between the semiconductor switches S3 and S4 is the AC terminal U.
In this circuit construction, when the voltages Edcp and Edcn of the DC single power supplies DP and DN are each 3E, and the voltage Vc1 across the capacitor C1 is controlled at E and the voltage Vc2 across the capacitor C2 is controlled at 2E, seven levels of voltages are delivered from the AC terminal U. For example, when the semiconductor switches S1 through S3 are in the ON state, a voltage 3E is delivered from the AC terminal U; when the semiconductor switches S1, S2, and S4 are in the ON state, a voltage 2E is delivered; when the semiconductor switches S1, S5, and S4 are in the ON state, a voltage E is delivered; when the AC switch Sac and the semiconductor switches S7, S2, and S3, or the AC switch Sac and the semiconductor switches S8, S5, and S4 are in the ON state, a voltage zero is delivered; when the AC switch Sac and the semiconductor switches S7, S2, and S4 are in the ON state, a voltage −E is delivered; when the AC switch Sac and the semiconductor switches S7, S5, and S4 are in the ON state, a voltage −2E is delivered; and when the semiconductor switches S4 through S6 are in the ON state, a voltage −3E is delivered from the AC terminal U. In detail, there are a plurality of control modes other than the ones describe above. They are, however, extended operation of the circuits shown in FIG. 11 and thus detailed description thereon is omitted here.
In this operation, there are two modes for delivering a voltage E from the AC terminal U. One of them is through a path 1: the semiconductor switch S1→the capacitor C2→the semiconductor switch S5→the semiconductor switch S4; the other is through a path 2: the AC switch Sac→the semiconductor switch S8→the capacitor C2→the semiconductor switch S2→the capacitor C1→the semiconductor switch S4. The capacitor C2 is charged through the path 1 and discharged through the path 2. The average voltage of the capacitor C2 can be controlled at the value 2E by detecting the voltage of the capacitor C2 and appropriately selecting the paths in order for the average value of the voltage to be 2E. There are similarly two paths for the mode to deliver a voltage −E from the AC terminal U, and the average voltage of the capacitor C2 can be controlled at the value 2E by appropriately selecting the paths.
There are two modes for delivering a voltage 2E from the AC terminal U. One of them is through a path 1: the semiconductor switch S1→the semiconductor switch S2→the capacitor C1→the semiconductor switch S4; the other is through a path 2: the semiconductor switch S1→the capacitor C2→the semiconductor switch S5→the capacitor C1→the semiconductor switch S3. The capacitor C1 is charged through the path 1 and discharged through the path 2. The average voltage of the capacitor C1 can be controlled at the value E by detecting the voltage of the capacitor C1 and appropriately selecting the paths in order for the average value of the voltage to be E. There are similarly two paths for the mode to deliver a voltage −2E from the AC terminal U, and the average voltage of the capacitor C1 can be controlled at the value E.
In the seven-level conversion circuit having the construction of FIG. 11, the semiconductor switches S7 and S8 conduct switching with a voltage variation step of two units, i.e. 2E. A large voltage variation in an output waveform generally produces a high micro surge voltage on an AC motor, for example, in the load side corresponding to the voltage variation, causing a problem of dielectric breakdown.
In order to deal with this problem, the inventor of the present invention has proposed the circuit disclosed in Japanese Unexamined Patent Application Publication No. 2013-146117. FIG. 12 shows the construction of the circuit, in which a DC power supply consisting of series-connected DC single power supplies DP and DN has terminals of a positive terminal P, a zero terminal M, and a negative terminal N in the order of descending electric potential. The terminal M is the base terminal at a potential of zero. Semiconductor switches in the following description are IGBTs each having an antiparallel-connected diode. The other types of semiconductor switchers can be employed, of course. A series circuit of semiconductor switches S1 through S6 are connected between the positive terminal P and the negative terminal N. The connection point between the semiconductor switches S3 and S4 is an AC terminal U. A series circuit of semiconductor switches S7 through S10 and a capacitor C2 are connected between the connection point between the semiconductor switches S1 and S2 and the connection point between the semiconductors switches S5 and S6. An AC switch Sac composed of antiparallel-connected reverse blocking IGBTs S15 and S16 is connected between the zero terminal M and the connection point between the semiconductor switches S8 and S9.
Further, a capacitor C1 is connected between the higher potential terminal of the semiconductor switch S3 and the lower potential terminal of the semiconductor switch S4, and a capacitor C3 is connected between the higher potential terminal of the semiconductor switch S8 and the lower potential terminal of the semiconductor switch S9. The capacitors C1, C2, and C3 are called flying capacitors. The AC switch Sac can be composed, in place of using the construction of antiparallel connection of the semiconductor switches S15 and S16 each exhibiting reverse-blocking ability shown in FIG. 12, by combination of IGBTs without reverse-blocking ability and diodes as shown in FIGS. 13A-13C. The circuit in FIG. 13A is composed of antiparallel-connected two series circuits each consisting of a diode and an IGBT. The circuits in FIGS. 13B and 13C are composed of two circuits connected in series, each circuit consisting of antiparallel-connected diode and an IGBT.
The magnitude of the voltage of each of the DC single power supplies DP and DN in the circuit of FIG. 12 is supposed here to be 3E. Similarly to the conventional example of FIG. 11, the voltages Vc1, Vc2, and Vc3 of the capacitors C1, C2, and C3 are changed by charging or discharging the capacitors to hold average values of Vc1=E, Vc2=2E, and Vc3=E. When the potential at the zero terminal M is zero, the output voltage Vu at the AC terminal U can be obtained at seven levels of ±3E, ±2E, ±E, and zero by ON/OFF operation of the semiconductor switches. For example, when the semiconductor switches S1, S2, S3, S9, S10, and S16 are in an ON state and the other semiconductor switches are in an OFF state, as shown in FIG. 14A, the output voltage at the AC terminal U is +3E, which is the voltage at the terminal P of the DC single power supply DP. When the semiconductor switches S1, S3, S5, S9, S10, and S16 are in the ON state and the other semiconductor switches are in the OFF state as shown in FIG. 14B, the output voltage at the AC terminal U is +2E, which is the voltage +3E of the DC single power supply DP minus the voltage +2E of the capacitor voltage Vc2 plus the voltage +E of the capacitor voltage Vc1.
When the semiconductor switches S3, S5, S9, S10, S15, and S16 are in the ON state and the other semiconductor swathes are in the OFF state as shown in FIG. 14C, the output voltage at the AC terminal U is +E, which is the potential zero at the terminal M of the DC power supply plus the voltage +E of the capacitor voltage Vc1. When the semiconductor switches S4, S5, S9, S10, S15, and S16 are in the ON state and the other semiconductor switches are in the OFF state as shown in FIG. 14D the output voltage at the AC terminal U is zero, which is the potential at the terminal M of the DC power supply. When the semiconductor switches S3, S5, S7, S9, S15, and S16 are in the ON state and the other semiconductor switches are in the OFF state as shown in FIG. 14E, the output voltage at the AC terminal U is zero, which is the voltage zero at the terminal M of the DC power supply plus the voltage +1E of the capacitor voltage Vc3 minus the voltage +2E of the capacitor voltage Vc2 plus the voltage +1E of the capacitor voltage Vc1.
Electric current flows from the terminal P, M, or N to the AC terminal U as a result of ON/OFF operation of the semiconductor switches in the paths shown in FIGS. 14A through 14E, while charging or discharging the capacitors. There are a multiple of paths for a mode to obtain the same voltage at the AC output terminal similarly to the five-level conversion circuit of FIG. 10 and the seven-level conversion circuit of FIG. 11. By detecting the voltages of the capacitors and selecting an appropriate path, the voltage control is possible for the capacitors C1 and C3 in FIG. 12 at E and the capacitor C2 at 2E. Other combination of paths can deliver a desired voltage and charge or discharge the capacitors, through details are omitted here.
The conversion circuit of FIG. 12 provides seven levels of output voltages Vu from the DC power supply having three levels of potential terminals combining the voltages Edcp and Edcn of the DC single power supplies DP and DN and the voltages Vc1, Vc2, and Vc3 of the capacitors C1, C2, and C3 by means of ON/OFF operation of the semiconductor switches. In order to obtain seven levels of output voltages, the average value of the voltage Vc1 across the capacitor C1 is necessarily E, the average value of the voltage Vc2 across the capacitor C2 is necessarily 2E, and the average value of the voltage Vc3 across the capacitor C3 is necessarily E. In actual operation of the circuit, however, the capacitor voltages Vc1, Vc2, and Vc3 change due to the current running in the circuit. In generally employed method for holding the capacitor voltages at the average values, ON/OFF operation of the semiconductor switches S1 through S10 and the AC switch Sac is combined to deliver desired voltages and simultaneously control charging and discharging of the capacitors C1, C2, and C3. This control needs a means for detecting the capacitor voltages Vc1, Vc2, and Vc3. Nevertheless, the capacitors have no common potential part. Thus, the voltage detecting circuit needs an insulating function, which increases device costs.


Methods of making adhesive articles providing air egress by supplying a route for the air to flow out from under the construction are described. One method includes providing a release liner comprising a moldable layer having a release surface and a back surface; applying a first pattern of a first non-adhesive material to a first portion of the release surface; applying a second pattern of a second non-adhesive material to a second portion of the release surface, wherein the second pattern partially overlaps the first pattern; embedding at least one of the first or second non-adhesive materials into the moldable layer; and transferring an adhesive layer having a front and back surface and end edges onto the release liner, wherein the front surface of the adhesive layer is adhered to the release surface of the release liner.

Pressure sensitive adhesives have enjoyed great acceptance for their convenience of use. The pressure sensitive adhesive is often used for tapes and articles containing graphic images. The advantages of the pressure sensitive adhesives are their strong bonding and simplicity of application. One drawback of these products is the initial tenacity of the pressure sensitive adhesive. The positioning of the product must be precise because of the initial strong bond of the adhesive. A need exists to make such products using pressure sensitive adhesives which are repositionable, i.e. the product may be removed after light application of pressure without damaging the product or the substrate. Similarly, a need exists for the products to be able to slide. Slideability allows for correction of alignment of the product without the need of completely removing the product and possibly damaging the adhesive article or substrate.
When the product is a graphic image and is applied over an area like a wall or truck panel, there is the possibility of trapping air under the product and forming bubbles or wrinkles. In order to avoid such problems, the product should exhibit air egress, i.e. the product should provide a route for air trapped under the product to be removed or to escape.
A need exists for products which have one or more of the desirable properties of air egress, repositionability and slideability.

Adhesive articles with improved air egress and methods of making the same


The thermoplastic resin composition of the present invention is made of:. (a) 5-95 weight % of polypropylene; PA1 (b) 95-5 weight % of a polyester; and PA1 (c) 2-70 parts by weight, per 100 parts by weight of the total of (a)+(b), of a polyolefin-polyester graft copolymer.. The polyolefin-polyester graft copolymer is constituted by (A) 10-90 parts by weight of a polyester having an intrinsic viscosity [.eta.] of 0.30-1.20 and an end carboxyl group content of 15-200 milliequivalent/kg; and (B) 90-10 parts by weight of a modified polyolefin having an epoxy group or carboxyl group content of 0.2-5 mol % and a weight-average molecular weight of 8,000-140,000. This thermoplastic resin composition may further contain (d) a modified polypropylene grafted with an unsaturated carboxylic acid or its anhydride.

The present invention relates to a thermoplastic resin composition comprising a polyester and polypropylene, and more particularly to a thermoplastic resin composition comprising a polyester and polypropylene extremely compatible with each other.
Polypropylene resins have excellent moldability, chemical resistance, water resistance, etc., but they are poor in mechanical properties such as flexural modulus, impact resistance, etc. To improve such properties of the polypropylene resins, attempts have been made to blend the polypropylene resins with polyesters having excellent impact resistance, mechanical strength, etc.
However, since the polypropylene and the polyester do not have good compatibility, proposals have been made to add a modified polyolefin which is grafted with an unsaturated carboxylic acid or its anhydride to improve their compatibility.
Japanese Patent Laid-Open No. 60-58447 discloses a thermoplastic resin composition comprising (A) polypropylene, (B) a thermoplastic polyester, (C) a modified propylene-.alpha.-olefin random copolymer, (D) a hydrogenated styrenebutadiene block copolymer, and (E) an inorganic filler, the modified propylene-.alpha.-olefin random copolymer (C) being produced by grafting a propylene-.alpha.-olefin random copolymer (G) having a crystallization degree of 0 to 30 weight % measured by X-ray analysis and a propylene content of 50 to 70 mol % with 0.01 to 5 weight % of a graft monomer selected from unsaturated carboxylic acids or their derivatives, the component (C) being 1 to 80 parts by weight, the component (D) being 1 to 50 parts by weight, and the component (E) being 5 to 150 parts by weight, per 100 parts by weight of the total of components (A) and (B).
Also, various proposals have been made to add epoxy group-containing copolymers as compatibilizers to the thermoplastic resin compositions of polypropylenes and polyesters.
Japanese Patent Laid-Open No. 61-60744 discloses a thermoplastic resin composition comprising (A) 10-90 weight % of polypropylene, (B) 90-10 weight % of a saturated polyester resin, and (C) 2-30 parts by weight, per 100 parts by weight of the polypropylene (A)+the saturated polyester resin (B), of an epoxy group-containing copolymer.
Japanese Patent Laid-Open No. 61-60746 discloses a thermoplastic resin composition comprising (A) 50-90 weight % of a polypropylene resin selected from a modified polypropylene and a modified polypropylene/polypropylene composition; (B) 50-10 weight % of a saturated polyester resin; and (C) 2-30 parts by weight, per 100 parts by weight of the polypropylene resin (A)+the saturated polyester resin (B), of an epoxy group-containing copolymer.
However, these thermoplastic resin compositions fail to show sufficiently improved flexural modulus and impact resistance. In addition, since sufficient compatibility of the polypropylene with the polyester cannot be achieved, the resulting thermoplastic resin compositions are likely to suffer from surface peel.