A method of producing a glass blank, comprising the steps of: supplying a desired weight of molten glass material to a bearer heated to a temperature of not more than a softening point of the glass material; performing and cancelling, at a temperature of not less than the softening point, pressing of the glass material supplied to the bearer so as to adjust a thickness of the glass material; and cooling the glass material to a temperature of not more than the softening point.

The present invention relates to a method of and an apparatus for producing a glass blank for optical glass elements such as a lens, a prism, etc. used in optical instruments.
Recently, a number of attempts have been made in which an optical lens is formed by a single molding process without a polishing process. Thus, at present, optical lenses are being mass produced by such molding process. To this end, a method is most efficient in which a glass blank in a molten state is poured onto a die so as to be subjected to pressure molding. However, in this method, it is difficult to control contraction of glass during its cooling. Thus, this method is not suitable for accurate molding of lenses. Therefore, a method is generally employed in which a glass blank is preliminarily worked to a specific shape so as to be supplied between dies and then, is heated and pressure molded as disclosed in, for example, Japanese Patent Laid-Open Publication Nos. 58-84134 (1983) and 60-200833 (1985). Meanwhile, Japanese Patent Laid-Open Publication Nos. 2-34525 (1990) and 2-14839 (1990) teach such preliminary working of the glass blank.
Hereinbelow, the above mentioned known methods of producing the glass blank are described with reference to FIGS. 11 to 14. FIGS. 11a and 11b show a known method of molding a glass lens. In this known method, a spherical glass blank shown in FIG. 11a is supplied between upper and lower dies 52 and 53 so as to be pressured molded therebetween into a molded lens 54 of FIG. 11b by pressing the upper die 52 towards the lower die 53 in a sleeve die 51. The upper die 52 is slidably movable in the sleeve die 51.
FIG. 12a shows steps of a known method of producing a glass blank, while FIG. 12b shows steps of a known method of producing a polished lens. The steps of FIG. 12a are substantially the same as those of FIG. 12b. Namely, inspection step (17) and molding step (18) of FIG. 12a are, respectively, replaced by deposition step (17) and inspection step (18) in FIG. 12b.
FIGS. 13a and 13b show a known method of molding a glass element. As shown in FIG. 13a, molten glass is poured from an discharge outlet 55 so as to be received by a molding die 56 disposed below the discharge outlet 55. When a predetermined amount of the molten glass has been poured into the molding die 56, the molding die 56 is lowered at a velocity larger than a flow velocity of the molten glass from the discharge outlet 55 such that the molten glass flowing downwardly from the discharge outlet 55 is separated from the molten glass poured into the molding die 56. Thus, the molten glass poured into the molding die 56 is cooled in the molding die 56 until at least a surface of the molten glass is set, whereby the glass element is obtained.
FIG. 14 shows a known method of molding a glass member. In this known method, molten glass flowing from the discharge outlet 55 is dropped by its own weight or is cut by engaging opposed blades 65a and 65b with each other as shown in FIGS. 15a and 15b such that a molten glass lump 57 falls into a recess 60 of a molding die 58. At this time, gas such as air, inert gas or the like is blown into the recess 60 through a pore 59 opening into the recess 60 such that a gaseous layer is formed between the molten glass lump 57 and a side surface of the recess 60 of the molding die 58 as shown in FIG. 14. Thus, until at least a portion of a surface of the molten glass lump 57 reaches a temperature of not more than a softening point of glass, the molten glass lump 57 is held in the recess 60 substantially out of contact with the side surface of the recess 60 so as to be cooled such that the glass member is produced.
However, the glass lens molded by the above known method of FIGS. 11a and 11b has such a drawback that unless a maximum surface roughness of the glass blank supplied into the die is 0.1 .mu.m or less, the glass lens has defects on the optical face and thus, cannot fulfil optical performances sufficiently.
Meanwhile, the known method of producing the glass blank shown in FIG. 12a requires time and cost equivalent to those for working of a glass lens, so that the glass blank becomes expensive.
Furthermore, in the known method of molding the glass element shown in FIGS. 13a and 13b, when the molten glass is brought into contact with the molding die 56, the molten glass is cooled rapidly. As a result, large wrinkled defects are produced on a contact surface of the molten glass relative to the molding die due to thermal shrinkage. Therefore, in the case where an optical element is formed by this known method, defects are produced on the optical face of the optical element undesirably.
Moreover, in the known method of molding the glass member of FIG. 14, not only it is difficult to deform the glass member into a desired shape but amount of the molten glass flowing from the discharge outlet is not stable due to influence of the gas blown into the recess through the pore of the molding die, which recess is disposed immediately below the discharge outlet.

Matsushita Electric Industrial Co., Ltd.


An apparatus is disclosed for the recovery, separation and recycling of refrigerant from a number of refrigerant chiller systems having individual low efficiency purgers. The apparatus has a high efficiency purger which reduces refrigerant contaminants in the non-condensable gases vented to atmosphere by 90 percent over that of the low efficiency purgers, and operates without interference with the normal purging cycles of the chillers. The apparatus further comprises conduits, valves and a pump which enables the apparatus to completely evacuate the refrigerant gas and refrigerant liquid from the chiller systems.

This invention relates generally to a refrigerant recovery apparatus used for removing, purifying and recycling refrigerant from refrigerant systems. More particularly, the invention relates to such an apparatus adapted for use with refrigerant systems commonly known as chillers, which operate at negative pressure, such that when leaks occur non-condensable atmospheric gases are drawn into the system, the non-condensable gases reducing the efficiency of the chillers to the point that the non-condensable gases must be separated from the refrigerant gases by a purger system. Even more particularly, the invention relates to an apparatus incorporating a recovery tank coupled with a slow, high efficiency purger to further separate the refrigerant gases from the non-condensable gases after initial treatment by fast, low efficiency purger systems, capable of receiving gases from a plural number of refrigerant chiller systems, as well as capable of withdrawing both liquid refrigerant and refrigerant gas from the refrigerant chiller systems.
Refrigerant chiller systems comprising a system for utilizing compressible refrigerant gases, for example CFC, to remove heat from the air, are well known for use in large buildings. For any relatively large building, a number of individual refrigerant chillers will be needed. The chiller systems operate at below atmospheric pressure, so that any leaks occurring in the system result in non-condensable atmospheric air being drawn into the system. This reduces the efficiency of the system and will eventually prevent the chiller systems from performing their function, unless the non-condensable gases are periodically removed from the system. It is known to use purger systems permanently connected to the chillers to separate the refrigerant gas from the non-condensable gases, the refrigerant gas undergoing a phase change into the liquid form in the presence of cooling coils contained within the purger. The non-condensable gases remaining in the gaseous state are then typically vented to atmosphere. Because of time and cost considerations, the purgers used with chillers are relatively fast, but low efficiency purgers, the cooling coils operating in the 35 to 80 degree Fahrenheit temperature range. This results in the bulk of the refrigerant gas being separated from the non-condensable gases, but the gas vented to atmosphere still contains a relatively large component of harmful refrigerant gas. As the pollution problem grows, stricter emission standards are being implemented, to the point that the standard low efficiency purgers do not remove enough of the refrigerant gases to satisfy the requirements.
There exist high efficiency purgers which operate at temperatures in the area of zero degrees Fahrenheit, but these purgers are slow in operation and relatively costly, to the point that equipping each refrigerant chiller system is not a practical solution to the problem. To prevent the venting of refrigerant gas to the atmosphere along with the non-condensable gases, a refrigerant recovery apparatus has been developed which can be interconnected with any number of refrigerant chiller systems and low efficiency purgers, the refrigerant recovery apparatus having a large capacity recovery tank containing cooling coils for initial separation and a slow, but high efficiency purger to dramatically reduce the amount of residual refrigerant gas mixed with the non-condensable gases prior to venting to atmosphere.
It is an object of this invention to provide a refrigerant recovery apparatus with a slow, high efficiency purger, which can be utilized with any number of refrigerant chiller systems having fast, low efficiency purgers, to separate the harmful refrigerant gas from the non-condensable gases prior to venting to atmosphere.
It is a further object of the invention to provide such an apparatus that takes the output gas from the low efficiency purgers and further purifies it by separating out up to 90 percent of the refrigerant gas remaining in the output gas prior to venting to atmosphere.
It is a further object of the invention to provide such a apparatus that operates automatically and does not interfere with the normal purging cycles of the individual refrigerant chiller systems.
It is a further object to provide such a system which allows also remove and replace liquid refrigerant and refrigerant gas the recovered refrigerant, now in liquid form, to be recycled back into the refrigerant chiller systems.
It is a further object to provide such a system which can directly from the refrigerant chiller systems.

Refrigerant recovery and purge apparatus

Southeastern Refrigerant Management, Inc.


This invention is directed to process for making a composition having the formula (I): ##STR1## wherein R.sup.3, R.sup.4, and R.sup.5 are independently hydrogen, substituted or unsubstituted hydrocarbyl, or an agronomically acceptable cation. The process comprises contacting a solution with a noble metal catalyst and introducing oxygen into the solution. The solution contains an N-substituted glyphosate having the formula (II): ##STR2## wherein R.sup.1 and R.sup.2 are independently hydrogen, halogen, --PO.sub.3 H.sub.2, --SO.sub.3 H, --NO.sub.2, or substituted or unsubstituted hydrocarbyl other than --CO.sub.2 H. R.sup.3, R.sup.4, and R.sup.5 are as defined for formula (I).. This invention also relates to an oxidation catalyst comprising a noble metal having a hydrophobic electroactive molecular species adsorbed thereon.

This invention generally relates to a process for converting N-substituted N-(phosphonomethyl)glycines (sometimes referred to as "N-substituted glyphosate"), as well as esters and salts thereof, to N-(phosphonomethyl)glycine (sometimes referred to as "glyphosate"), as well as esters and salts thereof, via a noble-metal catalyzed oxidation reaction. This invention is particularly directed to converting N-substituted glyphosates, as well as esters and salts thereof, having a single N-carboxymethyl functionality.
Glyphosate is described by Franz in U.S. Pat. No. 3,799,758 and has the following formula: ##STR3## Glyphosate and its salts conveniently are applied as a post-emergent herbicide in an aqueous formulation. It is a highly effective and commercially important broad-spectrum herbicide useful in controlling the growth of germinating seeds, emerging seedlings, maturing and established woody and herbaceous vegetation, and aquatic plants.
Various methods for making glyphosate from N-substituted glyphosates are known in the art. For example, in U.S. Pat. No. 3,956,370, Parry et al. teach that N-benzylglycine may be phosphonomethylated to N-benzyl glyphosate, and then reacted with hydrobromic or hydroiodic acid to cleave the benzyl group and thereby produce glyphosate. In U.S. Pat. No. 3,927,080, Gaertner teaches that N-t-butylglycine may be phosphonomethylated to form N-t-butyl glyphosate, and then converted to glyphosate via acid hydrolysis. Glyphosate also may be produced from N-benzyl glyphosate via hydrogenolysis, as described, for example, in European Patent Application No. 55,695 and Maier, L. Phosphorus, Sulfur and Silicon, 61, 65-7 (1991). These processes are problematic in that they produce undesirable byproducts such as isobutylene and toluene which create difficulties due to their potential toxicities. Moreover, acid hydrolysis and hydrogenation of N-substituted glyphosates has been demonstrated only for alkyl groups such as tertiary butyl and benzyl groups which are known to be susceptible to such reactions. Dealkylation of N-methyl, N-isopropyl, and other N-substituted glyphosates which are not readily susceptible to acid hydrolysis or catalytic hydrogenation has not been demonstrated.
Other methods for making glyphosate are directed to oxidatively cleaving N-(phosphonomethyl)iminodiacetic acid (sometimes referred to as "PMIDA"): ##STR4## PMIDA may be synthesized from phosphorus trichloride, formaldehyde, and an aqueous solution of the disodium salt of iminodiacetic acid, as described by Gentilcore in U.S. Pat. No. 4,775,498: ##STR5## It is well-known in the art that PMIDA may be converted into glyphosate by heterogeneous oxidation over carbon catalysts as described, for example, in U.S. Pat. No. 3,950,402 to Franz and U.S. Pat. No. 4,654,429 to Balthazor et al.; by homogenous catalytic oxidation as described, for example, in Riley et al. J. Amer. Chem. Soc. 113, 3371-78 (1991) and Riley et al. Inorg. Chem. 30, 4191-97 (1991); and by electrochemical oxidation using carbon electrodes as described, for example, in U.S. Pat. No. 3,835,000 to Frazier et al. These oxidation methods, however, have been reported to be useful only for preparing glyphosate from PMIDA, an N-substituted glyphosate having two N-carboxymethyl functionalities. None of these prior art oxidation methods have been reported to be useful for preparing glyphosate from N-substituted glyphosate compounds having only one N-carboxymethyl functionality, i.e., where R' in the following formula is other than --CH.sub.2 CO.sub.2 H: ##STR6## To the contrary, many prior art references suggest that if R' is a functionality other than a --CH.sub.2 CO.sub.2 H group, the prior art methods will cleave the --CH.sub.2 CO.sub.2 H group rather than R', and will therefore fail to produce glyphosate. This is particularly true for the prior art which is directed to heterogenous catalytic oxidations over carbon and electrochemical oxidations using carbon electrodes. The mechanisms for these oxidations are well known in the art, particularly for electrochemical oxidations where it is known as the Kolbe reaction, described in various organic electrochemistry books, e.g., S. Torii and H. Tanaka, Organic Electrochemistry 535-80 (H. Lund and M. M. Baizer eds., Marcel Dekker, 3rd ed. 1991). Both mechanisms involve the oxidative degradation of carboxylic acid to a carbon radical and carbon dioxide: ##STR7## There is no suggestion that these mechanisms could be used to cleave any other functionality besides --CH.sub.2 CO.sub.2 H.
Thus, a more general method for oxidizing N-substituted glyphosates to glyphosates is therefore desirable. Such a method would allow a wider range of N-substituted glycines to be used as raw materials for the production of glyphosate. Such a method also could be used to make glyphosate from N-methylglyphosate (sometimes referred to as "NMG"), an undesirable byproduct from the carbon-catalyzed oxidation of PMIDA.

Process for making glyphosate by oxidizing N-substituted glyphosates


2-Substituted-N-{3-[3-(1-piperidinomethyl)phenoxy]propyl}acetamide, derivatives thereof, and pharmaceutically acceptable salts thereof. The substitution group may be aminomethylcyclohexane carbonyl group or N-carbobenzoxy-p-aminomethylhexane carbonyl group. The compounds having the first-mentioned group can be an effective component of an antiulcer drug composition, and the compounds of the last-mentioned group are intermediates for producing the compounds having the first-mentioned group. Disclosed also is an antiulcer drug composition comprising the above compound as an effective component. The antiulcer drug composition exhibits both the gastric acid secretion inhibitive activity and the gastric mucosa protective activity, and is effective as suppression and cure of ulcers.

1. Field of the Invention
The present invention relates to a novel compound, 2-substituted-N-{3-[3-(1-piperidinomethyl)phenoxy]propyl}acetamide, derivatives thereof, and pharmaceutically acceptable salts thereof. The present invention also relates to a drug composition, especially to an antiulcer drug composition, comprising said compound as an effective component.
2. Description of the Background Art
Ulcers, typified by stress ulcer, are diseases characteristic to modern human beings. Their increase in the future is anticipated. For example, in the case of stress ulcer, depression of gastrointestinal tract movement, degradation of gastrointestinal tract vascular flow, and the like are reported to be caused by the action of the adrenocorticotropic hormones releasing factor which is induced by hypothalamus irritation. Simultaneous actions of parasympathetic nerves and sympathetic nerves render the conditions even more complicated. In the case of peptic ulcer, the ulcer is considered to develop when a balance between aggressive factors, such as pepsin, gastric acid, or the like, and defensive factors, such as mucus, mucosal vascular flow, or the like, is lost. Thus, an ulcer is caused by various reasons, including abnormal secretion of gastric acid, hormones, and the like; inhibition in the synthesis of mucus; inhibition in the synthesis of prostaglandin; and the like. Ulcers are thus considered to be formed due to coincidence of various factors.
On the other hand, in any types of ulcers, reducing gastric acid secretion, accelerating synthesis of muco polysaccharide which consists of gastric mucus, or increasing gastric mucosal vascular flow are believed to alleviate deep pains caused by ulcers and to degenerate the ulcers.
Nowadays, roughly classified, two types of antiulcer drugs are on sale; one is Histamine H.sub.2 -antagonist which has an action to depress gastric acid secretion, and the other is a gastric mucosa protective agent which exhibits actions to protect gastric mucosa. Although histamine H.sub.2 -antagonist shows a superior action and exhibits its effect rapidly, it has a problem that the rebound phenomenon is caused by repeated administration. The gastric mucosa protective agent, on the other hand, exhibits only a weak action, and, depending on the circumstances, it takes a long period of time for the agent to exhibit the its effect.
In view of the above-mentioned drawbacks in conventional antiulcer drugs, the present inventors have synthesized a number of compounds in order to develop a new antiulcer drug and were successful in obtaining a novel compound possessing both the gastric acid secretion inhibitive activity and the gastric mucosa protective activity.
Accordingly, an object of the present invention is to provide a novel compound which can exhibit both the gastric acid secretion inhibitive activity and the gastric mucosa protective activity, and which can be used as an effective component for a new type of antiulcer drug.
Another object of the present invention is to provide a drug, particularly an antiulcer drug, comprising said novel compound as an effective component.
Still another object of the present invention is to provide an intermediate compound for preparing said novel compound.
The present inventors have synthesized a number of compounds for the purpose of obtaining a novel compound possessing both of the above-mentioned activities, and found that 2-substituted-N-{3-[3-(1-piperidinomethyl)phenoxy]propyl}acetamide exhibits both the gastric acid secretion inhibitive activity and the gastric mucosa protective activity.

Acetamide derivative and application thereof


Systems, methods, articles of manufacture and apparatus are disclosed to align actions of audio source monitors. An example method disclosed herein includes invoking an audience monitor to transmit a radio frequency (RF) initialization packet to a base unit, receiving an indication that the base unit has received the RF initialization packet at a first time, and invoking the base unit to transmit an RF acknowledgement packet to the audience monitor. The example method also includes receiving an indication that the RF acknowledgement packet is received by the audience monitor and waiting for an end to a delay period having a first value, identifying whether the audience monitor has finished processing the RF acknowledgement packet when the delay period ends at a second time, and incrementing the delay period to a second value when the audience monitor is still processing the RF acknowledgement packet and the delay period has ended.

Audience measurement activities occur in consumer households, shopping areas (e.g., stores, malls, etc.), and other areas where people may be exposed to advertisements and/or other media. To identify when a consumer was exposed to media content, what the media content contains and/or where the exposure to the media occurred, the consumer may be equipped with a mobile unit to record portions of the media content exposed to the consumer.
In some examples, the consumer is equipped with a mobile unit to record audio that may be present in an area to be monitored. Presented or rendered media, such as an advertisement or a kiosk feature presentation (e.g., at a library, a museum, an amusement park, etc.) may be presented in proximity to a base unit that can also collect audio information (e.g., a portion of presented media content). When both the mobile unit and the base unit collect audio information, one or more post-processing activities may be employed to match the collected mobile unit audio information with the collected base unit information, thereby allowing identification of consumer location and/or the type of media content to which the consumer was exposed.

This patent is subject to a terminal disclaimer.

Methods, systems, and apparatus to synchronize actions of audio source monitors


There is provided a barrier system for stopping land-based and water-based vehicles from entering predetermined areas. The barrier system, which may protect relatively wide spans, is capable of stopping relatively high mass vehicles traveling at relatively high speeds. The barrier system comprises an anchoring system, vertical supports, an energy absorption unit, a gliding bar, and a net system. The gliding bar is selectively moveable relative to the energy absorption unit and may selectively define an unfixed mode wherein the gliding bar is moveable relative to the energy absorption unit and a fixed mode wherein the gliding bar is fixed relative to the energy absorption unit. The net system is connected to the gliding bar such that converting the gliding bar from the unfixed mode to the fixed mode raises the net system to prevent passage of vehicles.

1. Field of the Invention
The present invention is related to vehicle barrier systems, and more particularly, to a barrier system that is selectively retractable.
2. Description of Related Art
Originally, net-based barrier systems with energy absorption devices at end supports were associated with aircraft arresting devices. These systems are designed so that the aircraft arresting net system is let out more than 100 feet upon impact and the aircraft slowly decelerates to a stop over a long distance, to minimize damage to the aircraft. Such systems are not directly applicable to vehicle barrier systems because the net system, energy absorption units, and end supports of vehicle barrier systems are designed to completely stop vehicle over a short distance regardless of the amount of damage caused to the vehicle.
Vehicle barrier systems rated to stop a 15,000 pound vehicle at impact speed of fifty miles per hour of the prior art include large sliding steel gates, steel bollards filled with concrete and anchored into footings, interlocking concrete surface barriers, horizontal steel bars with end supports, pop up steel plates, steel cable systems at short spans with fixed end supports, and other related barrier systems of the prior art. These barrier systems are limited by the length of area that can be secured without adding fixed supports that penetrate the subsurface, and this limitation is typically fifteen to sixty feet. In addition, these barrier systems require an electrical power supply, require backup power systems, and use hydraulics or pistons, resulting in maintenance, repairs, and downtime of the barrier. Many of these systems are not an "all weather" use. These barrier systems are either semi-fixed in-place and are not easily removed, or permanently fixed in-place and, therefore, permanently block off vehicle access to the secured area. Onsite installation of prior art systems can take several weeks. System components are neither modular nor disconnected easily. Barriers made of steel and concrete create additional projectiles upon an impact event, and require significant repair work in the aftermath to restore a barrier to operational status.

Retractable wide-span vehicle barrier system


In a hydraulic method and installation for shaping can bodies the can body is filled with a liquid and placed in a die and pressure is applied to the interior of said can body until it assumes the shape of said die.

1. Field of the Invention
The invention concerns a method of cold shaping a metal can body and a can body shaping installation adapted to implement it.
2. Description of the Prior Art
One prior art can shaping method is usually applied to can bodies assembled from at least two components, typically a tubular part and a bottom crimped to one end thereof. The tubular part may be a cylinder of circular, rectangular or square cross-section. This method uses a mechanism forming a core adapted to be inserted axially inside the can body through the opening thereof and having sectors adapted to be moved apart in the radially outward direction until they contact the inside wall of the can body to be shaped. This deforms the can body permanently and the resulting shape depends on the shape of the core sectors. In a system of this kind the deforming means and the actuating system thereof are essentially mechanical. Cans shaped in this way have shortcomings in respect of their appearance which are inherent to the shaping system itself. In particular, the imprints of the various sectors are visible on the can body walls. This means that the latter cannot have a perfectly regular surface. These imprints may even cause scoring of the varnish and lead eventually to corrosion. They may also lead to rupturing of the can. Additionally, the mechanism is complex and costly.


A retractable surgical instrument having a transversely preformed, curved operative element extendible from a straight, linear sheath. The operative element is retained in the retracted position until the distal tip of the instrument has been positioned at a work site. Cutting edges on the curved operative element may be formed in a variety of styles, one such style being embodied as an arthroscopic knife wherein the tip of the knife blade is preformed such that it maintains a transverse curve when it is extended to an operating position. The cutting edges of the transverse knife blade may extend longitudinally from the protective sheath in which case the edges are spaced from the inside surfaces of the linear sheath by the cooperative action of a raised bearing surface on the knife and the edge of the sheath adjacent the concave side of the curve as well as by laterally extending edge protection projections.

1. Field of the Invention
The invention relates generally to retractable devices which have an operating element movable between an exposed, working position and a covered, storage position. More particularly, the invention relates to manually operable retractable surgical devices which have uniquely shaped operative elements capable of being extended from a retracted position to a selected extended position.
2. Description of the Prior Art
Retractable cutting devices for use in surgical procedures are commonly known in the prior art. The retractable nature of such devices assures that the working or cutting surface of the instrument will be held retracted within the device in such a way as to not interfere with the placement of the device at the work site to be operated upon. Very often the working or operative portion of the instrument is at the distal end of a generally longitudinal support member. When the distal end has been moved past or through areas which are interposed between the entry point of the instrument and the work site, the operative portion of the instrument, often a cutting surface, may be extended from its protective sheath in order to perform the desired surgical procedure without unintentionally injuring surrounding tissue.
The present invention is particularly adaptable to small cutting instruments and is, therefore, intended primarily for use in arthroscopy or microsurgery of the knee and other joints in humans (or other animals). Consequently, for explanatory purposes, the invention will be described in terms of an arthroscopic knife. It will be understood, however, that the principles of this invention are equally applicable to other surgical, and even non-surgical, cutting and non-cutting devices. For these reasons, the disclosed preferred embodiment of the invention and the use herein of terms such as "knife", "cutting", "blades" and the like should not be considered as limiting the scope of the invention.
Arthroscopy involves the use of viewing, probing and cutting devices that can be utilized through a very small opening in the patient's skin. The procedure necessarily involves the steps of insertion, retraction and manipulation of various instruments or devices through the skin to an area to be operated upon. Such steps are primarily blind until the device comes into view of the arthroscope positioned at the work site through another opening. Consequently, it is desirable that any cutting or other potentially dangerous instruments be protected from either unintentionally injuring the patient or from being damaged by other tools during the blind maneuvers. Retractable cutting devices are obviously quite desirable in arthroscopic procedures.
In addition to the desirability of retractable devices, it should be apparent that numerous shapes of operating elements are desirable. Surgical and other operating elements may obviously be provided with a variety of different profiles suitable for different tasks. In arthroscopic applications, for example, it is often desirable to have a surgical element curved in a plane transverse to the blade plane, such a shape being more suitable for certain procedures than a straight single or double-edge knife. Prior art arthroscopic knives are known which have transversely curved cutting edges wherein the curve of the cutting blade is established and guided by the curve of the flattened, curved guide sheath situated at the distal end of the instrument and within which the blade reciprocates between a retracted and an extended position. Known examples of such curved surgical instruments are the 3M Sheathed Knives available from the Orthopedic Products Division of the Minnesota Mining and Manufacturing Company.
One disadvantage associated with instruments having a blade reciprocable within a transversely curved sheath is that it is more difficult to insert such instruments into the desired work site. The curved sheath must be manipulated through what is essentially a straight longitudinal bore previously formed in the tissue by an arthroscopic obturator or trocar. This must be done with extreme care to avoid injuring portions of the body or joint interposed between the entry point of the instrument and the work site. Moreover, in some instances the surgeon may choose to utilize a rigid cannula or portal through which the instruments must be inserted. In these cases use of a curved sheath is impossible.
One of the concerns that must be addressed in all reciprocable cutting instruments is that the cutting edges of the operative element must be somehow spaced from adjacent surfaces of the protective sheath in order to prevent the cutting edges from being dulled during the extension and/or retraction of the element.
In view of the above, it is an object of this invention to provide a retractable surgical instrument having a curved operative element encased within a linear sheath.
It is also an object of this invention to provide a retractable surgical instrument having a curved operative element encased within a flattened linear sheath.
It is another object of this invention to provide a retractable surgical instrument having a curved operative element encased within a distally located, flattened linear sheath wherein the cutting edges of the element are spaced from the inside surfaces of the sheath during extension and/or retraction of the element.
It is still another object of this invention to provide a retractable surgical instrument having a curved operative element encased within a distally located, flattened linear sheath wherein an indication is provided at the distal tip of the instrument of the direction of curvature of the element.
It is yet another object of this invention to provide a retractable surgical instrument having a curved operative element encased within a flattened linear sheath wherein the curve of the element is such that the distal tip of the element will, in an extended position be situated beyond the plane of either broad side of the flattened sheath.

Retractable surgical instrument with curved operative element


An ink for ink jet recording apparatuses contains water and a pigment dispersion containing a resin and carbon black. The ink additionally contains a surfactant including a compound expressed by the general formula (I) below, and the mass average molecular weight of the resin, the DBP oil absorption of the carbon black, the content of the resin with respect to the content of the carbon black in the pigment dispersion, and the dried-by-evaporation viscosity V40, which is the viscosity of the ink at the dryness of 40% by mass, are all within the respective predetermined ranges.

The present invention relates to an ink for ink jet recording apparatuses and also to an image forming method.
It has been strongly desired for inkjet recording apparatuses to increase the image forming speed without compromising image quality. Unfortunately, when an inkjet recording apparatus performs image forming at a high speed, a recording medium, such as paper, may be passed between a pair of ejection rollers to be ejected before the ink is permeated into the recording medium. Ink adhered to the ejection rollers (offset) may adhere to a recording medium, which may increase the risk of poor imaging.
The risk of poor imaging resulting from the offset may be suppressed by reducing the ejection amount of the ink. However, this arrangement may make it difficult to form images having a desired density. In view of the above, to suppress occurrence of the offset while ensuring formation of images having a desired density, numerous studies have been made on compounds which can be contained in an ink to improve permeability of the ink into a recording medium.
Compounds suggested as having an effect of improving permeability of the ink into a recording medium includes a compound containing straight-chain alkanol to which a specific amount of ethylene oxide and/or propylene oxide is added. Further, an ink containing the compound is also suggested.

Ink for ink jet recording apparatuses and image forming method


The present disclosure provides an integrated spray and wipe system. A method of using such a system is also provided. In one embodiment, the system includes a fluid reservoir that extends through the center of a roll of cleaning material (e.g., paper towel roll). The tool houses cleaning fluid and cleaning wipes and therefore can be used to dispense liquid or cleaning wipes as needed.

Spray bottles for spraying cleaning fluids are known. Cleaning wipe dispensers are also known. Typically, spray bottles and cleaning wipe dispensers are separate stand alone devices. Non-integrated spray and wipe devices can be difficult to transport and use in the field. An integrated spray and wipe system that would be easier to use and transport is desirable.


A variable capacitor modulator for use in a voltage controlled oscillator, includes a differential varactor block, coupling capacitors for connecting nodes of the varactor block to a tank circuit, and an element connected between the respective nodes and ground to trim the gain of the variable capacitor modulator.

The rapidly growing market of personal communication systems, radio medical implanted systems, and wireless hearing aids provides an increasing demand for more integrated and more efficient radio frequency (RF) integrated circuits (IC's). These IC's are required to operate with supply voltages under 2 V and sometimes down to 1V with minimum current consumption at frequencies up to several GHz.
The recent progress of CMOS technology has considerably improved the transmit freqeuncy of the CMOS devices and made CMOS technology a viable choice for RF integrated circuits allowing cost effective one chip solution.
The transmitter is one of the mostly power hungry blocks of wireless systems. For current saving it is beneficial to use a directly modulated voltage-controlled oscillator (VCO) that operates at the transmit frequency as a signal generator for the transmitter. The modulated signal from the VCO can be amplified by the output stage and applied to an antenna directly or via a filter.
This architecture is simple but very flexible since the output stage can control the output power over a wide range and the antenna parameters can vary with application.
A good example of this transmit architecture is presented by "1 GHz FM transmitter" operating in any 26 MHz band from 100-1000 MHz described in document NT2800 CHIP-MITTER, www.numatechnologies.com/pdf/NT2800.
In some cases when the antenna is made as a high Q inductor with the self-resonant frequency more than 70% above the transmit frequency it is possible that VCO itself can operate as a transmitter. It allows one to save the current used in the output stage.
In this solution the output power range is limited by 12-20 dB depending on the antenna parameters and the supply voltage. This is because the high power is determined by voltage supply while the low power is defined by the minimum level of sustained oscillations.
The major disadvantage of the transmit VCO is that the modulation index tends to depend on the transmit power. This is because the varactor cell based on a MOS capacitor has a relatively narrow voltage control range that closely correlates with the MOS transistor threshold voltage. The typical range is +/−0.5 V while the voltage swing across the tank could be up to several volts. Due to this fact the VCO frequency is sensitive not only to the control voltage applied to the varactor cell but also to the voltage swing across the VCO tank. This fact causes either the power range limitation or the index modulation variations.
The most popular CMOS VCO configurations are based on the differential approach (Andreani, S. Mattisson "On the use of CMOS varactors in RF VCO's," IEEE J. Solid States circuits, vol. 35, pp. 905-910, June 20) in which two differentially connected varactors or a complete varactor bridge are used for the frequency control (FIG. 1).
The differential approach provides the most efficient way to get high power and S NR under voltage supply limitation. Also control voltage is applied to the nodes with zero RF voltage so control voltage source does not cause additional losses in the LC-resonator.
The varactor block can be connected to the LC-tank circuit directly or via coupling capacitors (U.S. Pat. No. 6,621,365) intended to reduce the VCO gain (FIG. 2).
These coupling capacitors also reduce RF voltage swing across varactors and help to suppress frequency to power sensitivity.
In the direct modulation VCO modulation can be obtained by applying a modulation voltage to the varactor block in addition to the control voltage which sets the carrier centre frequency (FIG. 3).
The disadvantage of this approach is illustrated is that the high VCO gain (˜10 MHz/V) required for the PLL (phase locked loop) means that the modulation voltage swing necessary for peak-to-peak frequency deviation (0.5-2 MHz at 400 MHz) should be 0.05-0.2 V peak-to-peak. Too low level of modulation voltage makes it difficult to control modulation index accurately. Also this low modulation voltage level means low signal to noise ratio. VCO gain variation with RF voltage swing (RF power) also affects modulation index.
Another way to provide modulation is to add an additional varactor block, which is connected to the LC-tank in parallel to the varactor block used for carrier frequency control. The additional block has a separate control voltage input and lower gain (FIG. 4).
The lower gain permits a higher modulation voltage and a larger signal to noise ratio. The modulation index can be controlled not only by modulation voltage swing, but in addition by means of variable variable capacitance sensitivity of the modulation varactor block, leaving appropriate high gain required for PLL loop.
As mentioned above the lower gain can be achieved with the varactor block connected to the LC-tank via coupling capacitors. But coupling capacitors can not be used to trim the gain in the modulation varactor block because both their pins supplied with rather high voltage and CMOS switches used to connect coupling capacitor segments are less effective due to smaller gate to source voltage and higher resistance while thy will be in the RF current path. So they kill the resonator Q-factor or add too much parasitics. Switched capacitors connected parallel to the modulation varactor block are also not suitable for the same reason.
A known way (Chi-Wa Lo, H. C. Luong "A 1.5V 900-MHz Monolithic CMOS Fast-Switching Frequency Synthesizer for Wireless Applications", IEEE J. Solid-State Circuits, vol. 37, No 4, pp. 459-470, April 2002) is used to trim RF carrier frequency coarsely with switched capacitors connected between the VCO outputs and ground (FIG. 5).
This solution is not suitable for trimming the modulation varactor block sensitivity because these switched capacitors affect the total capacitance connected to the LC-tank, but do not affect the dC/dV. It might seem that the modulator gain would still be affected by these capacitors since frequency depends on relative tank capacitance deviation dC/C which depends also on the denominator, but the PLL actually keeps total LC-tank capacitance constant for certain RF carrier frequency, so the denominator is actually constant.
A variable modulator capacitor with trimmed gain can be obtained with solution shown in FIG. 6, where top pins of two arrays of switched varactors are connected to the LC-tank via coupling capacitors. Modulation voltage is applied to these top pins relative to ground via resistors. Bottom pins of the switched varactors can be connected to ground via NMOS switches depending on required modulator gain. The disadvantage of this solution is incomplete utilization of the varactor's C-V characteristic since only positive modulation voltage can be applied relative to ground. Also full power RF voltage and control voltage are applied to the same top pin of the varactor and resistors used to decouple modulator voltage source from RF voltage cause additional unwanted losses and parasitics in the LC-tank.


A system and method for characterizing an interference demodulation reference signal (DMRS) in a piece of user equipment (UE), e.g., a mobile device. The UE determines whether the serving signal is transmitted in a DMRS-based transmission mode; if it is, the UE cancels the serving DMRS from the received signal; otherwise the UE cancels the serving data signal from the received signal. The remaining signal is then analyzed for the amount of power it has in each of four interference DMRS candidates, and hypothesis testing is performed to determine whether interference DMRS is present in the signal, and, if so, to determine the rank of the interference DMRS, and the port and scrambling identity of each of the interference DMRS layers.

In Long-Term Evolution (LTE) systems, the user equipment (UE) receiving a desired signal (or "served signal") may also receive an interfering signal, which may degrade the user equipment's ability to receive the served signal. If the user equipment is in possession of a model of the interfering signal, it may be able to cancel the interfering signal, improving reception of the served signal, in an approach referred to as interference aware detection (IAD).
Thus, there is a need for a method and apparatus for forming a model of an interfering signal.

Method and apparatus for interference demodulation reference signal detection with serving signal cancellation


A unique composition of a 5-amino salicylic acid (5ASA) and a phospholipid is disclosed for treating Inflammatory Bowel Disease (IBD), where the composition can be a mixture, a molecular association complex or a covalent compound of 5ASA and a reactive phospholipid covalently bonded together via a diazo linkage and to methods for administering the compositions to treat symptoms of IBD.

1. Field of the Invention
The present invention relates to unique formulations for treating inflammatory bowel disease (IBD), such as ulcerative colitis, including 5-amino salicylic acid (5ASA) and a phospholipid.
The present invention relates to unique compositions of matter including 5ASA and phospholipid adapted to release 5ASA in a distal small intestine and/or colon, where lesions due to colitis or Inflammatory Bowel Disease (IBD) are present in order to enhance the anti-inflammatory efficacy of 5ASA. In certain embodiment, the phospholipid composition including from about 15 wt. % to about 95 wt. % of phosphatidylcholine (PC) in a bio-compatible carrier and/or resin. The present invention also relates to methods for making and administering the compositions of this invention orally, enterally and/or rectally.
2. Description of the Related Art
For a background of phospholipids and anti-inflammatory pharmaceuticals the reader is directed to U.S. Pat. Nos. 4,918,063; 5,043,329; 4,950,656; 5,032,585; 5,763,422; and 5,955,451 and PCT/US01/51605, incorporated herein by reference.
Inflammatory Bowel Disease (IBD) represents a family of ulcerative diseases including Ulcerative Colitis and Crohn's Disease that affect the colon and distal small bowel. These diseases are manifested by episodes of GI bleeding, diarrhea, fever, infection and in the most advanced cases, GI fistulation are manifested by perforation and cancer. 5ASA has been used medically to manage patients with IBD, though its effectiveness to keep patients in remission has been limited.
Although 5ASA is an effective treatment, there is a need in the art for 5ASA preparations having improved efficacy to treat IBD and to keep patients in remission.

Preparations of phospholipids and pharmaceuticals containing 5-amino salicylic acid for the treatment of inflammatory bowel disease

The Board of Regents of the University of Texas System


A transmission grating includes: first light-transmissive regions having a refractive index of n1; and second light-transmissive regions having a refractive index of n2 that is smaller than n1. Light-reflecting interfaces on which light transmitted through the first light-transmissive regions is incident are in parallel with one another and are inclined such that a line normal to each of light-reflecting interfaces is at an inclination angle θ with respect to the flat light-incident surface and to the flat light-emitting surface, wherein 0°<θ<90°. When a thickness of the first light-transmissive regions in a direction perpendicular to the light-reflecting surfaces is t1 and a thickness of the second light-transmissive regions in a direction perpendicular to the light-reflecting surfaces is t2, the thickness t2, in μm, is in a range of 0.1/π(n12−n22)1/2 to t1.

The present disclosure relates to a transmission grating and a laser device using the same, and a method of producing the transmission grating.
A wavelength beam combining (WBC) technique to increase the brightness of semiconductor laser device is known. In this technique, laser light (beams) emitted from a plurality of semiconductor laser elements are collimated by an optical element (collimate lens) into substantially parallel light and made incident on a wavelength dispersive element (reflection grating) such that the beams are overlapped by wavelength-dispersive properties of the diffraction grating (for example, described in "Laser Beam Combining for High-Power High-Radiance Sources" T. Y Fan, IEEE Journal of Selected Topics in Quantum Electronics, Vol. 11, No. 3, May/June 2005, pp. 567-577).

Transmission grating and laser device using the same, and method of producing transmission grating


A redundant electricity-conducting structure, and a method for making it, for use in a liquid crystal display ("LCD"). The LCD has a first layer and a second layer covering a portion of the first layer such that an edge is formed where the second layer starts. The redundant structure includes: a first conductor partially covering each of an area over the first layer and the second layer such that the first conductor must undergo a large change in surface direction where the conductor follows the edge contour of the second layer; and a redundant second conductor connected to and partially covering the first conductor at least in an area extending outside of an area under which is located the large change in surface direction. An example of the redundant electricity-conducting structure is where the first layer is a substrate, the second layer is a gate line, the first conductor is a data lien oriented perpendicularly to the gate line, the structure includes an insulating layer between the data line and the gate line, and the second conductor at least covers an area on the data line adjacent to and outside of intersection region of the data line with the gate line. Another example is where the first layer is an insulating layer, the first conductor is either a source or drain electrode for a transistor, and the second layer is a semiconductor layer connecting the source electrode to a drain electrode.

1. Field of the Invention
The present invention relates to an improved liquid crystal display (LCD) device and an improved method of forming the array of conductors in an LCD device and, more particularly, to an improved thin film transistor active matrix LCD device and an improved method of forming the thin film transistor active matrix LCD device, the improvement coming from being able to prevent conductors in the array from becoming cut by internal stresses in the conductors caused by step coverage.
2. Description of Related Art
Generally, an active matrix for use in an LCD device includes a thin film transistor (TFT) connected to each pixel via a pixel electrode. The TFT is connected to a gating circuit through a metal gate line and to a metal signal (or data) line for transmitting a signal from a driving circuit to a pixel electrode made of indium tin oxide (ITO).
As shown in FIG. 1, an active matrix of a liquid crystal display device includes a gate electrode 1 of a thin film transistor, which is connected to a gate line 5, a drain electrode 2 connected to a signal (or data) line 4, and a source electrode 3 connected to a pixel electrode 6. In such an active matrix, if the gate line is enabled(i.e., an increased voltage is applied on the gate line 5), then the TFT turns on and a picture signal, if any, inputted by the signal line 4 is transmitted to the pixel electrode 6. By selectively applying signals to all the pixels in an LCD, a desired picture appears on the liquid crystal display.
FIGS. 2 and 3 illustrate cross-sections of FIG. 1. The LCD uses the ITO on passivation (IOP) technique to form the pixel 6. The transparent ITO pixel 6 is prepared by the following method. First of all, after a metal such as Cr, Ta, Al, etc., is deposited on a substrate 10 by a sputtering method, it is patterned by a photoreading method and gate electrode 1 and gate line 5 are formed on the substrate. Thereafter, an insulating layer 9 such as SiNx, SiO.sub.2, etc., is deposited on the substrate 10 having the gate electrode 1 and the gate line 5 formed thereon. Then, a semiconductor layer 7 is deposited thereon by the plasma CVD (chemical vapor deposition) method, and subsequently patterned.
Subsequently, a metal composed of Al or Al alloy is deposited by sputtering and then is patterned to form the signal (or data) line 4, the drain electrode 2 and the source electrode 3. Then a protective layer 8 is deposited thereon. After a contacting hole 11 is formed in the protective layer 8 (located at the end of the source electrode 3) by patterning, the pixel electrode 6 is formed on a pixel region of the substrate 10 and also is formed in the contacting hole region so that the pixel electrode 6 connects to the source electrode 3.
However, such a conventional active matrix for a liquid crystal display device as shown in FIGS. 1, 2 and 3, suffers from a number of problems. For example, the signal(or data) line or the source and drain lines frequently are cut because the overlying lines, being made of metal, are susceptible to the weaknesses of conforming to a stepped shape. That is, the signal or data line 4 can become cut due to having to conform, i.e., cross the stepped shape of the gate line 5 at the portion B where the gate line 5 crosses under the signal line 4. Alternatively, the source and drain electrodes 2 and 3 can become cut at the portion A (FIG. 1) of TFT due to the weaknesses imposed by the step coverage.

Redundant conductor structure for an LCD and method for formation thereof


A vending machine for vending a plurality of cans includes a storage means for storing plurality of cans to be vended, an article dispensing rod which is both pivotable and moveable in a vertical direction to control the movement of cans from the storage means to a dispensing station. A coin mechanism is provided having an output shaft operatively connected to the dispensing rod to effect both vertical movement of the dispensing rod and pivotable movement thereof. The movement of the dispensing rod by the output shaft of the coin mechanism enables the dispensing rod to control the movement of cans from the storage means to the dispensing station where the cans can be received by a user of the vending machine. A lockout mechanism is provided to prevent actuation of the coin mechanism and the dispensing rod when there are no cans present to be vended in the can storage means.

Vending machines are well known for vending articles such as canned soda. Many known prior art vending machines cost in the range $5,000 to $6,000 and include complicated and costly mechanisms for dispensing articles and for determining when a particular storage rack in the vending machine is empty.
The present invention overcomes the disadvantages associated with the prior art vending machines by providing a low-cost vending machine having a simple dispensing mechanism and means for sensing the absence of cans to be vended in the storage means and for locking the dispenser mechanism to prevent actuation thereof when there are no more cans to be vended in the can storage means.

Vending machine for cans with dispensing rod


To provide a structure for mounting a fuel tank on a vehicle body that can prevent harmful deformation of the fuel tank that would impair the function of the fuel tank in either case where the pressure in the fuel tank changes to a positive pressure or to a negative pressure, the structure for mounting a fuel tank on a vehicle body includes: a band lower (10L) secured to the vehicle body, extending along at least a lower wall (19L) of the fuel tank (1) and holding the fuel tank (1); a lower wall connecting means (40) that connects at least one part of the lower wall (19L) of the fuel tank (1) to the band lower (10L); a holding member (50) secured to the vehicle body and holding the fuel tank (1); and an upper wall connecting means (40) that connects at least one part of the upper wall (19U) of the fuel tank (1) to the holding member.

A structure is known in which, to mount a fuel tank on a vehicle body, a band is passed through a groove formed in a surface of the fuel tank and the both ends of the band are bolted to the vehicle body such that the fuel tank is securely mounted with the surface of the fuel tank being pressed against the vehicle body via a rubber cushion (Patent Document 1). According to Patent Document 1, this structure can suppress an independent oscillation of the fuel tank.
Also known is a structure in which ends of two upper bands passed along an upper surface of a fuel tank in the fore-and-aft direction of the vehicle body are overlapped with corresponding ends of two lower bands passed along a lower surface of the fuel tank in the fore-and-aft direction of the vehicle body, and the front ends of the bands are fastened to the first cross member of the vehicle by means of bolts and nuts while the rear ends of the bands are fastened to the second cross member in a similar manner (Patent Document 2). According to Patent Document 2, this structure allows the fuel tank to be secured on the vehicle body.
Further, a structure is known in which a securing member, which has a metallic threaded member (such as a nut) embedded in a resin member integrally formed of multiple layers of permeation-resistant resin and weldable/adhesive resin, is welded onto an upper surface of a fuel tank, and the fuel tank is mounted on the vehicle body via the securing member (Patent Document 3). According to Patent Document 3, this structure allows the fuel tank to be mounted firmly on the vehicle body.
Also known is a structure for attaching an accessory component such as a protector onto an exterior of a fuel tank, which includes: a recess defined in the surface of the fuel tank; an accessory component having a through-hole and to be attached to the exterior of the fuel tank; a first fastener disposed on an inner side of the accessory component with respect to the fuel tank; and a second fastener disposed on an outer side of the accessory component, wherein the first and second fasteners sandwich the accessory component therebetween and extend through the through-hole to engage with a claw provided on an inner circumference of the recess (Patent Document 4). According to Patent Document 4, this structure allows the accessory component to be attached to the fuel tank by simply providing the surface of the fuel tank with a recess.

Structure for mounting fuel tank on vehicle body and device for preventing deformation of fuel tank


A printed circuit board may include a controller socket, first and second sockets provided on a top surface, third and fourth sockets provided on a bottom surface, and first, second, and third branching points. The first branching point may be spaced apart from the controller socket by a first distance in a horizontal direction parallel to the top surface and may be electrically connected to the controller socket. The second branching point may be spaced apart from the first branching point by a second distance longer than the first distance and may be electrically connected to the first branching point, the first and third sockets. The third branching point may be spaced apart from the first branching point by a third distance longer than the first distance and may be electrically connected to the first branching point, the second and fourth sockets.

Example embodiments relate to a semiconductor memory. For example, at least some example embodiments relate to a printed circuit board and/or a storage device including a printed circuit board.
Semiconductor memory devices may be classified into volatile memory devices (e.g., a static random access memory (SRAM), a dynamic RAM (DRAM), and a synchronous DRAM (SDRAM)), which lose data stored therein at power-off, and non-volatile memory devices (e.g., a read only memory (ROM), a programmable ROM (PROM), an electrically programmable ROM (EPROM), an electrically erasable and programmable ROM (EEPROM), a flash memory device, a phase-change RAM (PRAM), a magnetic RAM (MRAM), a resistive RAM (RRAM), and a ferroelectric RAM (FRAM)), which retain data stored therein even at power-off.
In a FLASH-memory-based storage device, various operations are executed based on electric signals. As an example, a storage device may include a controller and non-volatile memory devices, which are configured to communicate with each other through a plurality of signal lines. In order to improve reliability of the storage device, many schemes are being conducted to maintain reliability of signals. However, owing to increasing demand for a storage device with a fast operation speed and a high integration density, it may be difficult to maintain the signal reliability.

Printed circuit board and storage device including printed circuit board


The present invention relates a method of producing a data storage medium comprising the steps of: a) coating a layer comprising a polymer material onto at least a part of a template surface thereby to obtain a modified template surface; b) clamping the modified template surface produced in step (a) with a target surface thereby to obtain an assembly; and c) introducing a liquid to an environment of the assembly obtained in step (b) thereby to transfer the layer comprising the polymer material of the modified template surface onto at least an adjacent region on the target surface.

A data storage device based on the atomic force microscope (AFM) is disclosed in "The millipede—more than 1,000 tips for future AFM data storage" by P. Vettiger et al., IBM Journal Research Development, Vol. 44, No. 3, March 2000. The storage device has a read and write function based on a mechanical x-, y-scanning of a storage medium with an array of probes each having a tip. The probes operate in parallel, with each probe scanning, during operation, an associated field of the storage medium. The storage medium comprises a polymer layer. The tips, which each have a diameter of between 20 nanometers (nm) to 40 nm, are moved across the surface of the polymer layer in a contact mode. The contact mode is achieved by applying forces to the probes so that the tips of the probes can touch the surface of the polymer layer. For this purpose, the probes comprise cantilevers, which carry the tips on their end sections. Bits are represented by indentation marks or non-indentation marks in the polymer layer. The cantilevers respond to these topographic changes while they are moved across the surface of the polymer layer during operation of the device in read/write mode.
Indentation marks are formed on the polymer layer by thermomechanical recording. This is achieved by heating the tip of a respective probe operated in contact mode with respect to the polymer layer. Heating of the tip is achieved via a heater dedicated to the writing/formation of the indentation marks. The polymer layer softens locally where it is contacted by the heated tip. The result is an indentation being produced on the layer that has, for example, a nanoscale diameter comparable to the diameter of the tip used in its formation.
Reading is also accomplished by a thermomechanical concept. The probe is heated using a heater dedicated to the process of reading/sensing the indentation marks. In this case, the probe is heated but not so as to cause heating of its associated tip. That is, the heating temperature is not enough to soften the polymer layer as is necessary for writing. The thermal sensing is based on the fact that the thermal conductance between the probe and the storage medium changes when the probe is moving in an indentation as the heat transport is in this case more efficient. As a consequence of this, the temperature of the cantilever decreases and hence its electrical resistance changes. This change of electrical resistance is then measured and serves as the measuring signal.
Presently, polymer layers for use in storage devices described above are prepared by spin coating a polymer of choice onto a substrate such as, for example, a silicon wafer. The surface roughness of a polymer layer that is produced with this method is on the order of, for example, 1 to 2 nm when measured over a typical bit dimension length scale.
As described above, information is encoded into the polymer layer in the form of indentation marks and non-indentation marks. Taking into account the surface roughness values typically obtained with spin coating, it is desirable to achieve a signal-to-noise ratio (SNR) of >10 dB over the lifetime specification of the storage device for sensing the information. In order to achieve such a sensing margin, each of the indentations should typically be formed with a depth on the order of, for example, 10 nm. Since the lateral dimensions of the indentations are on the same order of magnitude as their depth, it is inevitable that the recording density of the storage device is accordingly limited.
Accordingly, it is desirable to provide a method of producing a data storage medium that, when incorporated in a data storage device, allows for an increased recording density to be attained by such a device compared to a data storage medium produced using previously-proposed methods such as, for example, spin coating.

Method of producing a data storage medium

International Business Machines Corporation


A method of automatic gain control in both analog and digital domain is performed by receiving an incoming analog signal, determining an overall gain factor, determining a coarse analog gain control value and a fine digital gain control value, each of which, when taken together substantially equals the already determined overall gain factor, modifying the incoming analog signal using the coarse analog gain control value to form a coarsely adjusted digital signal, digitizing the coarsely adjusted digital signal, and using the fine digital gain control value to process the coarsely adjusted digital signal to form an outgoing digital signal, wherein the outgoing digital signal has been modified in both the analog domain and subsequently in the digital domain to achieve an appropriate signal to noise ratio.

1. Field of the Invention
The invention describes a hybrid automatic gain control (AGC) method and apparatus suitable for normalizing (by attenuation or amplification) dynamic range of analog input signal.
2. Description of Related Art
In conventional automatic gain control (AGC) systems, an input analog signal is normalized in either the analog domain or the digital domain. Conventional AGC is performed by measuring a particular parameter of the input analog signal (i.e., the sync height of a composite video signal, for example) and based on that measurement, the desired gain is calculated and applied to the input signal. In the digital domain, AGC implemented using a feed-forward type arrangement whereas in the analog domain, a feedback system is employed. Although digital domain type AGC is inexpensive to implement and fast, the output signal can exhibit coarse granularity due to the discrete nature of the multiplication in the digital domain. Even though AGC in the analog domain is continuous in nature, analog AGC is costly to implement and is subject to a very slow response, or oscillations, when confronted with sudden changes in the input signal.
Therefore, what is desired is a cost effective, system, method, and apparatus for providing both fast and high resolution automatic gain control (AGC).


An air cleaner that is capable of efficiently and effectively purifying and humidifying air. An air flow passage from air filters (4, 5) to a blower (8) is branched to first and second air flow passages (31, 32), and then these air flow passages join. A humidifying filter (14) is disposed in the first air flow passage (31), and a movable plate (35) for opening and closing the humidifying filter is disposed in the second air flow passage (32). The air cleaner comprises a control part (40) for controlling the opening and closing operation of the movable plate (35) and the rotating operation of the blower (8). A recess containing the air filters (4, 5) is formed in the front of the body (2) of the air cleaner. An air flow passage extending from under the recess to the back of the recess and bent upward is horizontally partitioned into upper and lower parts by a partition wall (27) to form the first air flow passage (31) and the second flow passage (32) in this order from the bottom. The movable plate (35) is a flat plate rotated around a pivotal axis (36) formed along one lateral side.

Various matters such as dust, pollen, tobacco smoke, breathed-out air and the like that are disagreeable or harmful to the human body are contained in air in a room (room air). Especially, in recent years, because houses are often closed completely, such harmful matters easily collect in a room. Accordingly, conventionally, windows of a room are sometimes opened for spontaneous ventilation. However, as a matter of fact, it is hard to carry out spontaneous ventilation as desired in an area where air pollution is serious, at home or in an office if there is a family member or a colleague who is suffering from hay fever. In such situation, an air cleaner that has an air cleaning function to clean room air is generally becoming widespread.
Generally, an air cleaner is equipped with an air filter on the front of its main body, and an air flow passage in which a blower is disposed is formed inside the main body. The air flow passage extends from an opening of the main-body front to an outlet of an upper portion of the main body. Such an air cleaner sucks room air, that is, outside air into the air flow passage through the air filter as the blower rotates, and sends out the sucked air into the room, that is, the outside through the outlet. Here, harmful matters contained in the air are caught, adsorbed, or decomposed by the air filter to be removed so that the air is cleaned.
Further, for the purpose of adjusting room air to obtain a more comfortable condition, some air cleaners have a humidifying function besides the air cleaning function. In an air cleaner having the humidifying function, a humidifying filter that contains water is so disposed as to close a portion of the sectional region of the air flow passage, and part of the air that is cleaned by the air filter absorbs water when it goes through the humidifying filter, thereby the air is humidified (e.g., see patent document 1).    [Patent document 1]: JP-A-2006-46729


An input signal detecting circuit includes a plurality of comparators configured to output a plurality of differential output signals in response to a differential input signal, respectively; and a differential exclusive OR circuit configured to output an exclusive OR resultant signal from the plurality of differential output signals outputted from the plurality of comparators. In at least one of the plurality of comparators, a DC operation voltage is changed in response to a control signal supplied to the comparator.

1. Field of the Invention
The present invention relates to an input signal detecting circuit for detecting a differential signal. This Patent application is based on Japanese Patent application No. 2007-057315. The disclosure thereof is incorporated herein by reference.
2. Description of Related Art
In recent years, data transfer between computers has been changed from a parallel transfer to a serial transfer in which transfer speed is fast. A circuit for recognizing reception of a signal when the signal is transmitted and received (hereinafter, to be referred to as an input signal detecting circuit) is standardized in the physical layers in many interfaces such as USB (Universal Serial Bus), PCI-Express (Peripheral Component Interconnect), SATA (Serial AT Attachment), and SAS (Serial Attached Small Computer System Interface). Also, each of the standards defines a value of the input signal amplitude. In order that such standardized circuits operate normally, it is important that an input signal has an amplitude within a range in the standard, independently of the use environment of the circuit.
One of the especially important factors in the environment under which a circuit is used is a temperature. Typically, in many cases, an interface unit uses an analog circuit, and an analog circuit uses a differential comparing circuit. Also, the differential comparing circuit uses elements such as transistors and resistors. The transistor has a transfer conductance [S] (hereinafter, to be referred to as gm), and a voltage amplification factor of the differential comparing circuit is determined based on a load resistance and gm. When the thickness of a gate oxide film of the transistor is represented as Tox, a dielectric constant of the gate oxide film is represented as εox, the vacuum dielectric constant is represented as εo, and a mobility of a carrier is represented as μ, a capacitance Cox of the gate oxide film is represented by the following equation (1).
                              C          ox                =                                            ɛ              ox                                                  ɛ              o                                            T            ox                                              (        1        )
Also, when a product of the capacitance Cox of the gate oxide film and the carrier mobility μ is represented as β and a current flowing between the drain and the source in the transistor is represented as Ids, a gate width of the transistor is represented as W, and a gate length of the transistor is represented as L, the transfer conductance gm can be represented by the following equation (2).gm=√{square root over (2×β×Ids×W×L)}  (2)
With reference to the equation (2), the transfer conductance gm varies in accordance with the temperature because the product β and the current Ids are included. Such variation of gm dependent on temperature has influence on the output amplitude of the differential comparing circuit. That is, the output amplitude of the differential comparing circuit is increased or decreased on the basis of the temperature. The input signal detecting circuit to which the differential comparing circuit is applied has a temperature condition under which the input signal within the range of the standard cannot be detected.
One conventional example of the input signal detecting circuit is Japanese Patent Application Publication (JP-P2006-054742A: first conventional example). FIG. 1 shows the configuration of the input signal detecting circuit disclosed in the first conventional example. With reference to FIG. 1, the conventional input signal detecting circuit includes differential comparing circuits CMP7 and CMP8 and an exclusive OR EOR3. Hereinafter, an N-channel MOS (Metal Oxide Semiconductor) transistor and a P-channel MOS transistor are referred to as an NMOS transistor and a PMOS transistor, respectively. The differential comparing circuit CMP7 includes NMOS transistors Mn9 and Mn10 as a differential pair, resistors R9 and R10 serving as load resistances, and a constant current source Ib7. One end of the constant current source Ib7 is connected to the sources of the NMOS transistors Mn9 and Mn10, and one end of the resistor R9 is connected to the drain of the NMOS transistor Mn9, and one end of the resistor R10 is connected to the drain of the NMOS transistor Mn10. The other end of the resistor R9 and the other end of the resistor R10 are connected to a power supply voltage VDD. The other end of the constant current source Ib7 is grounded. The differential comparing circuit CMP8 includes NMOS transistors Mn11 and Mn12 as a differential pair, resistors R11 and R12 serving as load resistances, a resistor Rb1 to supply an offset voltage Voff1, and a constant current source Ib8. One end of the constant current source Ib8 is connected to the sources of the NMOS transistors Mn11 and Mn12, and one end of the resistor R11 is connected to the drain of the NMOS transistor Mn11, and one end of the resistor R12 is connected to the drain of the NMOS transistor Mn12. The other end of the resistor R11 and the other end of the resistor R12 are connected to one end of the resistor Rb1, and the other end of the resistor Rb1 is connected to the power supply voltage VDD. The other end of the constant current source Ib8 is grounded.
The gates of the NMOS transistors Mn9 and Mn11 are connected to an input terminal to which an input signal SINP is supplied, and the gates of the NMOS transistors Mn10 and Mn12 are connected to an input terminal to which an input signal SINN is supplied. The NMOS transistor Mn9 is connected to the resistor R9 through a node N9. The NMOS transistor Mn10 is connected to the resistor R10 through a node N10. The NMOS transistor Mn11 is connected to the resistor R11 through a node N11. The NMOS transistor Mn12 is connected to the resistor R12 through a node N12. A differential output signal CMP7out, which is composed of an output signal CMP7outP as a positive (normal) phase signal and an output signal CMP7outN as a negative (opposite) phase signal, is outputted from the nodes N9 and N10. A differential output signal CMP8out, which is composed of an output signal CMP8outP as a positive (normal) phase signal and an output signal CMP8outN as a negative (opposite) phase signal, is outputted from the nodes N11 and N12. The exclusive OR EOR3 is connected to the nodes N9 to N12 and outputs a signal of an exclusive OR result between the differential output signal CMP7out and the differential output signal CMP8out (an output signal Sout (binary signals Sout3P and Sout3N)).
FIGS. 2A, 2B and 2C are timing charts of the operation signals at nodes in the input signal detecting circuit according to the conventional example. With reference to FIG. 2A, a differential input signal SIN is composed of the input signal SINP as the positive phase signal, and the input signal SINN as the negative phase signal, and is supplied to the input signal detecting circuit. It is supposed that the detection of the differential input signal SIN is not required between a time t1 and a time t5, and the detection of the differential input signal SIN is required between the time t5 and a time t9. The input signal SINP is supplied to the NMOS transistors Mn9 and Mn11, and the input signal SINN is supplied to the NMOS transistors Mn10 and Mn12. When a load resistance of the differential comparing circuit is assumed to be RL and a voltage (amplitude) of the input signal to the differential comparing circuit is assumed to be Vin, a voltage (amplitude) Vo of the output signal from the differential comparing circuit is represented by the following equation (3).Vo=gm×RL×Vin  (3)Here, the voltages of the input signals SINP and SINN are assumed to be SINP and SINN, respectively, the voltages of the output signals CMP7outP, CMP7outN, CMP8outP and CMP8outN are assumed to be CMP7outP, CMP7outN, CMP8outP and CMP8outN, respectively, and the resistances of the resistors R9, R10, R11 and R12 as the load resistances are assumed to be R9, R10, R11 and R12, respectively. At this time, the equation (3) is represented by the following equations (4) and (5).CMP7outP−CMP7outN=rm×R9×(SINP−SINN)  (4)CMP8outP−CMP8outN=rm×R11×(SINP−SINN)  (5)Here, R9=R10 and R11=R12.
As shown by the equations (4) and (5), the input signal SIN (SINP−SINN) is amplified for the values of gm×R9 and gm×R11 as the voltage amplification factors of the differential comparing circuits CMP7 and CMP8 and is outputted as the differential output signals CMP7out (CMP7outP−CMP7outN) and CMP8out (CMP8outP−CMP8outN) of the differential comparing circuits CMP7 and CMP8 (refer to FIG. 2B).
DC operation voltages Vo7P and Vo7N of the output signals CMP7outP and CMP7outN of the differential comparing circuit CMP7 are determined from the following equations (6) and (7) by using the power supply voltage VDD, the resistors R9 and R10 and the constant current source Ib7 (a current value Ib7).
                                          V            o                              7                    P                =                  VDD          -                                    R                                                                                10              ×              Id                                                                                7                        2                                              (        6        )                                                      V            o                              7                    N                =                  VDD          -                                    R                                                                                9              ×              Id                                                                                7                        2                                              (        7        )
On the other hand, DC operation voltages Vo8P and Vo8N of the output signals CMP8outP and CMP8outN of the differential comparing circuit CMP8 are calculated by using the power supply voltage VDD and the resistors Rb1 (the resistance value Rb1), R11 and R12. When the power supply voltage VDD, the resistors R9 and R10, R11 and R12, and the constant current sources Ib7 and Ib8 are the same power source, the same resistor and the same current source, the DC operation voltages Vo8P and Vo8N and the DC operation voltages Vo7P and Vo7N are separated by an offset voltage off1 indicated in the following equation (8).Voff1=Rb1×Ib8  (8)
Under this environment, the amplitude (SINP−SINN) of the differential input signal SIN is small between the time t1 and the time t5. As a result, the differential output signal CMP7out of the differential comparing circuit CMP7 and the differential output signal CMP8out of the differential comparing circuit CMP8 do not cross. On the other hand, since the amplitude of the differential input signal SIN is great between the time t5 and the time t9, the differential output signal CMP7out and the differential output signal CMP8out cross. The exclusive OR EOR3 compares the output signal CMP7outP and the output signal CMP8outN, and determines to be a logic level "1", if the output signal CMP7outP is higher in voltage than the output signal CMP8outN, and determines to be a logic level "0" if the output signal CMP7outP is lower than the output signal CMP8outN. At the same time, the exclusive OR EOR3 compares the output signal CMP7outN and the output signal CMP8outP, and determines to be the logic level "1" if the output signal CMP8outP is higher in voltage than the output signal CMP7outN, and determines to be the logic level "0" if the output signal CMP8outP is lower in voltage than the output signal CMP7outN.
With reference to FIG. 2C, with the relation between the output signals Sout3P and Sout3N of the exclusive OR EOR3, when these two logic levels are all "1" or "0", the output signal Sout3N is higher in voltage than the output signal Sout3P (a logic level "1"). On the contrary, when the two logic levels are different, the output signal Sout3N of the exclusive OR EOR3 is lower in voltage than the output signal Sout3P (a logic level "0"). In this way, when the differential input signal SIN having an amplitude to be detected is supplied, the logic level "0" is outputted as the output signal Sout. As mentioned above, the input signal detecting circuit according to the conventional examples can detect the differential input signal SIN so that the differential output signals CMP7out and CMP8out having amplitudes equal to or higher than the offset voltage Voff1 are obtained. That is, a threshold voltage (hereinafter, to be referred to as a detection threshold voltage) of the differential input signal SIN is set in accordance with the offset voltage Voff1 determined by the equation (8) such that the differential input signal SIN can be detected by the input signal detecting circuit according to the conventional example.
As shown in the equations (4) and (5), the amplitudes of the differential output signals CMP7out and CMP8out are determined in accordance with the transfer conductance gm whose value varies dependently on temperature. For this reason, even when the detectable differential input signal SIN, (having the amplitude equal to or higher than the detection threshold voltage is supplied, there would be a case that the differential output signals CMP7out and CMP8out having the correct amplitude cannot be outputted due to the influence of a peripheral temperature.
The equations (4) and (5) described in the operation of the above conventional circuit indicate a relation between the input and output of the differential comparing circuit. The voltage amplification factor of the typical voltage amplifying circuit is defined as (output voltage)/(input voltage)=voltage amplification factor=gm×RL, where RL is the load resistance. When this is applied to the differential comparing circuits CMP7 and CMP8 of the input signal detecting circuit according to the conventional example, the following equations (9) and (10) are obtained.
                                          (                                          CMP                                                                                7                                outP                            -                              CMP                                                                                7                                outN                                      )                                SINP            -            SINN                          =                  gm          ×          R                                                              9                                    (        9        )                                                      (                                          CMP                                                                                8                                outP                            -                              CMP                                                                                8                                outN                                      )                                SINP            -            SINN                          =                  gm          ×          R                                                              11                                    (        10        )
As shown in the equation (2), the temperature variation in the transfer conductance gm results from the current flowing through the transistor and the product β of the capacitance Cox of the gate oxide film and the carrier mobility μ. In particular, a temperature variation amount of the transfer conductance gm dependent on the temperature variation in the carrier mobility μ is great, which causes a severe variation in the voltage amplification factor represented by the equations (9) and (10). On the other hand, when the offset voltage Voff1 is assumed to be stable for the temperature, the detection threshold voltage of the differential input signal SIN can be also assumed to be stable.
FIGS. 3A and 3B are diagrams showing the waveforms of the differential output signals 7out and 8out when the differential input signal SIN having an amplitude of the detection threshold voltage or more is supplied to the input signal detecting circuit according to the conventional example. FIGS. 3A and 3B show the waveforms when the peripheral temperature is −25° C. and 75° C. With reference to FIGS. 3A and 3B, even when the peripheral temperature varies from −25° C. to 75° C., the DC operation voltages Vo7P (Vo7N) and Vo8P (Vo8N) in the differential comparing circuits CMP7 and CM8 are 800 mV and 760 mV, respectively, and they does not almost vary. That is, the offset voltage is 40 mV, which is constant independently of the temperature. On the other hand, although the amplitudes of the differential output signals CMP7out and CMP8out are 50 mV at the temperature of −25° C., they decrease to 35 mV at the temperature of 75° C. In this case, the differential output signal 7out and the differential output signal 8out are separated by 5 mV, and the differential input signal SIN cannot be detected. In this way, there would be a case that the originally detectable input signal cannot be detected because the peripheral temperature increases.
Typically, the input signal detecting circuit for detecting a very small signal is strongly required to provide a high sensibility and simultaneously avoid erroneous detection. As a result, a detection voltage range, namely, an allowable range of the detection threshold voltage (the amplitude) becomes narrow. For this reason, it is necessary to reduce or remove detection irregularity caused based on peripheral temperature, as mentioned above.


An LDMOS device and a method for forming the LDMOS device are provided. The LDMOS device includes: a substrate formed with a source region, a drain region and a drift region; a gate structure; a silicide block layer; a first conductive structure having one end electrically connected with the source region, a second conductive structure having one end electrically connected with the drain region; a first metal interconnecting structure electrically connected with the other end of the first conductive structure, a second metal interconnecting structure electrically connected with the other end of the second conductive structure; a third conductive structure having one end disposed on a surface of the silicide block layer; and a third metal interconnecting structure electrically connected with the other end of the third conductive structure. The LDMOS device has increased breakdown voltage, and reduced on-resistance, and its preparation process is safer and easier to control.

Lateral Diffused Metal Oxide Semiconductor (LDMOS) devices have been used in many fields, such as mobile phones, LED displays, LCD display drivers, or high power amplifiers in wireless base stations, due to their performance advantages in linearity, power gain and breakdown voltage.
In order to improve the breakdown voltage, conventional LDMOS devices are disposed with a field plate to deplete a drift area. However, existing scheme for improving breakdown voltage may bring an increase in an on-resistance of the LDMOS device. Therefore, there is a need for a method for improving the breakdown voltage without lowering the on-resistance of the LDMOS device.

LDMOS device and method for forming the same

Shanghai Huahong Grace Semiconductor Manufacturing Corporation