A dual channel video data recovery system for use in a bar code scanner. A first and a second video signal are generated in parallel in response to light reflected from a bar code. The first and second video signals are received and filtered to limit their frequency ranges and produce filtered first and second video signals. The first and second filtered video signals are limited to different and preferably coverlapping frequency ranges. The first and second video signals have differing thresholds which may be dynamically varied. The first and second filtered video signals are converted to first and second digital data strings. If both strings contain useful data, the string containing the higher-quality data is decoded to recover bar code information. If only one string contains useful data, the string containing useful data is decoded.

The present invention relates generally to improvements in optical bar code scanners. More particularly, the invention relates to methods and apparatus for dual video channel data recovery and advantageous thresholding techniques which may be employed in conjunction therewith.
Optical scanners, and especially bar code scanners, are in wide use in a variety of applications, and serve to increase the accuracy and efficiency of data acquisition wherever they are used. In typical use, a standardized bar code label is affixed to an object, the bar code carrying an identifying number for the object. The object is passed along a scan field, where the bar code reflects light emitted by a laser or other light source, and reflects the light back to a data acquisition channel. The data acquisition channel decodes the reflected pattern and uses the decoded information to retrieve data associated with the object.
Objects with bar code labels are typically moved across the scan field manually, at varying rates of speed. Further, the distance from the scanner window will typically vary from scan to scan. The further the label is from the window the higher the frequency in the captured signal for the bar code label. Therefore, the frequency of the light modulation captured by a scanner may vary from one scan to another, and even within the same scan. Moreover, it is desirable to be able to use bar code labels of varying sizes with the same scanner. The use of different-sized bar code labels also varies the frequency of the modulated light pattern captured by the capturing mechanism. It is therefore desirable to maximize the frequency range over which the data recovery of the bar code scanner operates.
Bar code labels are also subject to certain paper and printing imperfections, which cause interference with a successful scan. Labels with numerous imperfections are typically read at one threshold extreme or the other. For example, a high level of noise resulting from paper and printing imperfections may be thresholded out using a higher DC threshold level. However, the risk that is run is that this high threshold might also threshold out a weak signal for an actual bar code bar. On the other hand, for a low contrast bar code, where the background paper is rough and off white or the ink is not dark enough, a low threshold might be employed because a weak bar code signal would be likely. In this instance, noise or bar code imperfections exceeding the low threshold may be detected as bar code intervals. A variety of other scanning circumstances effect the appropriate choice of threshold, but, in short, a single threshold is not well suited to addressing all of the typical real world variations.
Bar code scanners of the prior art typically include a single data recovery channel with a limited frequency range and a single threshold which may have both a DC and an AC component. Noise is typically limited by a single bandpass filter. This increases the likelihood that a label with severe imperfections will require repeated attempts to scan, or will fail to scan altogether, as the imperfect label is more likely to produce a response that falls outside the acceptable frequency range.
There exists, then, a need in the art for a bar code scanner having dual data recovery channels which satisfactorily limit or filter out noise but which provide a broader frequency range sufficient to decode labels having imperfections which produce frequencies at one end of the range or the other. Further, it is highly desirable to have a dynamic thresholding arrangement which is adjusted in real time to adapt to observed scanning conditions as described further below.
A video data recovery system according to the teachings of the present invention preferably includes first and second video signal generators for generating first and second video signals in response to light recovered from the reflection from a bar code. The data recovery system further includes first and second video signal receivers for receiving the first and second video signals, and first and second filters for limiting the frequency range of each of the first and second video signals, thereby producing first and second filtered video signals. The first and second filters limit the first and second video signals to differing but overlapping frequency ranges. The first and second video signals have differing thresholds applied. The first and second filtered and thresholded video signals are furnished to first and second analog-to-digital converters, respectively, to produce first and second digital data strings. If both of the first and second digital data strings contain useful data, the string containing higher-quality data is decoded to recover the bar code information. If only one of the first and second digital data strings contains useful data, that string is decoded. Further, the thresholds may advantageously set to aggressively threshold on one channel and to less aggressively threshold on the other channels with dynamic threshold adjusts being possible to adapt to the scan environment.

Methods and apparatus for dual channel video recovery in bar code scanners


Batteries for boats and vehicles require a CRA (cranking) battery 23 and an AUX (auxiliaries) battery 22 to ensure a start. The preferred version has an AUX battery made of parallel plates and a CRA battery made of parallel plates lying in a monobloc case in face to face positions. Each battery has a pair of CRA terminals 20, 30 for the electric starter and a pair of AUX terminals 19, 31 for the AUX loads of the vehicle and the alternator. The AUX and CRA negative are joinable by a link or a switch 41 so that a single earth connection is made to the vehicle. Alternatives show the AUX and CRA batteries side by side, at 90 degrees, providing 24 v or 36 v with a 12 v tap; a CRA battery with two AUX batteries one 51 for constant voltage equipment. Advant-ageous disposition of terminals simplifies connections to vehicle wiring and to a like battery.

In our copending New Zealand applications: 236660, 244007, 247509, 264225, 270344 we have described this kind of battery and switches which control the charging and discharging of such batteries as the vehicle operates. The contents of these specifications are hereby incorporated by way of reference.
The conventional automotive SLI battery consists of six 2.1 volt Lead acid cells connected in series. The SLI battery has a number of functions that it must perform. Firstly it must be able to provide high amounts of current to the starter motor to start the vehicle. secondly, it must be able to supply a stable voltage to the ignition and fuel systems of the vehicle during starting. Thirdly it must be able to supply reserve current to the ignition and lights of the vehicle when the alternator is not providing current. Fourthly it must be able to supply current to power electrical accessories which draw current over long periods of time when the vehicle is not running.
Ideally the battery should have a life in excess of two years, and it must be able to provide enough energy to start the vehicle even in all weather extremes. Also the battery must be able to withstand being partially discharged without suffering significant capacity loss. Low in terminal resistance is a requirement for high energy output in a battery. Batteries with a very low internal resistance, due to the construction required to achieve this low internal resistance do not have particularly good deep cycle performance. Batteries with good deep cycling characteristics, usually do not have the high current capability required for starting vehicles at low temperatures. The battery must also be low in weight, small in size, and of as low a cost as possible to meet motor vehicle manufactures requirements. By incorporating two separate batteries, a deep cycle battery and a starter battery in a single case it may be possible to meet these requirements. We refer to the starter battery as the cranking battery (CRA) and to the deep cycle battery as the auxiliary (AUX) battery.
Normally when starting the engine of a vehicle at low temperatures the starter draws large amounts of current and the voltage at the battery terminal falls considerably. There may be sufficient energy to turn the starter motor however there may be insufficient voltage to properly power the ignition and fuel systems. A dual battery has two separate and independent voltage outputs, thus the starter motor can be supplied from the starter terminal of the battery and the ignition system can be powered from the other positive terminal of the battery. Thus the ignition system will receive a smooth voltage of approximately 12 volts even though the terminal voltage of the starter battery may fall below 5 volts during starting. This means that the starting performance using a dual battery can be superior to that of a single SLI battery.
Using a dual battery, it may be possible to allow one battery to be discharged while conserving energy in the other battery to start the vehicle.
There have been many attempts at putting two 12 volt series of cells into a single container, however none so far have been particularly successful, as the method for constructing the battery has been incompatible with standard battery manufacturing equipment or final manufactured form of the battery has been significantly different from that of a conventional SLI battery in terms of sizing or terminal layout and thus has had difficulty in fitting into an automobile.
In U.S. Pat. No. 3,475,221, Jordan describes a four terminal automotive battery with two parallel stacks of plates in each of the six cells in the battery. The disadvantage with such a simplistic arrangement is that should one stack of plates become discharged or fail then the other stack of plates which shares common electrolyte will also become discharged. As terms of art an element comprises positive and negative groups nested together with separators in place. A group is an assembly of plates of like polarity burned to a common strap.
In U.S. Pat. No. 3,758,345, Toth describes an automotive battery with a set of U-Shaped plates which constitute the main series of cells and a set of small rectangular plates which are accommodated in the space defined by the U in the large plate, which constitute the auxiliary series of cells. Because the cells share a common watering device, the electrolyte in the auxiliary cells is not separated from the electrolyte in the main cells.
U.S. Pat. No. 4,883,728 (Witehira) describes a 3-terminal automotive battery containing two 12 volt series of cells, with a common negative terminal in a single container. The design of battery that Witehira proposes has many inherent disadvantages. The provision of a common negative terminal makes it impossible to connect the batteries in series. Thus two 12 v batteries cannot be joined to make a 24 v source for trucks and special purpose vehicles. The design and layout of the proposed battery means that the positioning of the terminals is restricted. The construction of the proposed battery requires a total of 11 inter-cell welds as opposed to the 5 in a conventional 12 volt battery. The inter-cell welds are not all on the same axis so a single axis inter cell welder would not be suitable for manufacturing the battery. The plates and cell elements are placed in the battery in a North-South arrangement as opposed to the standard arrangement of laying the plates in an East-West fashion. Not only does this mean that most of the inter-cell welds are at right angles to those in a conventional battery but the plates are also laid in the battery at right angles to those in a conventional battery. The two positive terminals due to the close positioning of the two terminal cells, must be placed extremely close to each other. This has a number of disadvantages, notably that the terminal clamp on one terminal may short circuit the other terminal. Also if one terminal is at a higher potential to the other terminal and a thin film of liquid exists on the lid of the battery, electrochemical reactions may easily occur. Also due to the positioning of the terminal cells, the terminals are located in the middle of the battery, not the side as is usual. Thus it may be difficult for cable clamps to reach the battery terminal.
Examined Japanese Patent application 1-29022 in the name of Nippon Denso K.K. describes a 3-terminal automotive battery containing two 12 volt series of cells, with a common negative terminal in a single container. In this design they propose one series of cells with a larger capacity for starting the vehicle and another series of cells with a smaller capacity for providing a stable voltage to electrical equipment. The negative terminals of the two series of cells are internally connected to so that only one communal negative terminal extends from the case. Because the two series of cells are arranged side by side, conventional width plates cannot be used in the construction of this battery. Also because the plate widths are narrower than in conventional batteries, there are restrictions for casting the strap using a conventional group burning or cast on strap machine. The Battery contains 11 inter-cell wields, 10 of them are on the North-South axis and one of the on the East-West. Thus a multi access inter cell welding machines would be required on a production line. The battery has a common negative terminal so two of these batteries cannot be connected in series for 24 volt operation. The proposed battery does not provide for different construction methods in the two series of cells. Thus the cells are not optimized to provide deep cycling and starting functions and only a single plate type is used.
U.S. Pat No. 5,162,164 (Dougherty etal) and U.S. Pat. No. 5,002,840 (Klebenow etal) describe a 12 volt automotive battery with an external positive and negative terminal. The battery contains two series of six cells connected in parallel via a switch. The first series of cells is transposed along a first axis and the second series of cells is placed along a second axis transverse to the first axis. Bus bars are described for connecting the like terminals of the two series of cells. The bus bars are suspended between the battery lid and the battery case. The bus bars are covered by a chlorinated polyolefin plastic sleeve, which protects the bus bar from corrosion from the electrolyte, and allows them freedom of movement. The battery has only a single pair of terminals, thus it cannot provide two independent current sources simultaneously.
McDowall in U.S. Pat. No. 4,239, 839 describes a modular multicell battery wherein a barrier is inserted into mutually parallel array of identical plates (frames or separators). The barrier divides the cuboid container into two separate batteries each of which with its own volume of electrolyte. The position of the barrier partitions the plates into 33 the desired ratio in order to secure the selected outputs. the capacity is increased by adding more frames and separators.
EP 92106302 (Robert Bosch GmbH) uses two separate batteries mounted one on top of the other. One battery is a high current type for starting and the other is a deep cycle type for powering electrical accessories. Because the batteries are mounted one on top of the other, the access to the lower battery is hindered and this introduces servicing and testing difficulties.

Multiple battery comprising a cranking battery and an auxiliary battery


A row control circuit includes a selector for outputting, as a signal ZRXTRSTD, either signal INTSIG or ZRXTRST in accordance with a test signal TEST, and a holding circuit for receiving a signal ZRXTS by an input A, receiving the signal ZRXTRSTD by an input B, and outputting a word line activating signal RXT from an output node OUT. In a test mode, the phase relation of a sense amplifier activating signal S0N and the word line active signal RXT is set to be different from that in a normal mode. Consequently, a margin of a timing of reading operation or restoring operation can be evaluated.

1. Field of the Invention
The present invention relates to a semiconductor memory device and, more particularly, to a semiconductor memory device characterized in that a part of basic timings of operations of an internal memory cell array is asynchronous with the outside.
2. Description of the Background Art
In recent years, a memory of a large capacity is in demand conspicuously as a portable electronic device such as a portable telephone has more and more functionality.
As a memory of such a device, generally, a static random access memory (SRAM) is mainly used. In the case of realizing a memory of a large capacity by this SRAM, the cost of the memory forms a large proportion of the whole system. In order to avoid an increase in price of the device, therefore, an idea of using a dynamic random access memory (DRAM) of a low cost per unit bit of the memory in place of an SRAM has been generated.
For manufacturers of portable electronic devices each using an SRAM as a main memory of a system, it is difficult to newly assemble a control circuit of a refreshing operation into the system. Consequently, manufacturers have been being developing a new memory using a memory cell that is used in a dynamic random access memory but capable of transmitting/receiving data to/from the outside by a control similar to that of an SRAM.
To be specific, the memory is characterized in that a dynamic memory cell as employed in a DRAM is used as an internal memory cell, an external interface substantially the same as that in an SRAM is used, refreshing operation is controlled internally by the chip itself, and refreshing control does not have to be particularly performed from the outside.
In the specification, in the connection with the function, such a memory will be called a DRAM with a complete hidden refresh function.
FIG. 8 is a block diagram showing the configuration of a conventional DRAM 501 with the complete hidden refresh function.
Referring to FIG. 8, DRAM 501 with the complete hidden refresh function includes: an input terminal group 2 for receiving controls signals /CE, /OE, /WE, /LB, and /UB; a terminal group 4 to/from which data signals DQ0 to DQ7 are input/output; a terminal group 6 to/from which data signals DQ8 to DQ15 are input/output; a terminal group 8 to which address signals A0 to An are input; a power supply terminal 10 to which a source potential VCC is supplied; and a ground terminal 12 to which a ground voltage GND is applied.
Control signal /CE is a chip enable signal for selecting DRAM 501 when DRAM 501 is accessed from the outside. Control signal /OE is an output enable signal for setting DRAM 501 into a read mode and making an output buffer active. Control signal /WE is a write enable signal for setting DRAM 501 into a write mode. Control signal /LB is a signal for making selection of inputting/outputting data from/to data terminal group 4 on a lower-bit side. Control signal /UB is a signal for making selection of inputting/outputting data from/to data terminal group 6 on an upper-bit side.
DRAM 501 further includes: a mode control circuit 14 for receiving the signals from input terminal group 2 and address signals A0 to An and detecting a refresh stop mode; a refresh trigger generating circuit 16 for generating a refresh trigger signal REFCYC in accordance with an output of mode control circuit 14; and a control clock generating circuit 522 for outputting a control clock corresponding to a predetermined operation mode to each block in accordance with the signals supplied from input terminal group 2 and refresh trigger signal REFCYC.
DRAM 501 further includes: a column address buffer 24 for receiving address signals A0 to Am (where m denotes a natural number smaller than n) and transmitting them to the inside in accordance with an output of control clock generating circuit 522; and a row address buffer 25 for receiving address signals Am+1 to An and transmitting them to the inside in accordance with an output of control clock generating circuit 522.
DRAM 501 further includes: a row decoder 26 for receiving internal address signals IAm+1 to IAn output from row address buffer 25 in accordance with an output of control clock generating circuit 522 and selecting a word line WL; a column decoder 28 for receiving internal address signals IA0 to IAm output from column address buffer 24 in accordance with an output of control clock generating circuit 522 and selecting a bit line BL; a memory cell array 32 including memory cells MC arranged in a matrix; and a sense amplifier band 30 for amplifying and reading an output of memory cell array 32. Sense amplifier band 30 includes, but not shown, a plurality of sense amplifiers and a plurality of input/output circuits.
In FIG. 8, one word line WL, one bit line BL, and one memory cell MC out of the plural memory cells MC included in memory cell array 32 are shown representatively.
DRAM 501 further includes: a lower-bit side input buffer IBL for receiving data signals DQ0 to DQ7 from terminal group 4 in accordance with a lower-bit control signal LC output from control clock generating circuit 522 and transmitting them to sense amplifier band 30; a lower-bit side output buffer OBL for receiving a signal from sense amplifier band 30 in accordance with control signal LC and outputting a data signal to terminal group 4; an upper-bit side input buffer IBU for receiving data signals DQ8 to DQ15 from terminal group 6 in accordance with an upper-bit control signal UC output from control clock generating circuit 522 and transmitting the received signals to sense amplifier band 30; and an upper-bit side output buffer OBU for outputting data read from sense amplifier band 30 to terminal group 6 in accordance with control signal UC.
Generally, in a static random access memory (SRAM), signals supplied from the outside can be easily controlled. Higher packing density of memory cells MC can be achieved by using dynamic memory cells at lower cost as compared with static memory cells. However, since dynamic memory cells hold information by charges accumulated in memory cells, refreshing operation has to be performed every predetermined period, and the control is complicated.
In DRAM 501 shown in FIG. 8, signals supplied from the outside are address signals and control signals similar to those of an SRAM. Consequently, a semiconductor memory of a large capacity, which can be easily controlled is realized by using simple controls supplied from the outside like those in an SRAM and internally using memory cells similar to those in a DRAM.
When a memory cell in the DRAM is not accessed for a predetermined period, however, refreshing is necessary. In a period of time during which an access is not made, refresh trigger generating circuit 16 instructs control clock generating circuit 522 to perform refreshing operation by signal REFCYC.
FIG. 9 is a circuit diagram showing the configuration of sense amplifier band 30 and memory cell MC in FIG. 8.
Referring to FIG. 9, sense amplifier band 30 includes an equalize circuit BEQ, a sense amplifier SAK, and a column selection gate CSG per bit lines BL and ZBL. A memory cell MC is disposed in an intersecting point between a word line WLn provided in corresponding with each memory cell row and bit line BL or ZBL. FIG. 9 shows one memory cell representatively.
Memory cell MC includes an N-channel MOS transistor MT provided between bit line ZBL and a storage node SN and having a gate connected to word line WLn, and a capacitor MQ having one end connected to storage node SN and the other end coupled to a cell plate potential.
Between bit lines BL and ZBL equalize circuit BEQ for equalizing the potential of bit line BL and that of bit line ZBL in accordance with an equalize signal BLEQ is provided.
Equalize circuit BEQ includes three transistors; N-channel MOS transistor which is made conductive according to an equalize signal BLEQ to thereby connect bit lines BL and ZBL, N-channel MOS transistor which is made conductive according to equalize signal BLEQ to couple bit line BL to an equalize potential VBL, and N-channel MOS transistor which is made conductive according to equalize signal BLEQ to couple bit line BL to equalize potential VBL.
Between bit lines BL and ZBL, sense amplifier SAK activated by transistors N3 and P3 which are made conductive according to sense amplifier activating signals S0N and /S0N, respectively, is provided.
Sense amplifier SAK includes a P-channel MOS transistor P1 and an N-channel MOS transistor N1 connected in series between nodes S2P and S2N and each having a gate connected to bit line ZBL, and a P-channel MOS transistor P2 and an N-channel MOS transistor N2 connected in series between nodes S2P and S2N and each having a gate connected to bit line BL.
A connection node of P-channel MOS transistor P1 and N-channel MOS transistor N1 is connected to bit line BL. A connection node of P-channel MOS transistor P2 and N-channel MOS transistor N2 is connected to bit line ZBL. When activated, sense amplifier SAK amplifies the potential difference between bit lines BL and ZBL.
Column selection gate CSG which is made conductive according to a column selection signal CSL generated by a column address is provided for each bit line pair. By column selection gate CSG, bit lines BL and ZBL are connected to global IO lines GIO and ZGIO via local IO lines LIO in a reading or writing mode.
A cycle time of the memory will now be described.
Similar to a DRAM with the complete hidden refresh function, there is a memory what is called a pseudo SRAM having the same control pins as those of an SRAM but not using a time division method different from a DRAM. In the DRAM with the complete hidden refresh function, since the chip itself automatically performs refreshing operation, there is a case that refreshing occurs between (reading/writing) operations. In such a case, the cycle time characteristic deteriorates as compared with a pseudo SRAM having refresh pins.
FIG. 10 is a diagram showing an example of waveforms in the case where refreshing occurs between operations.
Referring to FIG. 10, in cycle #1, operation is switched from NOP (no operation) to READ in response to the rising edge of control signal /OE. FIG. 10 shows a case where a refresh trigger pulse automatically, internally generated competes with operation READ. Operation READ is finished synchronously with the rising edge of control signal /OE and is switched to NOP. Then refreshing is performed internally after completion of operation READ.
In cycle #2, due to designation of writing, control signal /WE changes from the H level to the L level. The signal may be input when the period of refreshing automatically performed internal is finished and the operation is switched again to NOP. The cycle time is therefore limited by a total of the refresh period and the period of reading or writing operation.
In order to prevent deterioration in cycle time characteristics when the refresh competes with operation READ or WRITE, it is very effective to automatically switch the completion of a series of array operations of inactivating a word line, inactivating a sense amplifier, and equalizing the bit lines by a predetermined internally-determined delay time of the DRAM with the complete hidden refresh function without waiting for the rising edge of control signal /OE.
FIG. 11 is an operation waveform chart for explaining the operations in the case where the array operations are completed internally, automatically.
Referring to FIG. 11, in cycle #1, control signal /OE goes low and the operation is switched from NOP to READ. At this time, the refresh trigger pulse competes with the operation READ. Operation READ is switched to operation NOP after delay time TD in which the internal array operations are finished. The switch is made without waiting for the rising edge of control signal /OE. The refreshing operation is finished after delay time TD1, and the operation is switched again to NOP. Then a write instruction can be accepted from the outside. The improved cycle time characteristic as compared with the case shown in FIG. 10 is therefore achieved.
As shown in cycle #2, a writing operation WRITE starts in response to the rising edge of control signal /WE. The operation is switched to NOP after elapse of delay time TD3. The switch is also internally, automatically made without waiting for the rising edge of control signal /WE.
As described above, in the case where the array operations are automatically completed in a delay time internally determined, the array operations are performed only in the minimum time, so that the improved cycle time characteristic as compared with the case of instructing completion of the array operations from the outside is achieved. Since the array operations are internally, automatically completed, however, a problem such that it becomes very difficult to evaluate a restoring characteristic (interval in which data can be rewritten into an array in a reading mode) occurs.
FIG. 12 is an operational waveform chart for explaining the access time of the memory.
Referring to FIG. 12, the access time of the memory is determined by times T11 to T15.
Time T11 is a period of time from completion of equalize operation according to the falling edge of equalize signal BLEQ to the instance when word line WL is made active.
Time T12 is a period of time from an instance when word line WL is made active to an instance when the sense amplifier is activated synchronously with the rising edge of control signal ZS0S.
Time T13 is a period of time from an instance when the sense amplifier is activated until the word line WL is made inactive.
Time T14 is a period of time from an instance when the word line is made inactive to an instance when the sense amplifier is made inactive.
Time T15 is a period of time from an instance when the sense amplifier is made inactive to an instance when the bit line pair is equalized again.
For the sake of stable operation, the longer each of the times T11 to T15 is, the better. However, for higher processing speed of the memory, it is necessary to shorten each time as much as possible. Consequently, it is important to grasp the margin of each time of the developed memory.
In the DRAM with the complete hidden refresh function, however, as described with reference to FIG. 11, operation READ is switched in delay time TD2 internally determined. Consequently, the operation limit cannot be evaluated in accordance with the control signal supplied from the outside. Therefore, it is difficult to evaluate the characteristics of the developed memory.
An object of the invention is to provide a semiconductor memory device capable of controlling the timing of an array operation in response to a trigger signal in a test mode and easily evaluating a restoring characteristic.
The invention is directed to, in short, a semiconductor memory device having a test mode and a normal mode as operation modes, and including a memory array, a plurality of word lines, a row decoding circuit, a plurality of bit line pairs, a sense amplifier circuit, and a timing control circuit.
The memory array includes a plurality of memory cells arranged in a matrix of rows and columns. The plurality of word lines are used to select a row of memory cells. The row decoding circuit activates a word line corresponding to an address signal out of the plurality of word lines in response to a word line activating signal. The plurality of bit line pairs is provided in correspondence with columns of the memory cells. The sense amplifier circuit for amplifies data held in the plurality of memory cells read on the plurality of bit line pairs in accordance with a sense amplifier activating signal.
The timing control circuit outputs the word line activating signal and the sense amplifier activating signal in accordance with an external control signal in the normal mode. The timing control circuit makes a phase relation between the word line activating signal and the sense amplifier activating signal different from that in the normal mode and outputs the resultant phase relation in response to a timing test signal supplied from the outside in the test mode.
A main advantage of the invention is, therefore, that a margin of a timing of making the word line active or inactive and a margin of a timing of making the sense amplifier active or inactive whose operation margins cannot be recognized in the normal operation can be evaluated.
The foregoing and other objects, features, aspects, and advantages of the present invention will become more apparent from the following detailed description of the present invention when taken in conjunction with the accompanying drawings.

Semiconductor memory device allowing easy characteristics evaluation


The invention relates to Corynebacterium ammoniagenes CJXOL 0201 KCCM 10447 producing 5′-xanthylic acid. More specifically, the invention relates to Corynebacterium ammoniagenes CJXOL 0201 KCCM 10447 which is a mutant strain of Corynebacterium ammoniagenes KCCM 10340 having a resistance to oligomycin. In order to obtain mutant strain having enhanced respiratory activity, the present invention adopted Corynebacterium ammoniagenes KCCM 10340 as parent strain and treated it with UV radiation and mutation derivatives such as N-methyl-N′-nitro-n-nitrosoguanidine(NTG) according to ordinary procedure. Therefore, Corynebacterium ammoniagenes CJXOL 0201 KCCM 10447 of the present invention makes it possible to increase ATP reproducing activity for same period of fermentation and can accumulate 5′xanthylic acid in culture medium at a high yield and concentration rate.

5′-xanthylic acid is an intermediate in the nucleic acid biosynthesis process, which is physiologically important in the body of animals and plants, used in food, medical supplies and other various field. The invention relates to a mutant strain having a resistance to oligomycin, obtained from a known strain Corynebacterium ammoniagenes KCCM 10340, producing 5′-xanthylic acid at a high yield and high concentration rate by a direct fermentation method.
5′-xanthylic acid is an intermediary product of purine nucleotide biosynthesis process and important material for producing 5′-guanylic acid. A widely used method to produce 5′-guanylic acid having fineness and high quality is microorganism fermentation method which produces 5′-xanthylic acid first and converts it into 5′-guanylic acid enzymatically, therefore, to produce 5′-guanylic acid, corresponding amount of 5′-xanthylic acid is necessary. Conventional methods to produce 5′-xanthylic acid are chemosynthesis, deaminization of 5′-guanylic acid which is produced as a result of decomposition of ribonucleic acid in yeast, a fermentation method to add xanthine as precursor material in fermenting medium, a fermentation method to use a mutant strain of microorganism, a method to add antibiotic material (JP 1477/42 and JP 20390/44), a method to add surfactant (JP 3825/42 and JP 3838/42) and so on. Among these, a direct fermentation method of 5′-xanthylic acid by a mutant strain of microorganism is quite advantageous in terms of industrial aspect. Thus, we inventors developed a mutant strain with increased productivity of 5′-xanthylic acid, by modifying the existing character of Corynebacterium ammoniagenes KCCM 10340 into the character of producing 5′-xanthylic acid at a large yield rate.
Most microorganisms reach to the condition that the volume doesn't increase any more when keep on culturing under the constant condition, and especially the concentration of microorganism producing primary metabolite, a growth-dependent product, doesn't increase any more. It is mainly caused by limited supply of dissolved oxygen. Method of enhancing aeration and agitation condition, for removal of the limited supply of dissolved oxygen, is used, but there is technical and economical limit in actual production method. To overcome the limit and increase yield rate and concentration of 5′-xanthylic acid by enhancing the volume of microorganism and various physiological activity, under the limited supply of dissolved oxygen, we inventors thought that the method of enhancing respiratory activity and ATP reproducing activity of microorganism under the same dissolved oxygen would be useful. Thus, the inventors investigated microorganism strains having a resistance to various respiratory inhibitors, and found out that a mutant strain having a resistance to oligomycin is most effective among these and can produce 5′-xanthylic acid at a high yield and high concentration rate by a direct fermentation method, and accomplished in this invention.

Microorganism producing 5'xanthylic acid


A clock recovery circuit capable of fast and accurate clock phase locking even in the presence of frequency shift and noise. The input signal includes, in order, a preamble with an alternating bit sequence pattern, a unique word and data. A detection unit detects zero crossings and measures the time interval therebetween. A 1-interval judgment unit judges whether an interval signal is within a predetermined range, and a 2-interval judgment unit sums two adjacent interval signals and judges whether the 2-interval signal is within a predetermined range. A control unit controls a zero-crossing signal based on the judgment result and outputs a valid zero-crossing signal if judged in the affirmative. A switching unit switches between outputting the zero-crossing signal and the valid zero-crossing signal as valid phase error information based on a frame reception signal input from a frame detection unit. A clock generation unit uses the valid phase error information in generating a symbol clock.

Technology for transmitting and receiving data divided into frames is widely used in the field of cable and wireless communications. In the frames used, a preamble (PR) and a unique word (UW) are prefixed ahead of data of a predetermined length. FIG. 2 shows a frame structure. The PR is provided at the head of the frame. The receiver performs gain control, frequency synchronization, symbol synchronization and the like during reception of the PR, in order to control the state in which the UW and data portions following the PR are received. Here, symbol synchronization is processing at the receiver to recover the timing (i.e. symbol clock) of the decision point at which the eye pattern of a symbol is most open, the symbol clock being generated by a clock recovery circuit.
In a typical method for clock recovery, the temporal position of zero crossings on both the in-phase (I) and quadrature (Q) axes are detected and used to recover the symbol clock. FIG. 3 schematically shows clock adjustment in a clock recovery circuit. In the clock recovery shown in FIG. 3, a phase error E with phase error information obtained from an input signal is detected based on a recovered symbol clock, and the clock phase is adjusted so as to reduce the phase error. Here, zero-crossing signals are used to adjust the clock phase in recovering the symbol clock, and thus referred to as phase error information. While fast phase locking is achieved when phase error information occurs successively within the symbol cycle because of the phase error being the same, phase locking is slowed when the phase error information occurs out of the symbol cycle due to the effects of jitter. An alternating pattern in which the phase of adjacent symbols inverts 180° is thus used in the PR, and the receiver obtains received data by generating a symbol clock using phase error information obtained successively from the alternating pattern and acquiring the decision point timing of the symbols based on the generated symbol clock.
Frequency shifts, phase noise and the like in the local oscillators of both the transmitter and the receiver cause phase shifts to occur between signals transmitted by the transmitter and signals received by the receiver. Frequency synchronization is thus required at the receiver, this processing being performed by a phase error correction (PEC) circuit for correcting phase shifts in received signals, or an automatic frequency control (AFC) circuit for directly controlling the oscillation frequency of the local oscillator in the receiver.
FIG. 4 shows the structure of a receiver. A PEC circuit 402 corrects phase errors in a detected signal input 411 from a signal detection unit 401, a clock recovery circuit 1 uses a phase-corrected signal 412 to generate a symbol clock 128, and a data decision unit 403 performs a data decision on phase-corrected signal 412 using symbol clock 128 to obtain received data 413. Note that symbol clock 128 is also used in PEC circuit 402 to calculate a phase correction value.
Normally, as shown in FIG. 4, correct received data can be obtained by performing the frequency synchronization (here, phase error correction) upstream of the symbol synchronization (here, symbol clock recovery). However, when frequency shift causes a large phase shift in the received signal, the cyclicity of the zero-crossing signals is disrupted. The phase error information thus becomes indeterminate due to multiple eyes opening in the symbol period when there should only be one eye, making clock recovery difficult. This is because the clock recovery circuit tries to lock the clock phase to the pseudo eyes. Also, errors occur in the phase correction performed at the PEC circuit based on the symbol clock generated by the clock recovery circuit, resulting in errors in the received data. Note that in the following description, phase shift in the detected signal caused by frequency shift is a different parameter to phase errors in the symbol clock being recovered.
In a conventional clock recovery technique using zero-crossing signals as phase error information, as shown in Japanese Patent Application Publication No. 2001-35095, only valid phase error signals are selected.
FIG. 37 is a block diagram showing the structure of an error selection circuit included in a clock recovery circuit recited in the above art. In the error selection circuit shown in FIG. 37, a T counter circuit 3700 measures the time interval between zero point information showing zero crossings, and an error-selection control signal generator 3701 judges whether the T count is within a predetermined range and outputs an error selection control signal based on the judgment result. An AND circuit 3704 evaluates both the current error selection control signal and the preceding error selection control signal stored at a D flip-flop circuit 3703, and outputs an error selection control signal 3710 based on the evaluation result to switching circuit 3706.
When the time intervals between the current zero crossings and the preceding zero crossings are both bit clock time periods that fall within a range defined by minimum and maximum values, the conventional error selection circuit outputs the phase error signal from a phase detector, having judged the phase error signal to show a substantially accurate phase error. On the other hand, if either one of these time intervals falls outside the set range, the conventional error selection circuit invalidates the phase error signal from the phase detector, having judged the phase error signal to be of doubtful accuracy.
The prior art is thus able to avoid causing phase fluctuation, bit slip and the like and thereby stabilize phase tracking performance, by validating only phase error signals relating to inversion intervals within the set range, and invalidating both phase error signals occurring immediately after short inversion intervals having a low signal level and phase error signals occurring immediately before and after long inversion intervals during which phase errors accumulate, due to the low reliability of phase errors in both cases.
In the field of cable and wireless communications targeted by the present invention, the following problems arise when a conventional error selection circuit applied in relation to binary digital signals in a digital signal player that plays information recorded on recording media such as DVD (digital versatile disc) performs symbol synchronization at the head of the frame with frequency shift in the received signal, during burst transmission using modulated signals in frame format.
Consider an example in which signals are modulated using π/4 DQPSK (Differential Quadrature Phase Shift Keying) Normally, an alternating pattern "10 01" is used in the PR sequence, and the clock recovery circuit uses a cyclic signal inherent in this sequential pattern as phase error information to recover the symbol clock. Note that FIG. 5 shows the phase transition amount for two bits (Xn, Xn+1) per symbol.
FIG. 6 shows the transition of a detected π/4 DQPSK signal when the alternating pattern. A signal point A in the −π/4 phase transits alternately with a signal point B in the 3π/4 phase. Here, the transition AB from point A to point B and the transition BA from point B to point A always transit in the same direction relative to the alternating axis. This transition is referred to here as an arc-shaped transition. The reason for this arc-shaped transition is as follows.
FIG. 7 shows the transition of a predetection π/4 DQPSK signal when the alternating pattern. The intermediate points (Man, Mbn, where n=1, 2, 3, 4) of the signal transition shown in FIG. 8 are expressed asMa1: ma·exp(π/8), Mb1: mb·exp(3π/8)Ma2: ma·exp(5π/8), Mb2: mb·exp(7π/8)Ma3: ma·exp(9π/8), Mb3: mb·exp(11π/8)Ma4: ma·exp(13π/8), Mb4: mb·exp(15π/8).Therefore, the differential detection output at adjacent intermediate points (Ma1 & Mb1, Mb1 & Ma2, Ma2 & Mb2, Mb2 & Ma3, Ma3 & Mb3, Mb3 & Ma4, Ma4 & Mb4, Mb4 & Ma1) for all combinations can be expressed asmamb·exp(π/4).  (1)Expression 1 indicates that the transition of the differentially detected signal always has a component in a π/4 phase direction between two signal points. That is, the signal transits in the same direction relative to the alternating axis. Thus with π/4 DQPSK modulation, the transition of the differentially detected signal is arc-shaped when the PR sequence has the alternating pattern "10 01".
Described next is the case in which two or more zero crossings occur along one of the axes during signal transition due to frequency shift being included in a signal having arc-shaped transition characteristics.
FIG. 9 is a timing chart showing zero-crossing signals when phase shift is absent. As is also apparent from the FIG. 6 signal transitions, the fact that zero crossings occur within the symbol cycle long both the I/Q axes in the case of phase shift being absent means that zero-crossing signals along the I/Q axes occur at one symbol intervals with respect to the symbol clock being recovered, and thus the successive phase errors EI and EQ are respectively the same. Accordingly, these zero-crossing signals are valid phase error information.
FIG. 10 schematically shows signal transition with additive +45° phase shift and noise in the detected signal shown in FIG. 6. As shown in FIG. 10, the signal points disperse with additive noise, widening the locus of the signal transition.
FIG. 11 is a schematic diagram showing the detected signal in FIG. 10 crossing the I/Q axes. The majority of transitions AB can be classified into the following four types.Transition AB12: 1st→2nd quadrantTransition AB123: 1st→2nd→3rd quadrantTransition AB412: 4th→1st→2nd quadrantTransition AB4123: 4th→1st→2nd→3rd quadrant
FIG. 12 is a schematic diagram showing zero-crossing signals and phase errors for transition AB4123. With transition AB4123, zero-crossing signals occur along both the I/Q axes as shown in FIG. 12. Note that with phase error EI in the in-phase (I) component, at least two zero-crossing signals occur per symbol period owning to the arc-shaped signal transition.
Consider an example in which the conventional error selection circuit discussed above judges the validity of phase error information when the input signal corresponds to the PR and the detected signal alternates in sign. In the case of two zero-crossing signals occurring at regular intervals (=0.5 T, where T=1 symbol period) per symbol period, pseudo eyes occur on either side of the eye pattern originally to be captured. While the true eye needs to be specified and sampled from this signal as phase error information, clock recovery with the conventional error selection circuit is unstable because of the two zero-crossing signals per symbol period being judged valid when Tcmin is set below 0.5 T. On the other hand, phase error information is not detected when Tcmin is set above 0.5 T because of both zero-crossing signals being judged invalid, making clock recovery impossible. Thus when the conventional error selection circuit is applied in relation to an alternating pattern PR with phase shift caused by frequency shift present in the detected signal, normal clock locking operations cannot be realized.

Clock recovery circuit and receiver using the circuit


Methods and systems provide for incubating a plurality of eggs at least partially at a primary incubation location and then incubating the plurality of eggs (e.g., a plurality of single sex eggs sorted from the plurality of eggs) at least partially during transport to a secondary location.

Generally, controlled climate chambers are used for the incubation of eggs. For example, the eggs are placed in the controlled climate chamber and climatic conditions are matched as well as possible to the optimum growth conditions for the embryos in the eggs. For example, the eggs may be subjected to a temperature progression. Such a temperature progression may start at a particular temperature (e.g., 100° Fahrenheit), which is then lowered because the eggs themselves start to produce heat. Such incubation of the eggs through hatch is generally performed according to an incubation profile that takes into consideration necessary temperature changes, as well as other climatic conditions (e.g., carbon dioxide (CO2) content, humidity, etc.). The incubation process is typically carried out in a particular controlled climate chamber at a single hatchery facility (e.g., the incubation process is tied to a single facility).
As indicated above, generally, in the hatchery, eggs are hatched in a climate controlled chamber. The environment in this chamber is controlled to optimize the hatching process. In this context, temperature, CO2 content, and humidity are some of the control variables controlled during the incubation process. The climate controlled chambers generally include large egg holding structures in which various trays holding eggs are placed. Such eggs during the incubation process may be held in a fixed position (e.g., using pallets of egg trays) or, eggs may be, for example, rotated during a part of the incubation process (e.g., incubator racks configured to hold the eggs such that the eggs can be moved to present the eggs in different positions relative to an air stream provided in the incubator). For example, in an exemplary and conventional incubation process for turkeys or ducks, incubation is completed in incubator racks and pallets for the first 25 days or so of an approximate 28 day incubation cycle. Thereafter, the eggs are transferred to hatch baskets for hatching. The eggs generally hatch approximately around the same time. For about the first day or so following hatch, the newly hatched poults can remain in a hatching chamber, living off the yolk, with little or no additional nutrients being introduced into the climate controlled chamber.
After the poults are hatched in a hatchery, they are generally transported as quickly as possible to a subsequent farm (e.g., for fattening, rearing, breeding, etc.). Such poults may be transported, for example, in an apparatus such as described in International Publication No. WO2005/070198 A1 entitled "Method for holding poikilothermic poultry, and device for holding poikilothermic poultry," assigned to HatchTech Group B.V., published 4 Aug. 2005, which describes a transportable climate controlled container (e.g., in which the temperature controlled).
In other words, a generally standard or conventional production cycle for poultry is for the poults to be hatched at a hatchery and then transported from the hatchery to a further farm, such as a fattening farm, where the poultry grows and is fattened. Farms of this type are generally many different fauns located at a distance from one another. For example, in many cases, such farms may be located a great distance from each other and/or from the hatchery.
Sex separate rearing is also an important component in the raising of poultry (e.g., turkey production). In other words, poults of a single sex are reared separate from those of the other sex. Typically, depending on production, processing/marketing requirements, and cost relationships, separate sex rearing can be of great economic benefit to poultry producers (e.g., one gender is raised much differently than another to optimize the production process). Yet further, in many circumstances, farms that raise one sex of poultry are generally located a substantial distance from farms that raise the other sex and/or may also be located a substantial distance from a hatchery.

Egg incubation transport system and methods regarding same


The invention provides a lubricating composition containing an oil of lubricating viscosity and a detergent. The invention further relates to a process to prepare the detergent, and the use of the lubricating composition in a mechanical device such as an internal combustion engine, or a driveline device.

It is well known for lubricating oils to contain a number of surface active additives (including antiwear agents, dispersants, or detergents) used to protect internal combustion engines from corrosion, wear, soot deposits and acid build up. Often, such surface active additives can have harmful effects on mechanical devices (such as internal combustion engines or driveline devices). Harmful effects may include possible wear (in both iron and aluminium based components), bearing corrosion, increased acid accumulation (due to lack of neutralisation of combustion by-products), or reduction in fuel economy.
A common antiwear additive for engine lubricating oils is zinc dialkyldithiophosphate (ZDDP). It is believed that ZDDP antiwear additives protect the engine by forming a protective film on metal surfaces. ZDDP may also have a detrimental impact on fuel economy and efficiency and copper corrosion. Consequently, engine lubricants may also contain a friction modifier to obviate the detrimental impact of ZDDP on fuel economy and corrosion inhibitors to obviate the detrimental impact of ZDDP on copper corrosion. Other additives may also increase lead corrosion.
Other art known to a skilled person includes a number of publications disclosing esters or amides or imides of carboxylic acids, or esters or amides or imides of hydroxycarboxylic acid as possible antiwear agents. The publications include Canadian Patent CA 1 183 125; East German Patent DD 299533 A5; International Publications WO 2006/044411, WO 2005/087904, WO2008/070307; Japanese Patent Applications 2005139238 A, 10183161A, 10130679A, and 05117680A; US Patent Applications 2010/0190669, 2010/0197536, and 2010/0093573, 20050198894; and U.S. Pat. Nos. 4,237,022, 5,338,470, 4,436,640, 4,157,970, 4,863,622, 5,132,034, 5,215,549, and 6,127,327.
Detergents such as metal sulphonates, metal phenates, metal salicylates, and metal salixarates are known. The detergents may be prepared in the presence or absence of a carboxylic acid. For example carboxylic acid-modified detergents are disclosed in EP 271 262 A, EP 273 588 A, U.S. Pat. Nos. 5,792,735 and 5,674,821. Typical acids disclosed therein may be defined by the formula RCH(R1)CO2H, wherein R is a C10 to C24 alkyl group and R1 is hydrogen or a C1 to C4 alkyl group. An exemplified acid-modified detergent includes a hydrocarbyl-substituted phenate that contains 12 to 20 by weight of stearic acid. U.S. Pat. No. 3,155,617 discloses a means of activating calcium oxide (prepared from roasting calcium carbonate), so that it is useful in the methanol process for preparing dispersions of calcium carbonate. The calcium oxide is treated in methanol suspension with a small amount of an acid such as acetic acid.

Lubricating composition containing a detergent


A droplet applying apparatus includes a base having a mounting surface on which a substrate is to be mounted, an arm part which is fitted to the base so as to be movable relative to the base in an arrow A direction, and a plurality of droplet ejecting sections which are fitted to the arm part so as to be movable in an arrow B direction and which eject droplets to the substrate mounted on the mounting surface. The droplet ejecting sections are fitted on a fitting surface of a first beam member of the arm part as well as on a fitting surface of a second beam member of the arm part.

In recent years, the ink jet technology has been expected for use as manufacturing apparatuses, not merely as printer devices for forming images on paper mediums. For example, in JP 2003-191462 A, an apparatus construction in which droplet ejecting elements using the ink jet system are mounted is disclosed as a manufacturing apparatus for liquid crystal displays, organic EL displays, plasma displays, electron emission elements, electrophoretic display devices and the like. For improvement of landing position precision onto the substrate, in JP 2003-191462 A, a stage for carrying the substrate in one fixed direction with an apparatus base body provided by a granite surface plate, and a carriage mechanism for moving an ink jet head along a direction perpendicular to the stage traveling direction, are provided on the granite surface plate in direct connection.
A general-use printer by the ink jet system, typically, forms images by using one ink jet head unit on which several pieces of ink jet head elements each having a width of ½ to 2 inches and having nozzle openings regularly arrayed at intervals of 150 to 300 nozzles/inch are mounted as elements for ejecting droplets in some plural quantity for each of the individual colors. As the method therefore, it has been practiced that recording sheet, while fed by a sheet feed roller, is scanned a plurality of times in a direction perpendicular to the carrying direction of the recording sheet so that an image is formed on the recording sheet.
Even with the use of the ink jet system as a manufacturing apparatus, the ink jet head elements are similar to those of general-purpose printers, the size of each ink jet head element in the nozzle array direction being 1 to 2 inches at most as it stands.
Meanwhile, manufacturing processes for liquid crystal displays, organic EL displays, plasma displays, electron emission elements and electrophoretic display devices are increasingly directed toward increasing the yield quantity by using larger-area substrates to reduce the cost and the cycle time. Manufacturing of these devices and others by the ink jet system would require an apparatus that is capable of managing large-area substrates having one side as much as several meters.
One of manufacturing apparatuses using the ink jet system capable of high-speed processing with large-area substrates is a line head system in which a plurality of ink jet head elements are arrayed to a length more than the substrate size. This system is so configured that at most 1 to 2-inch wide ink jet elements are staggered to an extent equal to the substrate size, in which case at least 100 to 200 heads need to be arrayed on condition that the substrate is several-meter sized. Apparatuses by this system can be said to be quite effective in cases where ejection to all over the substrate such as color filter substrates is required and moreover the ejection points are regularly located.
However, the line head system would be unsuitable for recovery of color filter substrates as shown in, for example, JP 2003-66218 A. JP 2003-66218 A shows a system which includes, as part of the manufacturing method of color filter substrates, ejecting a color filter material only to failure points on occurrence of coloring failure portions in the color filter substrate. Using the line head system as a means for correcting such failure points scattered on the color filter substrate would involve the same processing time as in the ejection of droplets to all over the substrate, and moreover cause most of the nozzles to be non-operating nozzles that perform almost no ejecting operation, leading to a high likelihood of occurrence of nozzle clogging. Further, maintenance operation would be required for all the nozzles, leading to increases in unnecessary waste fluids. Also, with a desire for uniformized ejection quantity, the line head system would give rise to a need for performing ejection quantity correction on a total of thousands of nozzles, one by one, despite the purpose of merely ejecting droplets to scattered desired points, hence extremely inefficient.
Further, in a system in which the ink jet head unit that has been widely used in general-purpose printers is reciprocated in plurality on one identical plane, the scanning distance of the ink jet head units is increased, and the scanning speed is also limitative in terms of stable operation, so that the processing time could not be shortened.
Furthermore, the desire for efficiently ejecting droplets to desired points without limitation to all over large-area substrates is what will be sought in the future not only for recovery of color filters but in various manufacturing fields.
With the ink jet system used as a manufacturing apparatus, there would be a need that the retaining member for retaining the head across the substrate be elongated to 2 to 4 m according as color filter substrates get bigger in area. However, it is hard to manufacture longer retaining members with high precision, and the impossibility of obtaining a high-precision retaining member would cause a fear that the precision of droplet landing positions for the substrate may be worsened.


A probe for use in spectroscopic analysis comprises an optical fiber with a rod-like end piece. One form of the probe has a local detector which can be deposited on the end piece or located close to it. This improves collection efficiency of radiation diffusely scattered from a sample being investigated. An alternative arrangement uses a local source of radiation.

Apparatus for carrying out spectroscopic analysis generally includes a source of radiation, typically infrared or near infrared (NIR) radiation, in the case of FT-IR spectroscopy. The Apparatus includes suitable optics for directing the radiation from the source to the location of a sample under investigation and for collecting radiation reflected from or transmitted through the sample for subsequent analysis. It is common in such apparatus to provide an output port to which can be coupled a probe, whereby the probe can be used to receive radiation from the source and direct it to a remote location for carrying out spectroscopic analysis. Such probes generally include one or more optical fibers within which the radiation can propagate. Examples of known probes are described in W092/09881 and EP-A-0652429. In these known arrangements the source of analysing radiation and the detector of the analysing radiation are both located in the main spectrometer housing which means that the analysing radiation has to propagate twice along the length of the fiber or fibres. Such arrangements suffer from poor efficiency in respect of the collection of the diffusely reflected radiation. The present invention is concerned with an improved design of probe.


A system and method for using high-end perception sensors such as high-end LIDARs to automatically label sensor data of low-end LIDARs of autonomous driving vehicles is disclosed. A perception system operating with a high-end LIDAR may process sensed data from the high-end LIDAR to detect objects and generate metadata of objects surrounding the vehicle. The confidence level of correctly identifying the objects using the high-end LIDAR may be further enhanced by fusing the data from the high-end LIDAR with data from other sensors such as cameras and radars. The method may use the detected objects and metadata of the detected objects processed from the data captured by the high-end LIDAR and other sensors as ground truth to label data of a same scene captured by a low-end LIDAR mounted on the vehicle. A neural network may use the labeled sensor data from the low-end LIDAR during offline supervised training.

Vehicles operating in an autonomous mode (e.g., driverless) can relieve occupants, especially the driver, from some driving-related responsibilities. When operating in an autonomous mode, the vehicles can navigate to various locations using onboard sensors, allowing the vehicles to travel with minimal human interaction or in some cases without any passengers.
Motion planning and control are critical operations in autonomous driving. The safety, accuracy and efficiency of motion planning and control operations depend on the ability of the ADVs to sense and predict the motions of moving obstacles such as other vehicles or pedestrians as well as to recognize non-moving objects. Sensors such as cameras, light detection and range (LIDAR) units, radars, etc., are used to capture video and electromagnetic images of environments around the vehicles. The ADVs may process information captured by the sensors to perceive driving environment including obstacles, traffic elements and road features surrounding the ADVs for planning and controlling the motions of the ADVs.
To recognize objects surrounding an ADV and to predict the motions or trajectories of nearby vehicles for safe navigation, a perception module of the ADV may use a neural network that operates on the captured sensor data. The sensor data may be captured by high-end LIDARs with 64 or 128 laser rays together with those of cameras, radars, etc. However, due to the high cost of high-end LIDARs and associated computational hardware, it may be desirable to find low-cost LIDARs that have 16, 32, or 40 rays. For the perception module to operate with the low-cost LIDARs, the neural network of the perception module may need to be trained using labeled data captured by the low-cost LIDARs. Labeling of perception data from sensors is a time consuming, costly, and often manual process. It is desirable to be able to automatically, efficiently, and cost-effectively label perception data from low-cost LIDARs for training neural networks of perception modules of ADVs that operate with the low-cost LIDARs.

Automated labeling system for autonomous driving vehicle lidar data


A collapsible pergola comprising a traditionally configured pergola having a plurality of locking hinge mechanisms disposed about each section of the pergola thereby enabling the pergola to be unfolded to set up or folded up to store away in a low-profile manner requiring no assembly or disassembly of the pergola by the user.

Landscaping and outdoor features are common decorations that people use to enhance their outdoor property. Such features that can be used as both a landscaping feature and a seating and resting facility is a pergola. Pergolas provide a way for crawling or hanging vegetation such as ivy, hops, grapes, or hanging baskets to be trained and displayed, and also provide seating and perhaps a horizontal table surface.
Usually pergolas are constructed out of wooden or composite materials and are permanent fixtures in the ground. This permanent installation lends itself to damage due to weathering and other incidental damage and can also only be associated with the vegetation that is established in the ground. There is a benefit to having a pergola that is capable of collapsing into a transportable state and transforming into a fully erected pergola positioned at a desired location, whether it is for a quick getaway or a lengthier use. Such a pergola would also benefit from being collapsed into as compact a state as possible and also be lightweight and easy to erect when needed. The use of the collapsible pergola as described herein fulfills this purpose.


A gas sensor element which has water-permeable electrodes, and water-impermeable leads connected to the electrodes A first electrode (133) has a space exposure portion (133b) exposed to internal space (160) of a gas sensor element (10) which communicates with an ambient atmosphere. A first lead (137) is connected to the first electrode (133). The first electrode (133) includes a first connection portion (133d) which is disposed at a position not exposed to the internal space (160) and connected to the first lead (137), and which is a portion of the first electrode (133) located most distant from the internal space (160). The entire first connection portion (133d) is located in a region A1 which extends from the internal space (160) over a distance of 1.0 mm or less. Also enclosed is a gas sensor including the gas sensor element.

1. Field of the Invention
The present invention relates to a gas sensor element, and to a gas sensor including the gas sensor element.
2. Description of the Related Art
A conventionally known gas sensor is attached to an exhaust path of an internal combustion engine such as an automotive engine for detecting a concentration of oxygen or a concentration of NOx in exhaust gas (gas to be measured) (refer to Patent Documents 1 and 2). Patent Documents 1 and 2 describe a gas sensor element used in the gas sensor and configured such that a plurality of platelike solid electrolyte bodies are laminated together. The gas sensor element includes electrodes provided on the front sides or back sides of the solid electrolyte bodies, and leads provided on the front sides or back sides of the solid electrolyte bodies and connected to the electrodes.
In Patent Documents 1 and 2, in order to ensure oxygen pumping performance, the electrodes are porous; as a result, the electrodes have gas permeability and water permeability. In contrast, the leads are formed to be dense since, in order to improve electrical conductivity, high density per unit area is desired. As a result, the leads are gas-impermeable and water-impermeable.
[Patent Document 1] Japanese Patent No. 4165652
[Patent Document 2] Japanese Patent Application Laid-Open (kokai) No. 2010-122187


A clamp apparatus to hold an object to a worktable includes a guiding pole mounted to the worktable, a pressing member connected to the guiding pole, a supporting pin extending from the pressing member towards the worktable, and a resilient member connected between the guiding pole and the worktable. the pressing member is rotatable related to the worktable between a first position and a second position. The pressing member forces the object against the worktable and the supporting pin passes through the worktable in response to restoring of the resilient member when the pressing member is moved to the first position. The supporting pin abuts against the worktable to keep a disengagement of the pressing member from the object overcoming restoring of the resilient member when the pressing member is moved to the second position.

1. Technical Field
The present disclosure relates to fixing apparatus and, more particularly, to a clamp apparatus for fixing an object to a worktable.
2. Description of the Related Art
Toggle clamps are used to hold objects in place for processing or testing, by clamping two objects together, or clamping an object to a worktable or another surface. An ordinary toggle clamp includes a clamping arm which pivots between a release position and a clamping position. However, substantial space is required to manipulate the clamping arm of the toggle arm.

Hong Fu Jin Precision Industry (ShenZhen) Co., Ltd.


A WDM signal monitoring system includes a measuring unit that measures power levels in a plurality of predetermined wavelength bands about a wavelength division multiplex signal, a waveform determination unit that determines an approximate waveform of each channel from each bit rate and modulation system of a plurality of channels which forms a wavelength division multiplex signal, and an approximation unit that determines a power level and a wavelength of each channel by approximating the power level in a plurality of wavelength bands which the measuring unit measured with the approximate waveform of each channel which the waveform determination unit determined.

1. Field
The present invention relates to a WDM signal monitoring system that monitors a power level and a wavelength of each channel of a wavelength division multiplexed (WDM) signal, that is, a so-called optical channel monitor (OCM), and a WDM transmission device equipped with the WDM signal monitoring system.
2. Description of the Related Art
The WDM transmission device measures a power level and a wavelength of a Wavelength Division Multiplex (WDM) signal by Optical Channel Monitor (OCM). Examples of construction of the OCM are shown in FIGS. 1 and 2. An example in FIG. 1 demultiplexes a WDM signal by an Arrayed Waveguide Grating (AWG) divider 10, and receives it with a photodiode (PD) array 12. In addition, an example in FIG. 2 spatially performs dispersion using a diffraction grating 14, and receives it with a PD array 16.
Regarding an OCM, in order to reduce cost, it is desirable to reduce the number of PDs. In the example of FIG. 1, four PDs per each channel are used as shown in an enlarged view on a right-hand side in FIG. 1. Then, the example finds a spectrum waveform by performing approximate calculation, such as Gaussian approximation, on the basis of a received light level of each PD, and determines the power level and wavelength of the signal. This approximation procedure is shown in FIG. 3. In FIG. 3, black dots 18 denote measured values from four PDs, and a curve 20 shows an approximated curve. By performing approximation as shown in the diagram, the power level P and wavelength λ of the channel are determined.
As an example, waveforms of 10-Gbps signal and 40-Gbps signal at the time of adopting a Non Return to Zero (NRZ) modulation system are shown in FIGS. 4 and 5, respectively. In this way, waveforms of a signal are different when bit rates of the signal are different.
Therefore, there is a problem that accuracy of an approximate calculation of OCM deteriorates and the power level and wavelength that are measured shift from actual values. In addition, as exemplified as a schematic diagram in FIG. 6, since spectral shapes change also by modulation systems, there is the same problem. Therefore, since the power level of the WDM signal is controlled on the basis of the wrong power level information, tilt compensation is not fully performed.
In addition to the above-mentioned problems, since the number of filters and nonlinear effects that are passed is different also with a route along which a path of an optical signal received has already passed, there is a problem that a spectrum waveform transforms.

Wavelength division multiplex signal monitoring system and wavelength division multiplex transmission device equipped with the same


A fluid dispensing system provides a non-contact method of monitoring the change in the fluid volume over time. This approach avoids the use of probes or sensors that come into direct contact with the fluid to be dispensed. The system comprises an apparatus comprising three chambers. The first chamber has a fixed volume and contains a pressurized gas. A solenoid valve is used to control the flow of gas from the first chamber into the second. The second chamber is sealed so that the combined mass of air in the first and second chambers remains fixed. The third chamber is adjacent to the second and contains medication in the form of incompressible fluid that is to be administered to a human or animal subject via a suitable delivery port. A piston is disposed between the second and third chambers and is movable responsive to the flow of gas into the second chamber to dispense fluid from the third chamber as desired. By sensing the pressure in the first and second chambers at any point in time, a processor is programmed to calculate the flow rate or dispensed volume of the fluid being delivered using principles derived from the Ideal Gas Law.

This invention relates to an apparatus and associated methods for dispensing fluids at a known, measurable rate. More specifically, the present invention pertains to a pump for the intravenous infusion of a medical treatment fluid in which the delivery rate is determined without direct measurement of the fluid flow rate, by using sensed pressure values and the principle of conservation of mass.
Drug delivery devices of varying construction are used to infuse medications or other biologically active substances into human or animal subjects. As used herein, the term "biologically active substance" means all types of medical and biological fluid used in the treatment of humans and animals including but not limited to peptides (such as insulin), analgesics, antiarrhythmics, steroids, hormones, nicotine, vitamins, anti-migraine medicine, anti-coagulants, local anesthetics, vaccines, allergens, muscle relaxants, etc. It should also be recognized that the apparatus is suited for the delivery of fluid into mammals, plants, fish, reptiles, and birds. The dosage levels are typically small and must be maintained over long periods of time in order to sustain a desired effect or result in the subject. A typical application is the administration of pharmaceutical preparations, where the treatment is vital for correct biological activity. The dosage delivery in such instances is often critical, and effective feedback in the form of measured flow rates is seldom available with currently used devices.
A wide variety of approaches have been offered by the prior art to meet the need for a portable device to automatically administer a substance into the vein of a subject. The need for such devices has thus been demonstrated, although the success to date has been limited. This limited success is, at least in part, due to the inability of these devices to provide a simple means to accurately determine the rate at which substance is actually delivered. Prior art devices employ such techniques as mechanical pumps, pressurized gases, pressurized liquids, or gas generating mechanisms. Because the administered substance must be maintained in a sterile environment, a flexible diaphragm is usually employed to separate it from the pump or driving gas.
The requirement for a sterile environment usually precludes direct measurement of either the rate of infusion or the total amount of the medication actually delivered. Instead, the rate of infusion is usually estimated based on the predicted rate of some other event. For instance, some devices use a pressure source in conjunction with a restrictor to regulate the flow of a driving gas. The assumed flow rate can, however, be inaccurate due to variability in pressure, temperature, viscosity of the drug being administered, or other environmental and mechanical factors. Devices using gas-generating mechanisms assume that the flow rate can be determined by correlation to an input such as a voltage. In some cases, other parameters such as body temperature or pulse rate may be used as a feedback mechanism to vary some driving force such as pressure in the cited example. In many instances, however, the precise rate at which a substance must be administered is predetermined without the availability of a feedback mechanism.
U.S. Pat. No. 4,443,218 to DeCant, Jr. et al. discloses an implantable infusate pump that utilizes a displacement reservoir to pump an infusate chamber. The displacement reservoir contains a highly viscous fluid that is provided by a second pressure reservoir that utilizes a mechanical pump. By monitoring the pressure differential across a flow restrictor located between the pressure and displacement reservoirs, the flow from the infusate chamber is indirectly measured. While this approach offers a means of measuring the flow of an administered substance, it has several disadvantages in terms of power consumption, overall life, and failsafe operation. Potential leakage of the liquid driver and the use of a mechanical pump are not conducive to sterile applications. The complex arrangement of a mechanical pump with springs and valves to control the pressure inside the pressure reservoir also makes this device more likely to fail as a result of wear.
U.S. Pat. No. 5,527,288 to Gross et al. discloses a drug delivery system based on the use of a gas-generating device. An electronic circuit is used to control the time and rate of gas generation into a chamber containing a flexible membrane. Pressure inside the chamber is used to pump a drug contained in a second chamber via the membrane common to both chambers. The generation rate is, however, dependent on environmental factors such as temperature and atmospheric pressure. The lack of a measuring means in this device thus prevents precise determination of the actual drug delivery rate.
A more complex means of controlling the drug delivery rate is also disclosed by Gross et al. in U.S. Pat. No. 6,186,982. In this patent, the same basic gas-generating means is used as in U.S. Pat. No. 5,527,288; however, a blocking member is incorporated to compensate for errors induced by temperature and pressure variations. Because of the more complex methods incorporated in this device, it is more prone to malfunction or loss of calibration than that disclosed in U.S. Pat. No. 5,527,288. Errors produced by these or other sources thus preclude an accurate determination of the drug delivery rate using this device.
U.S. Pat. No. 5,421,208 to Packard et al. discloses a device for measuring liquid parameters that is directed to peritoneal dialysis, in which a sterile aqueous solution must flow both into and out of the device. Two gas chambers are used to both control and measure the flow of a liquid contained in yet a third chamber. The first of the two gas chambers acts as either a pressure or vacuum source for the second, depending upon the direction of flow required. The second gas chamber acts as a pump for the liquid chamber via a flexible diaphragm dividing the two. The volume of the pump and liquid chamber remains constant during operation. Thus, by determining the volume of the pump chamber, the volume of the liquid chamber is determined. By monitoring the flow of gas from the source chamber and the pressure in the pump chamber, the volume of the pump chamber and, therefore, the liquid chamber can be deduced. One disadvantage of this approach is the need for a flow measurement sensor, which is more complex and prone to failure than sensors used in the art for measuring pressure. There is also a greater possibility for error in the liquid flow measurement due to loss of calibration or malfunction of the gas flow sensor.

This patent is subject to a terminal disclaimer.


A stable frequency is outputted by an oscillator circuit including a constant current circuit which is electrically connected between a first terminal and a second terminal, a voltage controlled oscillator circuit in which an oscillation frequency fluctuates in accordance with a potential difference between power supply voltage terminals, an n-channel transistor, a p-channel transistor in which a gate-source voltage is set to be constant by the constant current circuit, and a capacitor, in which a source electrode of the p-channel transistor is electrically connected to the first terminal, a drain electrode of the p-channel transistor is electrically connected a drain electrode and a gate electrode of the n-channel transistor, a source electrode of the n-channel transistor is electrically connected to the second terminal, and a gate electrode of the n-channel transistor is electrically connected to the second terminal through the capacitor.

1. Field of the Invention
The present invention relates to an oscillator circuit and a semiconductor device including the oscillator circuit.
2. Description of the Related Art
In recent years, semiconductor devices in each of which various circuits are integrated on one insulating surface have been developed. As a clock circuit necessary for a circuit, various oscillator circuits are known.
Oscillator circuits have been developed using CMOSs, and an oscillator circuit using a CMOS inverter is given as a typical example (for example, Patent Document 1: Japanese Published Patent Application No. 2003-283307).

Oscillator circuit having a stable output signal resistant to power supply voltage fluctuation

Semiconductor Energy Laboratory Co., Ltd.


The present embodiments provide methods for writing content to a media that comprise retrieving a first portion of a key structure from the media or a remote server, generating or receiving a second portion of the key structure based on the first portion of the key structure, encrypting content based at least on the second portion of the key structure, producing encrypted content, and writing the encrypted content onto the media. The present embodiments further provide recording media that include a digitally writable surface that is optically readable, a control area optionally comprising a pre-recorded set of keys defining a first portion of a key structure, and a data portion that records non-pre-recorded content protected according to a second portion of the key structure generated according to at least a portion of the first portion of the key structure.

Movie and music industries generate billions of dollars in revenue. A significant percentage of this revenue is through sales and rentals of movie titles and/or albums directly to consumers. Individual consumers can go to retail outlet stores and purchase movie titles, for example, on digital video discs (DVD) which can then be played at the users' home on DVD players.
By allowing users to purchase titles for at-home use, the movie industry has substantially increased its revenues. Other systems deliver movie titles directly to a user's home, for example through the Internet, cable television and/or satellite communication. Video-on-demand allows a user to select a desired title from a list of available titles, and the title is delivered to the user. Typically, the user must view the content at a predefined time. In some instances, a user is required to view the title within a predefined time period (e.g., within 24 hours).
Titles made available to the public, either through purchases of DVDs or through on-demand service, are protected in attempts to prevent users from duplicating the content. As such, users are generally unable to copy the content.

Secure transfer of content to writable media


In a signal transmitter and a signal receiver, a multiplexing part multiplexes a video signal and a time-base-compressed audio signal on the basis of a multiplexing control signal to transmit the multiplexed signal through a data line in the signal transmitter, and a demultiplexing part demultiplexes a video/audio multiplexed signal received through the data line into the original video signal and audio signal by a demultiplexing control signal in the signal receiver. According to the so-configured signal transmitter and signal receiver, it is possible to realize a signal transmission system compliant with the DVI standard, in which the audio signal as well as the video signal can be transmitted.

A conventional signal transmission system according to DVI (Digital Visual Interface) standard will be described with reference to FIG. 26. FIG. 26 is a diagram illustrating a structure of the conventional transmission system.
In this figure, numerals 2601 to 2603 denote TMDS encoders/serializers provided at the transmitting end, which TMDS-encode inputted component signals such as RED, GREEN, and BLUE signals, serialize the encoded signals, and output the same to transmission lines. Numerals 2604 to 2606 denote TMDS decoders/recoverer provided at the receiving end, which TMDS-decode the received signals, recover the decoded signals, and restore the component signals.
A DE (Data Enable) signal is a signal indicating a period during which the component signal such as RED, GREEN, and BLUE signals exists, and this is a HIGH active signal. For example, the DE signal is LOW in a period of a horizontal synchronizing signal or vertical synchronizing signal of video.
CTL (Control) signals CTL 0, CTL 1, CTL 2, and CTL 3 are prepared as control signals. However, these signals are not in use in the present DVI standard. More specifically, the levels of the signals are always 0.
The so-configured conventional signal transmission system will be described.
The TMDS encoders/serializers 2601 to 2603 at the transmitting end convert video signals (RGB signals) inputted at 8 bits into signals of 10 bits, serialize the converted signals, and output them to transmission lines. The object of the 8 bit-to-10 bit conversion is to reduce data changing points and convert the data into a format that is suitable for high-speed transmission. Further, the TMDS encoders/serializers 2601 to 2603 convert the 2 bit-CTL signals into 10 bit-CTL signals and transmit the converted CTL signals to the transmission lines. The DE signals are also encoded, serialized, and transmitted to the transmission lines.
The TMDS decoders/recoverers 2604 to 2606 at the receiving end decode 10-bit serial data received through the transmission lines into the 8-bit color signals, the DE signals, and the 2-bit CTL signals to decompress the signals.
However, the DVI standard is a standard for transmitting only video signals, and the conventional signal transmission system cannot transmit audio signals.
The present invention is made to solve the above-mentioned problem and has for its object to provide a signal transmitter and a signal receiver that can realize a signal transmission system according to the DVI standard in which audio signals as well as video signals can be transmitted.

Signal transmitting device and signal receiving device

Matsushita Electric Industrial Co., Ltd.


A dual band antenna and an electronic device are provided. The dual band antenna includes a feed end, an annular connection end, a metal screw, a first extension path, a second extension path, a third extension path, and a grounding part. The annular connection end has an opening and is connected to the feed end. The metal screw has a threaded stud passing through the opening, so that the metal screw is electrically connected to the annular connection end. The feed end, the first extension path, the second extension path, the third extension path, and the grounding part are sequentially connected to each other. The dual band antenna is configured to have a monopole antenna and a loop antenna, so that the dual band antenna has a wide operating frequency band, and the monopole antenna operates at 3.6 GHz and the loop antenna operates at 4.6 GHz.

Miniaturization of electronic products often results in spatial limitations when an antenna is disposed in the electronic product. Therefore, it can be difficult to meet requirements on frequency bands and specifications within limited space in the design of the antenna.
Common designs for reducing a size of the antenna include utilizing a chip antenna, using a high dielectric coefficient material as a carrier, etc. The chip antenna has a small volume, but an antenna operating bandwidth thereof is usually narrower, so that demands for communication systems nowadays cannot be fully met. Even though the use of the high dielectric coefficient material as the carrier can, through a cooperation of a three-dimensional design of the antenna and using the high dielectric coefficient material, effectively improve space utilization, but a process for manufacturing such an antenna is more difficult and involves higher costs.

Dual band antenna and electronic device using the same

USI SCIENCE AND TECHNOLOGY (SHENZHEN) CO., LTD.


A drug transferring needle includes a needle base portion, a first needle portion having therein an air passage, and a second needle portion longer than the first needle portion and arranged parallel to the first needle portion. In the first needle portion, a first air vent being one end of the air passage is provided on a distal end side of the second needle portion from a second air vent being the other end of the air passage. In the second needle portion, one end of a liquid passage is connected to the inside of the needle base portion, and the other end thereof is a liquid pass opening of the second needle portion. The second needle portion has a distal end having the liquid pass opening, a base portion connected to the needle base portion, and an intermediate portion connecting the distal end and the base portion.

In many cases, a drug prescribed for an inpatient in a hospital is obtained by taking out several kinds of drugs from different drug containers to mix the drugs. In addition, such a drug mixing operation is often manually performed by an operator, such as a pharmacist. To mix the drugs, an operation of inserting an injection needle into each of the drug containers to suck the drug therein by means of a syringe is necessary. This operation is a work load on the operator.
For instance, when a sealed vial container is used as the drug container to suck the drug from the drug container into the syringe, a pumping operation is often performed. The pumping operation is an operation in which suction is started in a state where an air layer having a smaller volume than the drug to be sucked is previously reserved in the syringe, thereby pushing and pulling the plunger of the syringe over and over again. When the pumping operation is performed, the drug in the drug container is gradually substituted for an air. The pumping operation is an operation which takes time and is troublesome for the operator, such as a pharmacist. In addition, when a viscosity of the drug in the drug container is high, viscosity resistance when the drug passes through the injection needle is increased. Therefore, the operator needs a large force.
In this way, the operation of sucking the drug from the drug container into the syringe needs time and labor, resulting in a great work load on the operator. Likewise, when the drug is discharged from the syringe into the drug container, first, a gas in the drug container is slightly sucked, thereby gradually substituting a liquid in the syringe for the gas in the drug container. The operation has also a great work load on the operator.
To reduce this work load, a drug transferring needle in which an air vent slot is provided in part of the needle to make the pumping operation unnecessary is proposed (for instance, see Patent Literature 1). In the conventional drug transferring needle, the air vent slot is provided in part of the needle, so that a pressure in the drug container and an atmospheric pressure are substantially equal.
FIG. 11 is a partially sectional view of a conventional drug transferring needle 1. In the conventional drug transferring needle 1, a metal needle 2 and a needle base 3 are integral. In the drug transferring needle 1, a sheath 4 is partially fitted onto an outer side of the metal needle 2, and an air vent slot 4a is formed between the metal needle 2 and the sheath 4. In addition, in the drug transferring needle 1, a filter 6 formed of a hydrophobic synthetic resin is attached to near an air vent opening 4b at one end of the air vent slot 4a.
The drug transferring needle 1 is attached to a syringe 7. Therefore, the pressure in the drug container and the atmospheric pressure are substantially equal, thereby making the pumping operation unnecessary. The reason why the pumping operation is unnecessary will be described.
When the drug transferring needle 1 is needled into a rubber stopper of a drug container 8 to suck a drug 9 from the drug container 8 into the drug transferring needle 1, part of the drug 9 in the drug container 8 is sucked into the syringe 7 through the drug transferring needle 1. As a result, the drug 9 in the drug container 8 is reduced. At this time, a gas 10 in the drug container 8 expands by a reduced volume of the drug 9. Therefore, a pressure of the gas 10 in the drug container 8 is lowered. Then, a pressure difference occurs between the pressure of the gas 10 in the drug container 8 and the atmospheric pressure. Outside air is then drawn into the drug container 8 through the filter 6 and the air vent slot 4a of the drug transferring needle 1 so as to reduce the pressure difference. In this way, a bubbled air 5a enters into the drug container 8 through the air vent slot 4a of the drug transferring needle 1. Therefore, the pressure difference is eliminated so that the pressure of the gas 10 in the drug container 8 is substantially equal to the atmospheric pressure. In this way, when the drug transferring needle 1 is used, the pressure of the gas 10 in the drug container 8 is regulated to be substantially equal to the atmospheric pressure. With this, the pumping operation of the syringe 7 can be unnecessary, and the work load when the drug is sucked from within the drug container 8 can be reduced.

Drug transferring needle and drug transferring method