A system and method for deploying resources to users. A system includes a computer that executes a resource deployment manager. The resource deployment manager provides an interface for selecting a remote user to whom a central resource is to be assigned, and for selecting a template upon which to base the assignment of the resource to the selected user. Further, the resource deployment manager assigns the central resources to the selected user based on the selected template.

Prior to the advent of the personal computer, a mainframe or mini-computer supporting multiple individual user terminals was the dominant computing paradigm. This centralized architecture allowed for efficient use of expensive computer hardware and software resources by sharing those resources across multiple users. With the coming of the relatively inexpensive personal computer, a new computing model arose that employed computing resources localized at each user to displace the remote and centralized resources typifying the earlier era.
The advantages of the centralized computing model are many however, and ubiquitous networking has led to the resurgence of centralized computing in a variety of forms. In one embodiment, a server provides processing and/or storage resources to one or more remote clients. In other embodiments, a remote client is assigned undivided access to a workstation or personal computer module maintained at a central site. In any embodiment, consolidation of data and program storage and/or computing resources reduces maintenance and support costs, while enabling increased system security. The remote client may take various forms. A remote client having minimal processing and storage capabilities, and that relies on centralized resources for adequate functionality is known as a "thin client."
Centralized computer systems are not without disadvantages. For example, failure of a single server supporting multiple users results in a loss of productivity proportional to the number of users supported. Architectures assigning unshared resources to each remote client serve to mitigate such disadvantages.
Each remote user connecting to a centralized system is assigned a set of resources. The extent of resources available to each user varies in accordance the user's needs. For example, a user may be assigned more or fewer resources in accordance with the applications utilized, or the user's security ranking. Allocation of system resources to users is generally controlled by a system administrator. Flexible and efficient methods for controlling user resource assignments are desirable to administrators of systems supporting a large number of users.

Hewlett-Packard Development Company, L.P.


An apparatus and method to objectively measure sensory discrimination thresholds at a test site in the upper aero digestive tract of a patient. A time and pressure controlled puff of air is delivered to the input of a Y-shaped tube; one output branch of the Y-shaped tube delivers the puff of air to the patient and the other output branch delivers the puff of air to a pressure transducer, for measurement and display of the pressure.

The present invention relates to an apparatus and a method to objectively measure sensory discrimination thresholds by delivering a time and pressure controlled air puff to the upper aero digestive tract, including, for example, the oral cavity, pharynx, or supraglottic larynx of a patient.
Within this application several publications are referenced by Arabic numerals within parentheses. Full citations for these and other references may be found at the end of the specification immediately preceding the claims. The disclosures of all of these publications in their entireties are hereby incorporated by reference into this application in order to more fully describe the state of the art to which this invention pertains.
There is a dearth of published studies of supraglottic and pharyngeal sensation in normal healthy controls, in the elderly, or in those who have suffered from a cerebrovascular accident (CVA). One of the primary problems with measuring sensation in this region (the area innervated by the superior laryngeal nerve) is the presence of the gag reflex and the relative inaccessibility of this area in awake individuals. These obstacles preclude standard sensory discrimination tests such as static and moving two point discrimination, vibratory testing, and stereognosis (1).
Knowledge of pharyngeal and supraglottic sensory discrimination thresholds is particularly important since hypesthesia or anesthesia in this area of the head and neck can cause severe dysphagia and an increased frequency of aspiration. Dysphagia and aspiration are commonly seen in the elderly (2), in those who have suffered a stroke (3), and in patients who have had ablative cancer surgery of the pharynx and larynx (4, 5) and/or loss of cranial nerves. The development of treatment modalities which address the sensory deficits in the pharynx and larynx is dependent upon defining and quantifying the sensory deficits in this region. The first step towards this goal is to establish normal thresholds for sensory discrimination.
However, as of yet, it appears that no one has been able to achieve this first step of measuring pharyngeal sensation in healthy control subjects, much less than in stroke patients with dysphagia. In other medical fields, air pulse stimulation of the cornea, or pneumatic tonometry has been used by ophthalmologists in order to measure intraocular pressure (6). Sensory discrimination testing using this technique, however, was not applied to the cornea. Air pulse stimuli have also been used as a natural stimulus to study the mechanisms whereby somatosensory systems analyze sensory stimulus patterns (7, 8). Furthermore air pulse stimuli have been shown to be an extremely sensitive and reliable method of determining sensory discrimination thresholds in the upper extremity of man (8, 9). However, it appears that no previous method of sensory testing of the upper aero digestive tract, including specifically the oral cavity, supraglottic larynx, or pharynx has been described.

Measurements of respiratory sensory discrimination thresholds


A complex band-pass ΔΣ AD modulator is provided with a subtracter device, a complex band-pass filter, first and second AD converters, and first and second DA converters. The first and second DA converters and first and second logic circuits are sandwiched by first and second multiplexers. At a first timing of a clock signal, the first multiplexer inputs and outputs the first and second digital signals as they are, and at a second timing thereof, the first multiplexer inputs the first and second digital signals, and outputs the first digital signal as a second digital signal and outputs the second digital signal as a first digital signal. The second multiplexer inputs and outputs first and second analog signals similarly. The first and second logic circuits substantially noise-shapes non-linearities of the first and second DA converters by realizing complex digital and analog filters, using high-pass and low-pass element rotation methods.

1. Field of the Invention
The present invention relates to a complex band-pass ΔΣ AD modulator, an AD converter circuit, and a digital radio receiver, and in particular, to a complex band-pass ΔΣ AD modulator for use in a digital radio receiver or the like, an AD converter circuit using the complex band-pass ΔΣ AD modulator, and a digital radio receiver using the AD converter circuit.
2. Description of the Related Art
Application of a band pass ΔΣ AD converter to an RF receiver circuit in a communication system such as a mobile phone and a radio LAN has been under consideration (for example, See first to fifth non-patent documents). Further, in an application used in the communication system (in particular, Low-IF receiver), the application of a complex band-pass ΔΣ AD modulator capable of suppressing an image signal generated on the inside of the modulator due to a mismatch between I path and Q path has been also under consideration since the image signal deteriorates a characteristic of the system (for example, See first to sixth non-patent documents). In the RF receiver circuit, when an AD converter circuit can be provided so as be shifted in a direction closer to an antenna, complicated functions which were conventionally realized by analog circuits can be realized by means of a digital signal processing method, then this achieves improvement of an integrity and a performance of the entire system.
In order to realize that, superior linearity, dynamic range, signal band and ability to eliminate the image signal are required for the AD converter circuit. Since the complex band-pass ΔΣ modulator is capable of suppressing the level of the image signal generated therein, any influence from the mismatch generated between the I and Q signal paths can be reduced. The ΔΣ AD modulator realizes a higher precision by means of an oversampling method and a noise shaping method. In the case of using a higher-order one-bit ΔΣ modulator to further pursue the high precision, the stability is a bottleneck, and a modulator having a higher-filter-order (and a higher-order digital filter as provided with the modulator at the next stage or the subsequent stage) and a higher oversampling rate (referred to as an OSR hereinafter) are required (for example, See seventh non-patent documents). In this case, it is necessary to increase the sampling ratio to increase the OSR. On the other hand, when a multi-bit ΔΣ AD modulator is used, a high resolution can be obtained with a low OSR, and the problem of the stability can be reduced (for example, See seventh and eighth non-patent documents).
Documents related to the present invention are as follows:
(1) Japanese patent laid-open publication No. JP-05-275972-A (referred to as a first patent document hereinafter);
(2) Japanese patent laid-open publication No. JP-11-017549-A (referred to as a second patent document hereinafter);
(3) Japanese patent laid-open publication No. JP-2000-244323-A (referred to as a third patent document hereinafter);
(4) Japanese patent laid-open publication No. JP-2002-100992-A (referred to as a fourth patent document hereinafter);
(5) K. Philips, "A 4. 4 mW 76 dB complex ΣΔADC for Bluetooth receivers", ISSCC Digest of Technical Papers, Vol. 46, pp. 64–65, February 2003 (referred to as a first non-patent document hereinafter);
(6) F. Henkel et al., "A 1 MHz-bandwidth second-order continuous time quadrature band-pass sigma-delta modulator for low-IF radio receivers", IEEE Journal of Solid-State Circuits, Vol. 37, pp. 1628–1635, December 2002 (referred to as a second non-patent document hereinafter);
(7) F. Esfahani et al., "A fourth order continuous-time complex sigma-delta ADC for low-IF GSM and EDGE receivers", Symposium of VLSI Circuits, Digest of Technical Papers, pp. 75–78, June 2003 (referred to as a third non-patent document hereinafter);
(8) R. Schreier et al., "A 10–300 MHz IF-digitizing IC with 90–105 dB dynamic range and 15–333 kHz bandwidth", IEEE Journal of Solid-State Circuits, Vol. 37, pp. 1636–1644, December 2002 (referred to as a fourth non-patent document hereinafter);
(9) T. Salo et al., "A dual-Mode 80 MHz band-pass ΔΣ modulator for a GSM/WCDMA IF-receiver", ISSCC Digest of Technical Papers, Vol. 45, pp. 218–219, February 2002 (referred to as a fifth non-patent document hereinafter);
(10) S. A. Jantzi et al., "Quadrature band-pass ΔΣ modulator for digital radio", IEEE Journal of Solid-State Circuits, Vol. 32, pp. 1935–1949, December 1997 (referred to as a sixth non-patent document hereinafter);
(11) S. R. Norsworthy et al. (editors), "Delta-Sigma Data Converters, -Theory, Design, and Simulation", IEEE Press, 1997 (referred to as a seventh non-patent document hereinafter);
(12) T. Ueno et al., "A fourth-order band-pass Δ-Σ modulator using second order band-pass noise-shaping dynamic element matching", IEEE Journal of Solid-State Circuits, Vol. 37, pp. 809–816, July 2002 (referred to as an eighth non-patent document hereinafter);
(13) T. Shui et al., "Mismatch shaping for a current-mode multibit delta-sigma DAC", IEEE Journal of Solid-State Circuits, Vol. 34, pp. 331–338, March 1999 (referred to as a ninth non-patent document hereinafter);
(14) L. R. Carley, "A noise-shaping coder topology for 15 bit converters", IEEE Journal of Solid-State Circuits, Vol. 24, pp. 267–273, April, 1989 (referred to as a tenth non-patent document hereinafter);
(15) E. Fogleman et al., "A 3.3-V single-poly CMOS audio ADC delta-sigma modulator with 53.8-dB peak SINAD and 105-dB peak SFDR", IEEE Journal of Solid-State Circuits, Vol. 35, pp. 297–307, March 2000 (referred to as an eleventh non-patent document hereinafter);
(16) R. Schreier et al., "Speed vs. dynamic range trade-off in oversampling data converters", in C. Toumazou et al. (editors), Trade-Offs in Analog Circuit Design, The Designer's Companion, Kluwer Academic Publishers, pp. 644–653, 2002 (referred to as a twelfth non-patent document hereinafter);
(17) Y. Yang et al., "A 114 dB 68 mW chopper-stabilized stereo multi-bit audio A/D converter", ISSCC Digest of Technical Papers, Vol. 46, pp. 56–57, February 2003 (referred to as a thirteenth non-patent document hereinafter);
(18) B. Razavi, "Principles of Data Converter Design", IEEE Press, 1995 (referred to as a fourteenth non-patent document hereinafter);
(19) A. Swaminathan, "A single-IF receiver architecture using a complex SD modulator", Master of Engineering thesis, Carleton University, Ottawa, Ontario, Canada, 1997 (referred to as a fifteenth non-patent document hereinafter);
(20) D. B. Barkin et al., "A CMOS oversampling band-pass cascaded D/A converter with digital FIR and current-mode semi-digital filtering", Symposium of VLSI Circuits, Digest of Technical Papers, pp. 79–82, June 2003 (referred to as a sixteenth non-patent document hereinafter);
(21) H. San et al, "A noise-shaping algorithm of multi-bit DAC non-linearities used in complex band-pass ΔΣ AD modulators", Circuit and System Workshop at Karuizawa by the Institute of Electronics, Information and Communication Engineers in Japan, published by the Institute of Electronics, Information and Communication Engineers, in Japan, pp. 85–90, April 2003 (referred to as a seventeenth non-patent document hereinafter);
(22) H. San et al., "An Element Rotation Algorithm for Multi-bit DAC Nonlinearities in Complex Band-pass Delta-Sigma AD Modulators", IEEE 17th International Conference on VLSI Design, Mumbai, India, pp. 151–156, January 2004 (referred to as an eighteenth non-patent document hereinafter);
(23) H. San et al., "A noise-shaping algorithm of multi-bit DAC nonlinearities in complex band-pass ΔΣ modulators", IEICE Transactions on Fundamentals, Vol. E87-A, No. 4, pp. 792–800, April 2004 (referred to as a nineteenth non-patent document hereinafter); and
(24) M. Miller, "Introduction to Sigma-Delta data converters", IEEE 2003 Custom Integrated Circuits Conference, Educational Sessions, San Jose, U.S.A., September 2003 (referred to as a twentieth non-patent document hereinafter).
However, in contrast to the one-bit DA converter having a superior linearity, it is not possible for a non-linearity of an internal DA converter of a multi-bit ΔΣ AD modulator to be noise-shaped on the inside of the modulator, and this leads to disadvantageous deterioration in the precision of the entire AD converter. These problems will be described in detail below.
FIG. 2A is a block diagram showing a configuration of a band-pass ΔΣ AD modulator according to a prior art. FIG. 2B is an equivalent block diagram of the band-pass ΔΣ AD modulator of FIG. 2A.
Referring to FIG. 2A, the band-pass ΔΣ AD modulator includes a subtracter SU1, a band-pass filter BP1, an AD converter AD1, and a DA converter DA1. In FIG. 2A, Ain denotes an analog input signal, and Dout denotes a digital output signal. In the equivalent block diagram of FIG. 2B, the band-pass ΔΣ AD modulator includes the subtracter SU1, a band-pass filter TR1 having a transfer function H (z), and adders SM1 and SM2. In FIG. 2B, X (z) denotes the analog input signal, Y (z) denotes the digital output signal, E (z) denotes a quantization error of the AD converter AD1, and δ (z) denotes a non-linearity error of the DA converter DA1. A relationship between the input and output signals can be represented by the following Equations:
                                          M                                      (              z              )                                =                                                    H                                                  (                  z                  )                                                            1                +                                  H                                                        (                    z                    )                                                                                [                                                X                                                        (                    z                    )                                                  +                                                      1                                          H                                                                    (                        z                        )                                                                                E                                                              (                      z                      )                                                                      +                                                      1                                          H                                                                    (                        z                        )                                                                                δ                                                              (                      z                      )                                                                                ]                                      ,        and                            (        1        )                                          Y                                (            z            )                          =                                                            H                                                  (                  z                  )                                                            1                +                                  H                                                        (                    z                    )                                                                                [                                                [                                      X                                                              (                      z                      )                                                        ]                                +                                                      1                                          H                                                                    (                        z                        )                                                                                E                                                              (                      z                      )                                                                      -                                  δ                                                        (                    z                    )                                                              ]                                .                                    (        2        )
A signal component S (z) and a noise component N (z) are defined as follows:
                                                                                S                                                        (                    z                    )                                                  ≡                                                                            H                                                                    (                        z                        )                                                                                1                      +                                              H                                                                          (                          z                          )                                                                                X                                                              (                      z                      )                                                                                ,              and                                                                                N                                                  (                  z                  )                                            ≡                                                                                H                                                                    (                        z                        )                                                                                1                      +                                              H                                                                          (                          z                          )                                                                                [                                                                                1                                                      H                                                                                (                              z                              )                                                                                E                                                                                (                            z                            )                                                                                -                                              δ                                                                          (                          z                          )                                                                                ]                                                  .                                                                        (        3        )
It is clearly understood from the Equation (3) that the quantization noise E (z) of the internal AD converter AD1 is noise-shaped, however, the non-linearity error δ (z) of the DA converter DA1 is not noise-shaped and directly outputted, and this leads to that it is difficult to realize a ΔΣ AD converter of a higher precision.
In order to noise-shape the non-linearity of the internal multi-bit DA converter DA1 of the band-pass ΔΣ AD modulator, algorithms such as a dynamic element matching method (for example, See the eighth non-patent document) and an element rotation method (for example, See the ninth non-patent document) were proposed. However, those methods can only be applied to a real band-pass ΔΣ AD modulator having a single input terminal and a single output terminal, as shown in FIGS. 2A and 2B.
Next, a noise-shaping algorithm for noise-shaping a non-linearity of a conventional DA converter for use in a real modulator having a single input terminal and an output terminal using the element rotation method will be described. A first-order noise-shaping algorithm for first-order noise-shaping the non-linearities of DA converters which are provided in low-pass and high-pass modulators each having a single input terminal and a single output terminal is also used in a noise-shaping algorithm for a complex band-pass modulator.
FIG. 3 is a circuit diagram showing a configuration of a DA converter of nine-level precision segment current cell type according to the prior art. A relationship between the DA converter of segment type and a mismatch value in respective current cells will be described. In the DA converter of segment current cell type having a conventional nine-level resolution includes eight unit current cells CS0 to CS7, and a resistance R, as shown in FIG. 3. When a current applied to a k-th current cell CSk is defined as Ik (k=0, 1, 2, . . . , 7), all of the currents Ik are equal to each other in an ideal state. On the other hand, the current values of the respective current cells are different from each other due to variation in the processes upon manufacturing an IC chip. The current values of the respective current cells are represented by the following Equations:Ik≡I+ek (k=0, 1, 2, . . . , 7),I≡(I0+I1+I2+ . . . +I7)/8,ande0+e1+e2+ . . . +e7=0,
where ek in the above Equation denotes mismatch values in the current values Ik due to the above mentioned reason. When a digital input signal is m, and the current cells CS0, CS1, CS2, . . . , CSm-1 are turned on, then the output voltage from the DA converter is represented by the following Equation:Vout=mRI+δ.
The non-linearity δ of the DA converter is given by the following Equation:δ≡R(e0+e1+e2+ . . . +em-1).
An influence caused by the mismatch values e0, e1, . . . , e7 (or, equivalently, the non-linearity δ of the DA converter) on the output power spectrum of the AD converter is generated in a substantially flat shape within a signal band.
Next, a low-pass element rotation method disclosed in, for example, the twelfth non-patent document, will be described. FIG. 4A is a block diagram showing a configuration of a DA converter circuit using the low-pass element rotation method according to the prior art. FIG. 4B is an equivalent block diagram of the DA converter circuit of FIG. 4A.
The DA converter circuit shown in FIG. 4A includes a digital low-pass filter TR11 having a transfer function (1/(1−z−1), a DA converter DA2 having a non-linearity δ (z), and an analog high-pass filter TR12 having a transfer function (1−z−1), which are connected in a form of cascade. In this case, the digital low-pass filter TR11 of FIG. 4A includes an adder SM11, and a delay circuit DE11 for feeding back an output signal from the adder SM11 to the adder SM11, as shown in FIG. 4B. Further, the analog high-pass filter TR12 of FIG. 4A includes a subtracter SU11, and a delay circuit DE12 for delaying an output signal from the DA converter DA2 by a predetermined time length and thereafter outputting a delayed signal to the subtracter SU11, as shown in FIG. 4B. The respective signals C1 to C4 are represented by the following Equations:C2(z)=(1/(1−z−1)C1(z)  (4);C4(z)=(1−z−1)C3(z)  (5); andC3(z)=C2(z)+δ(z)  (6).
Therefore, the analog output C4 (z) is represented by the following Equation:C4(z)=C1(z)+(1−z−1)δ(z)  (7)
The non-linearity δ (z) of the DA converter DA2 is subjected to a first-order noise-shaping by the digital low-pass filter TR11 having a transfer function (1−z−1). Further, the following Equations can be obtained from the Equations (4), (5) and (6):C2(n+1)=C2(n)+C1(n+1)  (8);C4(n+1)=C3(n+1)−C3(n)  (9); andC3(n)=C2(n)+δ(n)  (10).
The non-linearity δ(z) of the DA converter DA2 could be noise-shaped if it was possible to replace the multi-bit DA converter DA2 on the inside of the low-pass ΔΣ AD modulator by the circuit shown in FIGS. 4A and 4B. However, it is actually impossible to realize such a circuit. For example, when the signal C1 (n) is always a positive integer of 2, the input signal C2 (n) inputted to the DA converter DA2 is infinite according to increase of a timing "n" and eventually exceeds an input range of the DA converter DA2, and this leads to that it impossible to accurately realize the DA conversion. The low-pass element rotation algorithm was proposed in order to solve the above-mentioned problems and can equivalently realize the circuit. The following is proposed for the DA converter of segment current cell type.
(A) The respective current cells are arranged in a ring shape in the DA converter of segment current cell type according to the prior art, as shown in FIG. 5.
(B) A pointer for storing a position of the turned-on current cell is provided in the DA converter circuit. When the pointer is set to P (n) at the timing "n", the P (n)-th current cell is selected for the input data at a next sampling timing "n+1".
When it is assumed that the number of the current cells is infinite, and also the following Equations are assumed:C2(n)=a,andC1(n+1)=b(0≦b≦8),
then the current cells CS0, CS1, . . . , CS (a+b−1) of the DA converter DA2 are turned on. In this case, the following Equations are obtained from the Equations (8) and (10):C3(n+1)=(a+b)RI+R(e0+e1+e2+ . . . +ea+b−1).
Further, because of the following Equation:C3(n)=aRI+R(e0+e1+e2+ . . . +ea−1),the analog signal C4(n+1) of the DA converter DA2 is represented by the following Equation:C4(n+1)=C3(n+1)−C3(n)=bRI+R(ea−1+ea+ea+1+ . . . +ea+b−1).
Concretely speaking, the current cells CS (a−1), CSa, CS (a+1), . . . , CS (a+b−1) of the DA converter are turned on. In the present example, there is a possibility that a+b−1>7. However, since the actual DA converter is provided with only eight current cells, the current cells CS (mod8(a−1)), CS (mod8 (a)), CS (mod8 (a+1)), . . . , CS (mod8 (a+b−1)) as arranged in a ring shape are turned in the case of applying the low-pass element rotation algorithm. In this specification, in place of a general notation "x modulo y" or "x mod y", which show a remainder as obtained when "x" is divided by "y", a simplified notation thereof, "modyx" is used for the description. An operation of the low-pass element rotation algorithm will be described in detail as follows:
(a) It is assumed that the input data is C1(n)=cn (n=0, 1, 2, 3, . . . ) at the timing "n";
(b) The number "cn" of current cells CS (mod8 (P(n)+1)), CS (mod8 (P(n)+2)), CS (mod8 (P(n)+3)), . . . , mod8 (P(n)+cn) are turned on; and
(c) At the timing "n+1", the pointer P (n+1) is set as follows:P(n+1)=mod8 (P(n)+cn).
FIG. 6 shows current cells (hatched parts) which are turned on when the input data changes as 4, 3, 2, 2, 5, . . . in the case of noise-shaping a non-linearity of 3-bit segment type DA converter using the low-pass noise-shaping element rotation method according to the prior art.
Referring to FIG. 6, when the input signal is "4" at the timing "n", the current cells CS0, CS1, CS2 and CS3 are turned on. Next, when the input signal is "3" at the timing "n+1", the current cells CS4, CS5 and CS6 are turned on. When the input signal is "2" at a timing "n+2", the current cells CS7 and CS0(=mod8 (8)) are turned on. Further, when the input signal is "2" at a timing "n+3", the current cells CS1 (=mod8 (9)) and CS2 (=mod8 (10)) are turned on in a manner similar to that of above. When the current cells which were turned on are thus selected clockwise, the mismatch in the current cells (that is the non-linearity of the DA converter) is subjected to the first-order noise-shaping (for example, See the eleventh to thirteenth non-patent documents) . The inventors of the present invention carried out simulations using a software of MATLAB (registered trademark), and it was confirmed that a power spectrum of the non-linearity of the DA converter was shown in the flat shape in the signal band when the conventional DA converter of segment type was used, however, the non-linearity was first-order-noise-shaped in the case of using the above-mentioned algorithm.
Next, a high-pass element rotation method as disclosed in, for example, the ninth non-patent document, will be described below. FIG. 7A is a block diagram showing a configuration of a DA converter circuit using the high-pass element rotation method according to the prior art. FIG. 7B is an equivalent block diagram of the DA converter circuit of FIG. 7A.
The DA converter circuit shown in FIG. 7A includes a digital high-pass filter TR21 having a transfer function (1/(1+z−1)), a DA converter DA3 having a non-linearity δ(z), and an analog low-pass filter TR22 having a transfer function (1−z−1), which are connected in a form of cascade. The digital high-pass filter TR21 of FIG. 7A includes a subtracter SR21, and a delay circuit DE21 for feeding back an output signal from the subtracter SR21 to the subtracter SU21, as shown in FIG. 7B. The analog low-pass filter TR22 of FIG. 7A includes an adder SM21, and a delay circuit DE22 for delaying an output signal from the DA converter DA3 by a predetermined time length and thereafter outputting a delayed output signal to the adder SM21, as shown in FIG. 7B. A relationship among respective signals D1 to D4 is represented by the following Equations:D2(z)=(1/1+z−1)D1(z)  (11),D4(z)=(1/1+z−1)D3(z)  (12),andD3(z)=D2(z)+δ(z)  (13).
Therefore, the analog output signal D4 (z) is represented by the following Equation:D4(z)=D1(z)+(1+z−1)δ(z).
The non-linearity δ(z) of the DA converter DA3 is subjected to the first-order noise-shaping by the analog low-pass filter TR22 having a transfer function (1+z−1). Further, the following Equations are obtained from the Equations (11), (12) and (13):D2(n+1)=D2(n)−D1(n+1)  (15);D4(n+1)=D3(n+1)+D3(n)  (16);andD3(n)=D2(n)+δ(z)  (17).
If it was possible to replace the multi-bit DA converter on the inside of the high-pass ΔΣ AD modulator by the circuit shown in FIGS. 7A and 7B, the non-linearity of the DA converter could be noise-shaped, however, such a circuit cannot be realized in a manner similar to that of the low-pass ΔΣ AD modulator. Accordingly, the high-pass element rotation algorithm was proposed and can equivalently realize the circuit. It is assumed that the current cells are arranged in the ring shape and the pointer is provided in the DA converter of segment current cell type. An operation of the high-pass element rotation algorithm will be described in detail as follows:
(a) At a timing "2n":
(a1) The input data is D1 (2n)=d2n.
(a2) The number "d2n" of current cells CS (P(2n)), CS (mod8 (P(2n)+1)), CS (mod8 (P(2n)+2)), . . . , CS (mod8 (P(2n)+d2n−1)) are turned on. Concretely speaking, the number "d2n" of current cells are turned on starting from the P(2n)-th current cell and shifting in the clockwise direction.
(a3) The pointer at a timing "2n+1" is set to P(2n+1)=mod8 (P(2n)+d2n−1).
(b) At the timing "2n+1":
(b1) The input data is D1 (2n+1)=d2n+1.
(b2) The number "d2n+1" of current cells CS (P(2n+1)), CS (mod8 (P(2n+1)−1)), CS (mod8 (P(2n+1)−2)), . . . , CS (mod8 (P(2n+1)−d2n+1)) are turned on. Concretely speaking, the number "d2n+1" of current cells are turned on, starting from the P(2n+1)-th current cell and shifting in the counterclockwise direction.
(b3) The pointer P(2n+2) at a timing "(2n+2)" is set as follows:P(2n+2)=mod8 (P(2n+1)−d2n+1+1).
FIG. 8 shows the current cells which are turned on when the input data changes as 4, 3, 2, 6, 5, . . . in the case of noise-shaping the non-linearity of the DA converter of 3-bit segment type using the high-pass noise-shaping element rotation method according to the prior art.
Referring to FIG. 8, when the input data is "4" at the timing "n", the current cells CS0, CS1, CS2 and CS3 are turned on. Next, when the input data is "3" at the timing "n+1", the current cells CS3, CS2" and CS1 are turned on. When the input data is "2" at the timing "n+2", the current cells CS1 and CS2 are turned on. Further, when the input data is "6" at the timing "n+3", the current cells CS2, CS1, CS0, CS7, CS6 and CS5 are turned on in a manner similar to that of above. More concretely, the direction in which the current cells are turned on is alternately changed between the clockwise and counterclockwise directions every time when the sampling timing changes.
As mentioned above, the input and output relationship in the band-pass ΔΣ AD modulator having the configuration of FIGS. 2A and 2B is represented by the Equation (2). It is understood from the Equation (2) that the quantization noise E (z) of the internal AD converter is noise-shaped, however, the non-linearity error δ(z) of the DA converter DA3 is not subjected to the noise shaping and directly outputted, and this leads to that it is difficult to realize the ΔΣ AD converter achieving a higher precision. More concretely, the DA converter of multi-bit type includes the non-linearity resulting from a matching precision generated in the device, which adversely affects the performance of the entire AD converter circuit. In particular, there is caused an even more serious problem when a refining process is adopted in order to downsize and accelerate the circuit. Although the AD converter circuit using the complex band-pass ΔΣ modulator was proposed in the first to fourth patent documents, the proposed AD converter circuit can not solve any mentioned problems.

Complex band-pass ΔΣ AD modulator for use in AD converter circuit

Semiconductor Technology Academic Research Center


An information processing apparatus having a resume function which can maintain the security even when a plurality of users commonly use the apparatus. A work state at a power-off time of the apparatus is preserved together with a work state name including a user""s ID in a different area in a plurality of preservation areas for resume function on a main memory for each user. When a power source is again turned on, data in the preservation area corresponding to the user""s ID is used to reproduce the work state of the user at the power-off time. The work preservation areas can be provided on a file server apparatus in a network not needing battery back-up. When the information processing apparatus is used, a work state at a power-off time can be independently preserved and reproduced for each user.

The present invention relates to an information processing apparatus such as a personal computer, and more particularly, to a resume function for reproducing the work state that existed when a power source was turned off of the processing apparatus, upon turning on the power source again. The present invention also relates to a resume function in an information processing system which has a plurality of information processing apparatuses connected through a network.
Thanks to the advance of small device mounting techniques and development of power consumption reducing techniques in recent years, personal computers, work stations, word processors and so on (hereinafter they are called xe2x80x9cinformation processing apparatuses havexe2x80x9d) become increasingly smaller in size, and even notepad-size products operable with a battery have recently been brought to the market. Such battery driven information processing apparatuses require a user to frequently shut off the power supply either manually or automatically in order to prevent the battery from being consumed in a short time. However, when the power source is to be turned off, the user is required to store user information, for example, a document under processing and so on, in a non-volatile storage unit, and moreover, when the power source is to be turned on again, the user must recall a program and the thus stored user information from the non-volatile storage unit. For this reason, such frequent turning-off of the power source causes a problem that efficient use of the apparatus is less likely for the user.
To attend to this problem, it is now common for a battery driven information processing apparatus be provided with a so-called resume function is to store the contents of a display memory, I/O registers of input/output devices and so on in a main memory, and preserve the contents of the main memory by backing up the same with a battery before turning off the power source such that when the power source is again turned on, the contents of the display memory, the I/O registers of the input/output devices and so on preserved in the main memory are written back to the respective devices, and a state upon turning off the battery is reproduced as if the apparatus had been kept operating. Information processing apparatuses having such a resume function are disclosed, for example, in JP-A-57-17042 and JP-A-2-93814.
As described above, the resume function provides an excellent information processing apparatus which can reproduce a user""s work state upon again turning on the power source and does not cause the degradation of the usability of the apparatus even if the power source is frequently turned off to reduce the consumption of the battery. However, the resume function hitherto provided in information processing apparatuses does not allow the user to perform another operation while preserving a work state. Also, when a plurality of users use a single information processing apparatus in which a user has preserved a work state using the resume function, another user, when turning on the information processing apparatus, will see the preserved work state of the previous user, thereby presenting unfavorable problems regarding security and utility.
Also, since the main memory is backed up by a battery to preserve a work state, the work state can be preserved only for a limited time period according to the capacity of the battery.
Further, the resume function hitherto provided in information processing apparatuses allows the user to reproduce a previous work state only on the same information processing apparatus in which the user interrupted a work and preserved the corresponding work state, thereby preventing the user from operating the same work on different apparatus at various locations.
The conventional resume function provided in information processing apparatuses further implies a problem that a connection state to a network cannot be correctly reproduced.
The conventional resume function provided in information processing apparatus further presents a problem that a message such as electronic mail transmitted through a network cannot be received during an automatic power-off state for reducing power consumption.
It is a first object of the present invention to provide an information processing apparatus which is capable of preserving and reproducing a plurality of work states.
It is a second object of the present invention to provide an information processing apparatus which is capable of preserving a plurality of work states without backing up a memory with a battery.
It is a third object of the present invention to provide an information processing system which is capable of reproducing a work state on a different information processing apparatus from that in which a user interrupted work and preserved the corresponding work state.
It is a fourth object of the present invention to provide an information processing system which is capable of preserving and reproducing a work state on a first information processing apparatus operated by a user using a file in a different information processing apparatus through a network.
It is a fifth object of the present invention to provide an information processing apparatus having a resume function which is capable of correctly reproducing a work state upon again turning on the power source even if the information processing apparatus is turned off while connected to another information processing apparatus on a network.
It is a sixth object of the present invention to provide an information processing apparatus which is capable of displaying a message sent from another information processing apparatus connected thereto through a network, even if the power source of the information processing apparatus is turned off.
The first object is achieved by providing plural sets of work state preservation areas for storing information in a storage unit, and reproducing a work state of the information processing apparatus based on the information in one set of the work state preservation areas specified by the operator from among the plural sets. Since work states at a plurality of times are respectively preserved in the plural sets of the work state preservation areas, respective work states of a plurality of operators or work states of a single operator at a plurality of times are preserved and reproduced.
The second object is achieved by preserving work states in a magnetic disk drive or the like which need not be backed up by a battery. Since the work states are preserved in a magnetic disk drive or the like which need not be backed up by a battery, a main memory does not require battery back-up so that no electric power is consumed during power-off state of the information processing apparatus.
The third object is achieved by providing plural sets of work state preservation areas in a storage unit of a first information processing apparatus; accessing the storage unit of the first information processing apparatus from a second information processing apparatus through a network; and executing at least processing for storing information on work states at particular times in work state preservation areas and processing for reproducing a work state based on information stored in one set of the work state preservation areas specified by the operator from among the plural sets. Since a plurality of information processing apparatuses are connected to each other through a network, and the work state preservation areas are collectively arranged in a single information processing apparatus, the other information processing apparatuses do not require battery back-up of main memories thereof or installation of a magnetic disk drive or the like. Also, the work state can be reproduced by an information processing apparatus other than that on which the work state was preserved.
The fourth object is achieved by executing processing for storing a used state of a file in use through the network when a work state is preserved and processing for reproducing the used state of the file when the work state is reproduced. Even if another information processing apparatus in which a file being used through the network is stored sets this file in an unused state after preserving a work state of the file, since the used state of the file has been stored upon preserving the work state, the used state of the file can be reproduced on the basis of the stored contents upon reproducing the work state.
The fifth object is achieved by constantly supplying a network controller with electric power even after preserving a work state, temporarily reproducing the work state when the network controller receives a frame from the network in this state, and performing the necessary processing to maintain a connection state with another information processing apparatus. Since the network controller or a timer is kept supplied with electric power even after preserving the work state, the processing necessary to maintain the connection state with other information processing apparatuses can be continuously performed, thereby making it possible to correctly reproduce the work state when the power source is again turned on.
The fifth object is also achieved by constantly supplying the timer with electric power even after preserving a work state, temporarily reproducing the work state when the timer detects the lapse of a specified time in that state, and performing processing necessary to maintain a connection state with another information processing apparatus. Since the network controller or the timer is kept supplied with electric power even after preserving the work state, the processing necessary to maintain the connection state with the other information processing apparatus can be continuously performed, thereby making it possible to correctly reproduce the work state when the power source is again turned on.
The sixth object is achieved by constantly supplying the network controller with electric power even after preserving a work state, reproducing the work state when the network controller receives a frame from the network in that state, and displaying a message to be displayed to the user, if included in the frame. Since the network controller is constantly supplied with electric power even after preserving a work state, a frame including a message can be received and the message can be displayed to the user.
Therefore, according to the present invention, since a plurality of work states can be preserved and reproduced independently of each other, the user is allowed to perform different work while preserving a particular work state. Since work states of a plurality of users can be preserved and reproduced independently of each other, even if a plurality of users operate a single information processing apparatus to use the resume function, security and utility are not damaged. Also, a work state can be preserved without using a main memory requiring back-up by a battery, which leads to realizing the resume function on an information processing apparatus or the like which does not have a battery back-up function. Since a work state on an information processing apparatus may be preserved in a different information processing apparatus connected thereto through a network, the work state may be reproduced on an information processing apparatus different from that on which the user interrupted a work and preserved the work state, thereby providing an information processing apparatus which allows the user to operate the same work at various locations. Even if an information processing apparatus is logically connected with another one through a network, a work state can be correctly preserved and reproduced, which enables the utilization of excellent features provided by the resume function, such as improvement of user-friendly operation and reduction in power consumption, in an information processing apparatus connected to a network. Further, even when an information processing apparatus is temporarily turned off while connected to a network for the purpose of reduction in power consumption, it is automatically turned on again to display a message, if arriving at the user, whereby the resume function can be utilized without damaging the serviceability provided by an information processing apparatus connected to a network such as for electronic mail and message transmission function and so on.

Information processing apparatus with resume function and information processing system


The present disclosure relates to a method for upgrading lignocellulosic material carbohydrates and/or carbohydrate derivatives by dimerisation and/or oligomerisation using specific catalysts and to the use of the upgraded products.

U.S. Pat. No. 8,629,310 B2 discloses upgrading of lignocellulosic oxygenate base material, such as γ-valerolactone (GVL), comprising the steps of hydrogenating the oxygenate base material, followed by condensing the hydrogenated base material.
WO 2015/144856 A1 discloses condensation of levulinic acid (LA) in the presence of a solid acid catalyst system.
EP 3050868 A1 discloses condensation of levulinic acid (LA) in the presence of water and a base catalyst which may comprise sodium hydroxide or potassium hydroxide.

Upgrading lignocellulosic or carbohydrate material


One aspect of the invention relates to a video distribution system for live distributing a video containing a virtual space and an animation of a character object generated based on a motion of a distributor user. The video distribution system determines, when receiving from a viewer user watching the video a participation request to request participation in the video, which one of first and second groups the viewer user belongs to. If the viewer user is determined to belong to the first group, the video distribution system arranges a specific avatar of the viewer user in a first region within the virtual space. If the viewer user is determined to belong to the second group, the video distribution system arranges the specific avatar in a second region within the virtual space as long as a condition for participation is satisfied.

Video distribution systems have been known that generate an animation of a character object based on motion of a distributor user and live distribute a video including the animation of the character object. Such video distribution systems are disclosed, for example, in Japanese Patent Application Publication No. 2015-184689 (Patent Literature 1) and "Hasegawa Yusuke, Beginning of New Era of Virtual Idle, PROJECT MariA, CG WORLD, Japan, Bone Digital Co., Ltd., Nov. 10, 2017, Vol. 231, pp. 74-79."
As disclosed in Japanese Patent Application Publication No. 2012-120098 (Patent Literature 2), another video distribution system is also known that, in response to a request from a viewer user watching a video, can cause an image containing an avatar of the viewer user to be displayed in a background region of the video being distributed. The viewer user is able to post his/her comment via the avatar on the video. In this manner, the viewer user can use his/her avatar to participate in the video being distributed.
Japanese Patent Application Publication No. 2017-187995 (Patent Literature 3) discloses a social media system that enables a plurality of users to make voice communication using avatar images staying in a virtual room. The social media system disclosed in this Publication imposes an upper limit on the number of avatars that are allowed to stay in each room. When an entry request is made for a certain room, the entry request is granted if the number of avatars that are already in the room does not exceed the upper limit imposed on the room. If the entry request for the room is granted, a new avatar is permitted to enter the room.

Video distribution system for live distributing video containing animation of character object generated based on motion of distributor user, video distribution method, and video distribution program


A media transport system provides full vacuum under media as the media traverses an entire print path of an ink jet printer while simultaneously providing for a no-vacuum inter-copy gap that moves along with the media past print heads of the ink jet printer. This is accomplished with a dual vacuum inner/outer vacuum drum system that includes a first drum that has a matrix of holes that allows for full coverage of vacuum with a second underlying drum that is shifted to align a second set of holes to match the sheet pitch. By shifting the second drum in relation to the first drum, a combination set of holes is aligned to provide full vacuum across the media while a column of holes is blocked to provide a non-vacuum inter-copy gap.

Cross reference is hereby made to copending and commonly assigned U.S. patent application Ser. No. 15/070,036 to Douglas K. Herrmann, filed Mar. 15, 2016 and entitled DUAL VACUUM BELT SYSTEM WITH ADJUSTABLE INTER-COPY GAP.
1. Field of the Disclosure
This disclosure relates generally to printing or recording devices that deposit ink on a recording media, such as paper. More specifically, the invention relates to such devices wherein a rotating cylindrical drum moves a sheet of paper beneath an ink jet print head. In particular, the invention relates to the aspects of rotation of the drum with recording media attached thereto by vacuum air flow while simultaneously controlling vacuum air flow through inter-copy gaps.
2. Description of Related Art
In ink jet printers where it is necessary for a vacuum drum transport to transport media under ink depositing print heads, the area where no sheet is present at the inter-copy gap creates unwanted air flow past the print heads through a gap between the print heads and media attached to the vacuum drum. This air flow creates turbulence around ink jets of the print heads and ink droplets from the ink jets are deflected from their intended trajectory. This leads to degraded print accuracy and a distorted image.
A problem is created with vacuum drum systems in that the technology used to create the vacuum under media also creates a vacuum at the inter-copy gap. With no media to block the air flow caused by the vacuum, air is pulled past ink jet heads and the air velocity causes dispersion of the jetted ink drops between the print heads and the media. This sudden change in air velocity under the print heads also induces turbulent air flow at the jetting plate surface. The turbulent air generates eddy currents across the print head face plate. These currents dry the ink meniscus in each jetting port resulting in increased numbers of misdirected and missing jets that develop during a print run. Ideally, the vacuum should be present only under the media and not at the inter-copy gap. The media, however, needs to have vacuum up to the edges of each sheet so a change in a permanent underlying plenum would create a no vacuum area under the print head and lead to the media separating from the drum and creating an uneven print surface. Hence, the need for an improvement specifically targeting those ink jet print systems with vacuum drum transport through the ink jetting zone.
Vacuum drum transports are old as evidenced by U.S. Pat. No. 8,177,231 which shows the use of a vacuum drum to move a sheet through an image forming device. The drum has vacuum, however, the system does not make any accommodations to remove air flow at the inter-copy gap or for different inter-copy gap areas of the sheet. U.S. Pat. No. 4,312,007 discloses an ink jet printer that employs a rotating cylinder to move a sheet of paper beneath an electrically driven and piezoelectrically actuated ink ejection mechanism. In U.S. Pat. No. 4,574,291 a synchronizer is disclosed for generating a pulsed trigger signal synchronized with the angular position of a rotating object, such as, a drum in an ink jet copy machine. A drive system for an ink jet printer that employs a rotating drum is disclosed in U.S. Pat. No. 4,739,346.

Ink jet coaxial drum system with inter-copy gap tracking


A chair having a backrest with an adjustable contour includes a slidable lumbar member for selectively changing the location of the contour in correspondence with the anatomy of the chair occupant. The lumbar member is displaceable within a travel slot. A handlebar member is operable by a seated chair occupant for releasably locking the lumbar member at selected heighth positions.

1. Field of the Invention
This invention relates generally to a chair having a backrest with a changeable support surface and especially to adjustable contour backrest.
In particular, this invention concerns a backrest for providing support to the lower back region of a chair occupant.
2. Background Art
Current seating designs for office furniture, such as task chairs, commonly incorporate multiple positional features for user comfort. With regard to backrest designs, various concepts have been utilized to support the natural curve of the spine and to relieve stress on the lumbar vertebrae.
Typical of such designs are chairs having an inflatable air lumbar support mechanism for increasing and/or decreasing the convexity of a backrest as illustrated in U.S. Pat. No. 5,660,438. A chair having a mechanically operable camming device for imparting a curvature to a backrest is disclosed in U.S. Pat. No. 3,948,558. The backrest of the chair shown in U.S. Pat. No. 4,601,514 relies upon a spring member for varying the curvature.
A limitation of the above-described backrests is that each is primarily concerned with curvature variations in the backrest without compensation for the differences in location of the lumbar region of respective chair occupants.
The backrest disclosed in U.S. Pat. No. 3,642,319 utilizes a shaft having an eccentric rotary axis for modifying the convexity of and for positionally relocating the contour. A disadvantage of this mechanism is that it cannot be readily operated by a chair occupant while seated in the chair.
Additional backrest designs for positionally adjusting a lumbar support are respectively shown in U.S. Pat. Nos. 5,217,278 and 4,156,544. These backrest devices employ complex control mechanisms and are intended for use in vehicle seats rather than for office furniture.
The backrest of the present invention in contrast to the previously described devices provides a relatively simple construction and has a plurality of contour elevational settings.

Chair having a backrest with an adjustable contour


There is provided a novel silane compound, di-sec-butoxy-n-propyl methoxysilane. The aforesaid silane compound is prepared by reacting n-propyl trihalosilane with sec-butanol and then reacting a resultant reaction product with methanol.

It is known that a polymer with high stereoregularity can be prepared by the use of alkoxy silanes as a catalytic component in the polymerization of propylene. However, it was impossible to sufficiently attain both high polymerization activity and high stereoregularity with known alkoxy silanes as a catalytic component in the polymerization of propylene.
Further, silane compounds are expected to be useful as silane coupling agents and resin modifiers. Accordingly, new silane compounds are awaited.

Silane compound and process for the preparation thereof


An optical distributor includes an optical-signal input port, a light receiving device, a light emitting device, a light splitter, and optical signal output ports. The light receiving device converts an optical light signal input to the optical-signal input port into an electric signal. The light emitting device converts the electric signal into an optical signal. The optical splitter 14 splits the converted optical signal into two optical signals. The optical-signal output ports output the split optical signals. The light receiving device includes a light receiving element, a pre-amplifier, and a limiting amplifier. The light emitting device includes a light-source drive element and a light emitting element.

1. Field of the Invention
The present invention relates to an optical distributor for splitting an input optical signal and outputting the split optical signals, and an optical distributing system using the optical distributor.
2. Description of the Related Art
In an optical network system for transmitting an optical signal to a plurality of devices connected to optical fibers, optical splitters (optical distributors) each for splitting an optical signal and transmitting the split optical signals to the devices are disposed at respective positions. The optical signal is input to desired devices by way of the optical splitters. For the optical splitters of this type, the following optical splitters have been known.
<Literature 1>
F. Auracher and H.-H. Witte, "Optimized layout for a data bus system based on a new planar access coupler", APPLIED OPTICS, Vol. 16, Nos. 12, 3140–3142, December 1977
The literature 1 discloses a coupler for coupling and/or splitting an optical signal with respect to a trunk fiber (FIG. 1 of the literature 1). A connecting portion of the main fiber is shifted, and a splitting fiber is connected to the connecting portion. Thereby, the coupler is implemented.
<Literature 2>
Marshall C. Hudson and Frank L. Thiel, "The Star Coupler: A Unique Interconnection Component for Multimode Optical Waveguide Communications Systems", APPLIED OPTICS, Vol. 13, No. 11, 2540–2545, November 1974
The literature 2 discloses an optical coupler for coupling and/or splitting an optical signal with respect to a main fiber (FIG. 1 of the literature 2). In the literature 2, a multi-to-multi optical coupler such as a star coupler is used. An optical coupler of a reflection type may be used as another form of the optical coupler (FIG. 2 of the literature 2).
An optical data way terminal device is disclosed in JP-A-62-014538. In the terminal device, an optical signal from a single optical fiber transmission path, which is arranged to have a looped shape or a linear shape, is split at a splitting portion having a variable splitting ratio.
An optical bus system including an optical fiber line and an optical coupler is disclosed in JP-A-63-001223. A splitting ratio of the optical fiber is gradually increased from a start end of the optical fiber line so that the split destinations receive light beams having light levels substantially equal to each other.
A bus system optical network system is disclosed in JP-A-1-222533. The network system includes two optical fiber cables for trunk transmission line, which are interconnected at one ends to each other, and an optical two-splitting coupler for connecting an output signal from a communication control unit and an input signal to the communication control device to the two optical fiber cables, respectively.
An optical splitter and an optical network are disclosed in JP-A-2001-166177. The optical splitter includes a light-transmission medium having first and second end faces, and a light diffusion portion provided at the first end face. The optical splitter changes a splitting ratio of an optical signal at an output portion in a manner that a light intensity distribution at an end face of a light emitting side of the light-transmission medium is changed by varying any of a distance between the first and second end faces, light incident position, and light diffusion angle.
Meanwhile, in a system for transmitting an optical signal to a plurality of devices connected to an optical fiber, it is sometimes desired to distribute optical signals of desired levels to the devices. An example of such is a case where video information is transmitted from a video output device to a receiver in a room at each floor in a building such as a hotel. In a possible way to distribute video information from the video output device to each receiver, an optical transmitting unit of the video output device is connected to optical receiving units of the receivers by optical fibers, respectively. In this case, installed optical fibers equal in number to the receivers are required, resulting in increase of wiring cost. A possible way to cope therewith is that an optical coupler are installed at each floor, a light signal from the optical transmitting unit is sent to the optical couplers, and in turn the couplers each splits the optical signal and sends the split ones to the receivers. However, when the optical couplers split the optical signal, a signal level of the optical signal drops depending on the splitting number. Accordingly, it is impossible to send the optical signal of sufficient level to the light receiving unit of each receiver. This problem would arise not only in the above case, but also in a system for transmitting an optical signal to another device by way of the optical fiber.

Optical distributor and optical distributing system


Systems and methods that use a CW Doppler radar to monitor paint particle velocities as they are sprayed from a paint gun to optimize the application of sprayed paint onto the object, and provide a closed loop spray painting system and paint spraying method that controls the application of paint in real time using data generated by the radar. The Doppler radar and a signal analyzer are used to analyze the Doppler return signals and display data indicative of the velocity of the paint particles. The data may be used by an operator to manually adjust the paint spray system. In addition, the spectrum analyzer may be used to generate and couple control signals to the paint spray system to provide for closed loop feedback control of thereof. One method comprises the following steps. Spraying paint particles toward an object that is to be painted using a paint spray gun. Radiating Doppler radar signals at the paint particles that are moving toward the object. Receiving backscattered Doppler shifted radar returns from the moving paint particles. Processing the received backscattered Doppler shifted radar returns to produce data indicative of the velocity of the paint particles. Displaying the data indicative of the velocity of the paint particles. This method unobtrusively and remotely measures paint particle velocity and velocity distribution. By additionally generating control signals in response to the data, the paint spray system is controlled.

The present invention relates generally to monitoring of spray painting systems and methods, and more particularly, to a spray paint monitoring system and method using Doppler radar.
Currently, automotive spray paint operations are required by emission laws and regulations to reduce the amount of volatile organic compounds that are emitted into the atmosphere. Conventional solvent borne spray paint processes presently used produce volatile organic compounds emissions of 4.0 lbs/gal, which just barely meets the federal and state (many but not all) pollution restrictions. It is anticipated that the restrictions will become much more stringent in the near future and that unless cleaner spray paint technology is developed expensive incineration facilities or other costly pollution controlling equipment will be required to control the pollution from paint operations.
A new spray painting process currently under development using super-critical carbon dioxide which is expected to lower the volatile organic compound emissions to 2.0 lbs/gal and which is expected meet the tighter requirements without requiring installation of pollution control equipment. However, to control the spraying process, a paint spray monitor is required. Specifically, in order to continually monitor and optimize the application of spray paint, it is necessary to provide for real time monitoring of the particle gun used in the spray painting system.
One conventional sensor that has been used in spray paint monitoring is a laser system that monitors the speed and size of individual paint particles. The laser approach uses two parallel helium-neon laser beams which were crossed as a result of being passed through a convex lens which had a focal length of 5 cm. An fringe pattern formed at the point where the laser beams intersected and the fringe spacing was approximately 5 .mu.m. The waist of the beam at the focal point was approximately 70 .mu.m, which was suitable for measuring particles in the 50-70 .mu.m range. As a paint particle boundary crossed the interference fringe pattern it produced a temporal intensity fluctuation which was governed by the velocity of the particle in order to measure such small particles a short working distance was therefore required and consequently the laser source and the light scattering detector needed to be inside the spray paint profile.
The laser approach was successful in measuring spray paint particle velocities. However, due to the small beam width many measurements throughout the paint spray profile were needed in order to determine the distribution. To test the equipment, a series of experiments were run to determine the particle velocities at a distance of approximately 12 in from the spray gun nozzle 32 and at 5 different points through the spray paint particle distribution (center, and 2 and 3 inches above and below center, relative to the gun nozzle position). Particle velocities were measured as a function of changing the pre-orifice and orifice size in the paint gun nozzle 32 as well as changes in the CO.sub.2 pressure applied to the gun. A trend to higher maximum mean particle velocity was observed when increasing the orifice size while maintaining the same pre-orifice size. The range of mean velocities was observed to change between 3 and 14 m/s over the course of all combinations of pre-orifice and orifice sizes used. It was also determined that for all combinations of pre-orifice and orifice sizes, a reduction in CO.sub.2 pressure approximately 27% from 1500 psi to 1100 psi resulted in approximately 15% reduction in the maximum mean paint particle velocity. In these cases velocity did seem to be a good indicator of changing paint gun parameters.
The disadvantage of the laser scattering approach is that it requires a short working distance (approximately 5 cm) which makes the measurement intrusive to the spray paint profile. Since the laser beam sampling volume is very small (approximately 10-13 m.sup.3) many measurements through the paint spray profile are necessary in order to determine the complete velocity distribution profile. This makes the measurements both time consuming and unsuitable for real time feedback monitoring. Consequently, the laser system is obtrusive (too close to the paint spray gun), too restricted in its monitoring area, and much too slow to accumulate gun data for real time process control.
Therefore, it would be desirable to have monitoring equipment and a closed loop control system and processing methods to improve spray paint quality control and provide cost savings resulting from increased transfer efficiency as a consequence of a higher charge transfer efficiency system on the paint gun. It would also be desirable to have monitoring equipment and a closed loop control system and processing methods that provide for a reduction in the emission of volatile organic compounds caused by spray paint operations.
Therefore, it is an objective of the present invention to provide for a spray paint monitoring system that may be employed with super-critical carbon dioxide spray painting systems. It is a further objective of the present invention to provide for a method that provides for real time monitoring of the performance of a particle gun used in a spray paint system by monitoring the paint spray produced thereby to optimize the application of spray paint. It is a further objective of the present invention to provide a system and method for closed loop control of a pressurized painting system.

Spray paint monitoring and control using doppler radar techniques


A new type of static RAM cell is disclosed that is based on a gated diode and its voltage amplification characteristic. The cell combines the advantages of a static RAM, in which data refresh is not needed, and those of gated diode cells, which are scalable to low voltages, have high signal to noise ratio, high signal margin, and tolerance to process variations, to form a single high performance static memory cell. This new cell has independent read and write paths, which allow for separate optimization of the read (R) and write (W) events, and enable dual-port R/W operation. Furthermore, storage node disturbance during the read and write operations are eliminated, which greatly improves cell stability and scalability for future technologies.

The small signal amplification characteristics of the gated diode device structure were originally used to create signal amplifiers and dynamic memory cells, including one transistor one diode (1T1D), two transistor one diode (2T1D), and three transistor one diode (3T1D) memory cells. U.S. patent application Ser. No. 10/735,061, entitled "Gated Diode Memory Cells," incorporated by reference herein, describes 1T1D and 2T1D gated diode memory cells, a new type of dynamic memory cell with internal voltage amplification based on gated diode circuits and structures. U.S. patent application Ser. No. 10/751,714, entitled "Amplifiers Using Gated Diodes," incorporated by reference herein, describes gated diode circuits for signal amplification that are suitable for amplifying small amplitude signals. U.S. patent application Ser. No. 10/751,713, entitled "3T1D Memory Cells Using Gated Diodes and Methods of Use Thereof," incorporated by reference herein, describes dynamic memory cells designed from gated diode circuits.
The gated diode memory cells in the above-identified patent applications are all dynamic designs in that data is retained in the storage node in the form of a unidirectional, single ended voltage and (capacitive) charge. The amount of charge stored eventually decays to a low level due to intrinsic leakage mechanisms, such as transistor off-state current, gate tunneling current, and junction leakage current. The low level charge is insufficient to maintain storage of the data. A "refresh" event is therefore needed (after a certain period of time) to bring the voltage or charge level back to its appropriate level in order to retain the stored data.
These previously proposed memory cells have a number of desirable characteristics, including low voltage operation, high signal to noise ratio, high signal margin, high tolerance to process and threshold voltage (Vt) variations, non-destructive read operation, fast read/write time, and short random access cycle. This allows for the continued scaling of memory for future technologies with lower supply voltages. Due to the signal amplification of the cell voltage of the gated diode memory cells, the memory cells can have a much higher signal margin than existing static random access memory (SRAM), dynamic random access memory (DRAM), and dynamic gain cells.
SRAM has traditionally been used for high performance applications, such as embedded caches in high performance processors, due to its fast read/write times, non-destructive read, short random access cycle, and static data storage (no refresh needed). As technologies are scaled to lower voltages, the static noise margin in the cross-coupled latch in the SRAM cell degrades (i.e., the signal margin or voltage difference between a 0- or 1-voltage and the flip point voltage becomes very small), especially during a read event, in which the internal storage node of the cell is perturbed. With the growing influence of process-induced variations, threshold voltage fluctuations further degrade the SRAM cell stability.
A need therefore exists for a memory device that does not require data refresh, but has the scalability to low voltages, high signal to noise ratio, high signal margin, and tolerance to process variations characteristic of gated diode dynamic memory cells.

Static random access memory utilizing gated diode technology

International Business Machines Corporation


A flex circuit, which is fabricated from metallization on thin film, is mounted between two opposite sides of frame to form an electronic card sized to fit as a replacement for a rigid epoxy glass card in a card carrier having a backplane. Appropriate placement of electrical components on the flex circuit and using a flex circuit longer than the spacing between the opposite sides of the frame to which the flex circuit is mounted, allows the use of taller parts on adjacent cards in the card carrier, since the flex circuit can be conformed to eliminate obstructions caused by insufficient spacing between cards.

The present invention relates to electronic packaging and more specifically to an electronic card for use in card-on-board packaging.
Electronic card assemblies are typically fabricated from alternating layers of copper and epoxy glass, laminated together to form a sandwich of conductive and insulating materials. The resulting cards are very rigid which is desirable in many applications. The cards are mounted, typically with a fixed spacing between adjacent cards, through connectors to a planar board. Alternatively, the printed circuit card can be mounted between two boards with zero insertion force connectors serving the dual function of channel guides and electrical connectors. As used herein the term planar board refers to a panel made of insulating material that has circuits, electronic components, and connectors on the panel. A board, also referred to as backplane, is a panel which has connectors but does not have electronic components.
Difficulties can arise when a card needs to be upgraded for reasons of cost reduction, reliability improvements or adding additional function, since the card design is limited by the original spacing between adjacent cards. Most components, except for long lead items such as capacitors which can be bent to avoid adjacent obstructions, are rigidly mounted on circuit cards and do not allow positional adjustment to avoid interference with adjacent cards. If a heat sink or additional memory were required on a replacement card it might not fit in the spacing available, necessitating board or planar board redesign.
It is an object of the present invention to provide electronic card assemblies which eliminate many space restrictions imposed when modifying existing card-on-board designs.

International Business Machines Corporation


A composite wood panel having a first and a second longitudinal edge comprising an essentially parallel first surface and second surface, a core, a spacer integrally formed in or attached in the core on at least the longitudinal edges wherein the spacer extends from an edge a pre-determined distance whereby upon placing one panel adjacent to a second panel a spacer of the first panel will abut a spacer of or an edge of a second panel thereby forming at least a first aperture between the adjacent panels wherein an aperture is located between adjacent edges of the panels. A spacer can push into its panel upon linear expansion of a panel. The spacer can be, e.g., a tongue, edge profile, or separate spacing material. Methods for making and using panels are disclosed.

Construction materials must be installed correctly to insure the best performance. Wood-based panel products undergo dimensional changes when exposed to elevated moisture conditions. Most panels are put into service conditions at less than equilibrium moisture content. Consequently, there can be an uptake in moisture from the surrounding environment and "growth" in panel dimensions. The term used to describe this phenomenon is linear expansion (LE), whereby physical dimensions (length and width) will grow with moisture uptake.
There are a number of consequences to linear expansion when panels 1 are fitted tightly together at joints 3 prior to expansion (see, e.g., prior art FIGS. 1-3):
1) Panels 1 will buckle 4 somewhere along an unsupported span (FIG. 1).
2) Excessive deflection 5 may result (FIG. 2) in putting surfaces out of level.
3) The upper 8 and lower 9 surfaces (top and bottom faces) of the panel 1 will flare out 7 at the panel-to-panel joint 3 in a release of forces (FIG. 3). This flaring 7 of panel edges at joints 3 is sometimes attributed wholly to edges well, where the uptake of moisture causes expansion in the vertical direction, but is more likely to be a result of a combination of expansion in both directions. Flare-out 7 occurring prior to finishing the structure can necessitate sanding, adding additional cost to construction. Occurrence of edge flaring 7 after finishing can cause gypsum board (drywall) to crack, exterior siding to bulge out, floors or shingles to bulge out, etc.4) Expansion of panels may push walls out of plumb; and5) expansion of a wall system can push floors, ceilings, and roofs off level. In current panel construction, if enough LE occurs and the panel edges come into contact with each other, the compressive force on the surface flakes causes them to raise or "tent" up, causing ridging in the panel joint. This can cause shingles to telegraph the ridging, and can be a cause for customer complaint.
Given that the above expansion characteristics and consequent impacts are well known, most manufacturers, their third-party certification agencies, and governing standards prescribe a minimum gap at panel joints to allow for linear expansion. The amount of gap recommended is dependent on the inherent linear expansion character of the substrate (i.e., some panels will expand more than others).
The American Engineered Wood Association (APA) defines the panel spacing as the gap left between installed structural panels in floor, wall, or roof deck construction (http://wooduniversity.org/glossary.cfm, APA, 2006) and indicates that spacing distance should be enough to allow for any possible expansion due to changing moisture absorption levels to help prevent buckling and warping.
In general, when wood-based sheathing panels are installed, a ⅛″ space between adjacent panel edges is recommended. Common techniques for spacing panels are simply to measure the gaps formed between deck boards as they are installed or to drive 8d or 10d nails into joints next to an installed deck board and place the next deck board against the nails. Previous methods for spacing include:
1) 8d or 10d box nails for gauging ⅛″ spacing between panels or other spacers;
2) H-clip with spacing distance between adjacent panels (mechanical attachments); and
3) Panel edge profiling using a tongue and groove (T&G). A minimum ⅛″ gap between square edged panels is recommended when the panels are applied to framing members. Often, the framers or roofers are not aware of the recommended ⅛″ spacing for structural wall panels, and certainly, this is not common practice in the field. Some framers even believe that leaving the recommended space is a code violation. It is believed that excessive education and training are required regarding the need for ⅛″ spacing if not using existing mechanical spacers such as H-clips or nails.
Most warranty claims and problems of the above nature presented to panel manufacturers arise from improper installation—the panels were not gapped as prescribed. Whether due to inexperienced installers, insufficient gapping from imprecise measurement tools, or time constraints in building schedules, proper gapping is not being done on all product installations.
Thus, problems associated with wood-based panels being installed without proper spacing has persisted for many years without solution. Consequently, a self spacing panel will be highly desirable for saving installation time and increasing value since the need for a separately installed spacer can be eliminated in the processes.


A lens barrel includes an imaging optical system including a plurality of lens groups located on an optical axis; an insertable/rotatable optical element which produces a specific photographic effect when rotated on the optical axis; and a drive mechanism including a motor which moves the insertable/rotatable optical element between an inserted position, in which the insertable/rotatable optical element is positioned on the optical axis, and a removed position, in which the insertable/rotatable optical element is removed from the optical axis by forward and reverse rotations of the motor, respectively. The drive mechanism rotates the insertable/rotatable optical element on the optical axis by the forward rotation of the motor when the insertable/rotatable optical element is in the inserted position.

1. Field of the Invention
The present invention relates to a lens barrel, more specifically relates to a lens barrel incorporating at least one rotatable optical element that produces a specific photographic effect when rotated on a photographing optical axis.
2. Description of the Related Art
In a lens barrel which incorporates an optical element (e.g., an optical filter or a wide-converter lens) that produces a predetermined photographic effect when inserted into an optical path on a photographing optical axis, it is necessary to remove such an optical element from a position on the photographing optical axis when the optical element is not used. Among such kind of optical elements, in a particular type of optical element which functions when driven to rotate such as a polarizing filter, the optical element needs to be driven not only to be inserted into and removed from an optical path on the photographing optical axis but also to rotate in an inserted state of the optical element, which may complicate the drive mechanism for the optical element.

Lens barrel incorporating a rotatable optical element


A zoned lens comprises at least two adjacent zones (16) formed such that the differences between the optical path lengths between an object point and a pixel of light beams extending through these two adjacent zones (16) of the lens (15) are at least equal to half the coherence length of the light used, preferably at least equal to the coherence length of the light used.

Lenses are in this case generally understood to be both refractive lenses and diffractive lenses (for example, Fresnel zone plates). A diaphragm provided with a small hole can also be provided with effective powers (effective refractive powers), as described with reference to the drawings. Optical elements with a zero nominal power but with a limited aperture such as, for example, circular or annular plates with parallel front and rear surfaces can therefore also be understood here as "lenses".
Different zones of a lens are represented by areas of a lens which can be differentiated by physical properties, wherein between the zones the physical properties alter very rapidly or abruptly over a relatively small area. In particular, step-like sudden changes in the thickness of the lens material being used, for example, steps on the front or rear surface of the lens, delimit different zones of a lens. The use of different lens materials in different areas of the lens also results in a zoned lens in the present sense. The geometrical arrangement of the different zones can be configured in many different ways. For example, a central circular zone can be provided, to which outer concentric annular zones are adjacent. The surface areas of the different zones can be the same or different.

Bifocon Optics Forschungs-Und Entwicklungsgmbh


A signalling light for mounting on a back shelf of a motor vehicle, and for being covered by a cap or the like, the light comprising a box that is open towards the back window of the vehicle and that contains a filament bulb that extends from one side of said box into said box, the box being closed adjacent to the back window of the vehicle by a closure glass. According to the invention said box includes a removable portion having a cross-section that is substantially U-shaped and that forms a heat screen between the filament bulb and the cap, said removable portion constituting an access hatch giving access to the bulb. The light is suitable for mounting on the back shelf of a motor vehicle.

At present, there is known in the prior art, a signalling light, in particular stoplight, that is mounted on a back shelf of a motor vehicle and that comprises a housing containing filament bulb. The housing is closed adjacent to a back window by a translucent glass through which the signalling light beam is emitted, and it is covered by an outer cap that extends around the box between the back shelf and the back window. The light and the outer cap are fixed to the back shelf of the vehicle.
The major drawback of such a signalling light lies in the fact that it is necessary to dismantle the light completely in order to change the bulb. It is necessary to begin by removing the outer cap and then to dismount the box and the closure glass in order to gain access to the bulb which is fixed on an inside wall of said box.

Signalling light mounted on a back shelf of a motor vehicle


The present invention relates to a multiplexing system comprising a set of transcoders (TC[1] to TC[n]), a controller (CONT) and a multiplexer (MUX). The set of transcoders comprises n transcoders, each transcoder (TC[i]) allowing an input compressed data signal (ICS[i]) encoded at an input bit rate (Rin[i]) to be converted into an output compressed data signal (OCS[i]) encoded at an output bit rate (Rout[i]). The controller (CONT) receives from each transcoder parametric information on the regulation process and the video coding complexity and subsequently computes the bit rate allocated (Rout[i]) to each transcoder (TC[i]) according to a total bit rate capacity available at the output of the multiplexer. The controller receives also parametric information derived from the input compressed data signal (ICS[i]), this information being used to improve the bit rate allocation strategy. Finally, the multiplexer (MUX) provides a multiplexed data signal (MS) by multiplexing of the output compressed data signals (OCS[1] to OCS[n]).

The international patent application published under number WO 95/29559 describes a multiplexing system for controlling plural channel processors. The multiplexing system is described with reference to FIG. 1 and includes:                a multiplexer (MUX) for providing a multiplexed signal (MS),        plural channel processors (CP[1] to CP[n]), each channel processor (CP[i]) having a control input, a data input for receiving an input signal (IS [i]), a complexity output for supplying a complexity signal representing the complexity of an associated input signal, and a data output for supplying an output data signal (OS[i]) to an associated input of the multiplexer, and        a bit rate allocator (CONT) responsive to the complexity signals, for supplying bit rate control signals to the associated control inputs of the channel processors as a function of the complexity signals, in such a manner that a bit rate (Rout[i]) of an output data signal (OS[i]) from a channel processor (CP[i]) is a function of the complexity of an associated input data signal and of the combination of the input data signals.
In such a multiplexing system, the bit rate (Rout[i]) of an output data signal (OS[i]) from a channel processor (CP[i]) is equal to:
      Rout              [      i      ]        =                    X                          [          i          ]                                      ∑                      j            =            1                    n                                  X                                [            j            ]                                    Rtot  where                i is the number of the channel processor,        X[i] is the complexity of the preceding group of pictures (hereinafter referred to as GOP) on a sliding window basis, i.e. the sum, for all the pictures of that GOP, of the product of the average quantization scale Qpic for a picture and the number of bits Tpic used to encode that picture:
            X                    [        i        ]              =                  ∑        GOP                          Qpic        ·        Tpic              ,                Rtot is the total bit rate capacity available at the output of the multiplexer:
  Rtot  =            ∑              i        =        1            n                          Rout                          [          i          ]                    .

Bit rate allocation in joint bit rate transcoding


The subject invention concerns a novel microbe and genes encoding novel toxin proteins with activity against cockroaches. Cockroaches are common house pests, and they create problems in hospitals, the food industry and in agriculture. The novel Bacillus thuringiensis microbe of the invention is referred to as B.t. PS185L8. The subject invention also concerns the use of PS201T6 to control cockroaches. The spores or crystals of these microbes, or variants thereof, are useful to control cockroaches in various environments. The genes of the invention can be used to transform various hosts wherein the novel toxic proteins can be expressed.

Bacillus thuringiensis (B.t.) produces an insect toxin designated as .delta.-endotoxin. It is synthesized by the B.t. sporulating cell. The toxin, upon being ingested in its crystalline form by susceptible insects, is transformed into biologically active moieties by the insect gut juice proteases. The primary target is insect cells of the gut epithelium, which are rapidly destroyed.
The reported activity spectrum of B.t. covers insect species within the order Lepidoptera, many of which are major pests in agriculture and forestry. The activity spectrum also includes the insect order Diptera, which includes mosquitos and black flies. See Couch, T. L. (1980) "Mosquito Pathogenicity of Bacillus thuringiensis var. israelensis," Developments in Industrial Microbiology 22:61-76; Beegle, C. C., (1978) "Use of Entomogenous Bacteria in Agroecosystems," Developments in Industrial Microbiology 20:97-104. Krieg, et al., Z. ang. Ent. (1983) 96:500-508, describe a B.t. isolate named Bacillus thuringiensis var. tenebrionis, which is reportedly active against two beetles in the order Coleoptera. These are the Colorado potato beetle, Leptinotarsa decemlineata, and Agelastica alni. In European Patent Application No. 0 202 739 there is disclosed a novel B.t. isolate active against Coleoptera. It is known as B. thuringiensis var. san diego (B.t.s.d.). U.S. Pat. No. 4,966,765 discloses the coleopteran-active Bacillus thuringiensis isolate B.t. PS86B1.
Cockroaches such as the German cockroach (Blatella germanica), Oriental cockroach (Blatta orientalis), American cockroach (Periplaneta americana) and Brown cockroach (Periplaneta americana) are some of the most important insect pests in homes and commercial structures. These pests have omnivorous feeding habits which result in the destruction of food, leather and fabrics. Cockroaches have also been implicated in the transmission of Salmonella and Toxoplasma. Cockroaches contain allergins. Approximately 7.5 percent of the human population is sensitive to these allergins.
Cockroaches are frequently controlled with baits. Because these baits are used in homes and restaurants, cockroach insecticides must be safe to humans. The heavy use of synthetic insecticides has resulted in the selection of resistant cockroach populations. New highly safe insecticides are necessary to control these resistant populations.

Bacillus thuringiensis isolates active against cockroaches and genes encoding cockroach-active toxins