An optical head device according to the present invention includes: a light source for outputting laser light; an optical system for allowing the laser light to be radiated onto an optical disk medium; and an aberration correction section for correcting an aberration of the laser light. The aberration correction section includes: a plurality of mirror sections for reflecting the laser light; a plurality of mirror driving sections for displacing the plurality of mirror sections; and a detection section for detecting a physical condition within the optical head device.

The optical memory technology which involves use of an optical disk medium having a pit pattern as a high-density and large-capacity information storage medium is being put to practical use, with its purposes being expanded to digital audio disks, video disks, text file disks, and further to data file disks. The functions which are necessary for using a finely-focused laser light to successfully perform recording of information onto an optical disk medium and reproduction of information from an optical disk medium in a highly reliable manner are generally classified into: a convergence function of forming a diffraction-limited light spot; a focus control (focusing servo) function for an optical system and a tracking control (tracking servo) function; and a pit signal (information signal) detection function.
In order to further enhance the recording density of an optical disk medium, the numerical aperture NA of an objective lens to be mounted in an optical head is on the increase and the wavelength λ of light from a light source is on the decrease, whereby the spot diameter of light which is converged by the objective lens is being reduced. Moreover, in order to further increase the recording capacity of an optical disk medium, there has been a trend to provide in an optical disk medium a plurality of recording layers for recording information.
For example, according to the CD (Compact Disc) standard, the numerical aperture NA of an objective lens is 0.45 and the wavelength of light from a light source is 780 nm. On the other hand, according to the DVD (Digital Versatile Disc) standard, which is adapted for a higher recording density and a larger capacity, the numerical aperture NA is 0.6 and the light wavelength is 650 nm.
By the way, an aberration which occurs due to a tilt of an optical disk medium with respect to the optical axis increases as the wavelength of light becomes shorter. Therefore, in order to employ a shorter-wavelength light source and still obtain a good light spot, it is effective to reduce the base thickness (i.e., a distance from a light-entering surface of an optical disk medium to a recording layer) in a manner to cancel such an aberration. Thus, the base thickness is 1.2 mm for the CD, but is 0.6 mm for the DVD.
Moreover, according to the BD (Blu-ray Disc) standard, which uses blue laser light, the numerical aperture NA is 0.85, and the base thickness is 0.1 mm.
A spherical aberration which is ascribable to the base thickness protecting a recording layer of an optical disk medium is in proportion with the fourth power of the numerical aperture NA. Therefore, when setting a large numerical aperture NA of 0.85, as in the case of the BD standard, a means for correcting spherical aberration is provided in the optical system.
Conventionally, a technique has been proposed which detects a specific type of aberration from the output signal of an optical pickup device and corrects the aberration. There are transmission-type aberration correcting devices using liquid crystal devices, as well as reflection-type aberration correcting devices which drive thin film mirrors or arrayed micromirrors, as are disclosed in Patent Document 1 and Patent Document 2.
Furthermore, although the market demand for downsizing of electronic devices is only increasing, progresses in semiconductor micromachining technology have facilitated the fabrication of micro structures such as aberration correcting devices. In the recent years, this technology is referred to as the micromachining technology, and there is a great deal of research and development directed to microactuators to which this technology is applied. One instance of an actual product of this is an acceleration sensor of a capacitance detection-type. Another instance is a spatial light modulation apparatus disclosed in Patent Document 3. This has been developed as an image displaying device for a video projector, and is known by the name of DMD (Digital Micromirror Device). Although this microactuator uses electrostatic attraction as its driving method, other examples would be electromagnetic force, thermal stress, optical pulling force, and the like.
A driving method which is used particularly frequently is electrostatic attraction. This method has an advantage in that it is capable of minimizing the driving voltage with a low power consumption, while also realizing a high response speed.
Furthermore, Patent Document 4 discloses a deformable mirror which, on the strength of the fact that electrostatic attraction is utilized as its driving force, realizes a displacement detection function of detecting its own displacement based on changes in capacitance.
Moreover, Non-patent Document 1 discloses a chip on which a temperature sensor, a pressure sensor, and a humidity sensor are collectively mounted. Each of these sensors is designed individually in accordance with the subject of detection, such that a different material is used for each sensor, each sensor being produced on its own.
[Patent Document 1] Japanese Laid-Open Patent Publication No. 2000-155979
[Patent Document 2] Japanese Laid-Open Patent Publication No. 2002-288873
[Patent Document 3] Japanese Laid-Open Patent Publication No. 8-334709
[Patent Document 4] Japanese Laid-Open Patent Publication No. 2002-228813
[Non-patent Document 1] "AN ALL-CAPACITIVE SENSING CHIP FOR TEMPERATURE, ABSOLUTE PRESSURE, AND RELATIVE HUMIDITY", IEEE 12th International Conference on Solid-State Sensors, Actuators and Microsystems, Boston, Mass., June 2003

Microarray with actuators inside and outside of light-irradiated region, and optical head device and optical information device incorporating the same


A precision molecular and motion sensor utilizing a Dispersed Fourier Transform Spectrometer to remotely sense targets. Remote sensing is conducted at various ranges, against various ambient backgrounds, to detect, classify, identify, characterize, and discriminate targets. A Dispersed Fourier Transform Spectrometer is expanded by modification and augmentation of existing optical, mechanical, and software components to enable basic terrestrial use while providing specific optimization for various applications which are designed with emphasis on the sensitivity of the Dispersed Fourier Transform Spectrometer.

The Dispersed Fourier Transform Spectrometer (DFTS) is a further modernization of the 1883 invention by Dr. Albert Michelson, who laid the theoretical basis for the Fourier Transform Spectrometer (FTS). The DFTS, as outlined in U.S. Pat. No. 7,206,073, which is hereby incorporated by reference in its entirety, consists of an FTS with a grating spectrometer and a metrology sub-system that can discern sub-nanometer vibrations and displacements, as well as discriminate and identify molecular species.
The DFTS was designed to investigate and characterize extra-solar stellar masses and motions at cosmic distances; it possesses the requisite high level of sensitivity to accomplish such tasks. However, the DFTS has not been applied to the problem of remotely sensing targets within the terrestrial domain. It is desirable to provide both systems and methods of implementing such systems, which capitalize on the capability of the DFTS to both: (1) detect differential motions and vibrations by measuring the variation in fringe shifts present with different spectral bands, and (2) differentiate between molecular species by using combinations of different spectral bands.

Systems for terrestrial target detection and characterization using a dispersed fourier transform spectrometer


The subject invention provides a unique system and method that facilitates self-regulation of a social network system based at least in part on user behavior, and in particular on good or desirable user behavior. The system and method involve monitoring user behavior such as user activity and user interactions with other users and the network itself. Several factors can be weighed to determine whether the user behavior is good. Network assets or rights can be allocated to good users in the form of gifts or trade exchange opportunities whereas less desirable or bad users may not receive such gifts or trade opportunities or assets and rights might be revoked from them. By watching user behavior and promoting good behavior in this manner, the social network can be managed and self-regulated to optimize the utilization and distribution of both limited and unlimited assets (e.g., network created and user created assets or resources).

One of the most effective channels of disseminating and obtaining information is through direct, personal relationships referred to as social networks. A social network consists of individuals and their personal relationships to other individuals through which social information and opportunities are exchanged. The direct, personal relationship implies that two people "know" each other and typically have a certain amount of trust for each other. The value of social networks can be demonstrated for example by the "six degrees of separation" phenomenon, which means that the distance between any two individuals in terms of direct personal relationships is relatively small (e.g., 6 degrees or less). Social networks are frequently employed by individuals often without conscious thought. For example, a person may be searching for a job and contact his or her friends to determine if they are aware of available positions. These friends are able to provide reliable information about positions they themselves directly know about. Additionally, these friends can recommend their job-seeking friend for available positions, assuming they consider the job-seeking friend to be qualified, reliable, hard working, and the like. Furthermore, these direct personal relationships can be employed to obtain social information and/or opportunities such as for example information about possible romantic partners, good movies, restaurants, buying, selling, buying or trading of items and services, recommendations for movies, restaurants, romantic partners and the like.
Direct personal relationships are particularly useful in obtaining information and opportunities because of the associated reliability of information and individuals involved. For example, an individual typically is more often willing to swap a vacation home (house-swap) with a friend of a friend, even though the individual may not personally know the friend of a friend, than to house-swap with a stranger. A basis for such trust is that the individual can trust that their immediate friend would not be associated with the person offering to house-swap (e.g., friend of the friend) if the friend of a friend was not reliable or trustworthy. More generally, the immediate friend can be trusted to offer an honest assessment of the trustworthiness of the third party. Social networks are often relied upon for opinion-based information such as for example, movies, restaurants, travel locations, and the like. Such information within a large number of the general populous is typically more relied on than well known restaurant and movie critics.
In the context of a social network, where people post messages possibly with pictures, comments and other type of annotation such as audio or video clips, there is a problem of maintenance and user regulation related to limited system resources and user behavior.

Systems and methods to facilitate self regulation of social networks through trading and gift exchange


An output circuit for a PWM inverter is provided which has an N-type first power device and a P-type second power device. Gates of the first and second power devices are connected to each other. Also, emitters of the first and second power devices are connected to each other. An input electrode control circuit controls the voltage applied to the common gates with respect to the common emitters. The voltage may be a positive or negative value, or zero. The input electrode control circuit controls the conduction states of the two power devices based upon the states of input light emitting devices associated with a first and second photocoupler (current generator). When both of the photocouplers are not lit, no current is generated and the conduction states of the power devices are instantaneously interrupted.

The present invention relates to an output circuit for a PWM (pulse width modulation) inverter which performs PWM control on the coil voltage of an electric motor.
PWM is an abbreviation for Pulse Width Modulation. The PWM technique is widely used in the field of motor control.
Recently, a PWM inverter rapidly becomes widespread and is widely used in motor control.
FIG. 9 is a block diagram showing the configuration of a usual PWM inverter, and shows an example of a three-phase PWM inverter. In the PWM inverter, generally, the number of output circuits 53 for the PWM inverter varies depending on the phase number of a motor to be controlled, but their fundamental operations are the same with each other.
The configuration of the three-phase PWM inverter will be described with reference to FIG. 9.
First, the fundamental frequency and the effective voltage of a three-phase voltage waveform to be supplied to a motor 60 are set to a frequency voltage setting circuit 58. Next, a PWM control circuit 59 internally generates three-phase PWM signals on the basis of information which is set to the frequency voltage setting circuit 58, and outputs the signals as switching control signals 42, 61, and 62. The switching control signals 42, 61, and 62 are binary signals which respectively instruct that the motor winding terminals 52, 63, and 64 are to be connected to a plus terminal of a main DC power source 14 or a minus terminal thereof. The frequency of the switching control signal 42, 61, or 62 is called a PWM carrier frequency and has a frequency which is usually ten or more times the fundamental frequency of the three-phase voltage waveform which is supplied to the motor 60. Usually, it is often that the fundamental frequency of the three-phase voltage waveform to be supplied to a motor is about 0 to 200 Hz, and the PWM carrier frequency is about 2 to 20 kHz.
A motor release signal 156 is a binary signal which instructs the motor to be set to a free running state or not to be the free running state. The free running state is a state in which all the motor winding terminals 52, 63, and 64 are connected to none of the plus and minus terminals of the main DC power source 14. In a case such as that where a trouble of any kind happens, usually, this state is set so as to protect the motor and a control apparatus.
The output circuits 53 for the PWM inverter are semiconductor switching circuits which control the connection of the motor winding terminal 52, 63, or 64 to the plus or minus terminal of the main DC power source 14 in accordance with the switching control signal 42, 61, or 62. The output circuits 53 are configured so that, when the motor release signal 156 instructs the motor to be set to the free running state, the motor winding terminal 52, 63, or 64 is connected to none of the plus or minus terminal of the main DC power source 14 irrespective of the switching control signal 42, 61, or 62. Usually, the voltage of the main DC power source 14 is often selected to be about DC 140 V which is obtained by rectifying and smoothing AC 100 V, or about DC 280 V which is obtained by rectifying and smoothing AC 200 V.
Hereinafter, the conventional output circuits 53 for the PWM inverter will be described.
FIG. 10 is a circuit diagram showing the configuration of the conventional output circuit 53 for the PWM inverter.
Referring to FIG. 10, a logic inverting circuit 65 inverts positive or negative logic of the switching control signal 42 and outputs an inverted switching signal 80. An AND circuit 157 outputs the result of AND of the motor release signal 156 and the switching control signal 42, as an upper arm switching signal 159. The AND circuit 157 outputs also the result of AND of the motor release signal 156 and the inverted switching signal 80, as a lower arm switching signal 160. On-delay circuits 66 and 67 output upper and lower arm control signals 81 and 82 which are obtained by delaying rise edges of the upper and lower arm switching signals 159 and 160 by an on-delay time TD, respectively.
A base drive circuit 68 causes a power transistor 70 to be turned ON or OFF in accordance with the upper arm control signal 81. A base drive circuit 69 causes a power transistor 71 to be turned ON or OFF in accordance with the lower arm control signal 82. Specifically, when the upper arm control signal 81 is in `H` level, the output transistor of a photocoupler 72 is turned ON. This causes a transistor 74 to be turned ON, so that a transistor 76 is turned OFF, thereby turning ON the power transistor 70. By contrast, when the upper arm control signal 81 is in `L` level, the output transistor of the photocoupler 72 is turned OFF. This causes the transistor 74 to be turned OFF, so that the transistor 76 is turned ON, thereby turning OFF the power transistor 70.
A base drive circuit 69 operates in the strictly same manner as the base drive circuit 68.
Other examples of the base drive circuits 68 and 69 are disclosed in, for example, Japanese utility model unexamined publication No. SHO 57-42589 and Japanese patent unexamined publication No. SHO 59-178980. These examples basically operate in the same manner as the base drive circuits 68 and 69 shown in FIG. 10 and may be replaced with the circuits.
Hereafter, description is made as to operation of the output circuit 53 for the PWM inverter configured above.
First, the case where the motor release signal 156 is in `L` level, namely instructs the motor to be set to the free running state will be considered. Then it will be found that both the power transistors 70 and 71 are in the OFF state irrespective of the level of the switching control signal 42 or in both the cases where the signal is in `L` level and where the signal is in `H` level.
Hereinafter,, the case where the motor release signal 156 is in `H` level or instructs the motor not to be the free running state will be described.
FIG. 11 is a waveform chart showing signals in the output circuit 53 for the PWM inverter of FIG. 10. When the switching control signal 42 is changed from `L` level to `H` level, the on-delay circuit 66 changes the upper arm control signal 81 from `L` level to `H` level with a time delay of the on-delay time TD from the change of the switching control signal 42. When the upper arm control signal 81 is changed to `H` level, the power transistor 70 is turned ON. There exists an operation delay time TX1 between the operations of the base drive circuit 68 and the power transistor 70. The operation delay time TX1 varies depending on changes of temperature of the power transistor 70 and the value of the current passing through the collector, and also on variations and aging of components constituting the base drive circuit 68 and the power transistor 70.
When the switching control signal 42 is changed from `L` level to `H` level, the inverted switching signal 80 is changed from `H` level to `L` level, and the on-delay circuit 67 changes the lower arm control signal 82 to `L` level with a substantially no time delay. When the lower arm control signal 82 is changed to `L` level, the power transistor 71 is turned OFF. There exists an operation delay time TY2 between the operations of the base drive circuit 69 and the power transistor 71. The operation delay time TY2 varies depending on changes of temperature of the power transistor 71 and the value of the current passing through the collector, and also on variations and aging of components constituting the base drive circuit 69 and the power transistor 71.
When the switching control signal 42 is then changed from `H` level to `L` level, the on-delay circuit 66 changes the upper arm control signal 81 to `L` level with a substantially no time delay, so that the power transistor 70 is turned OFF. There exists an operation delay time TY1 between the operations of the base drive circuit 68 and the power transistor 70.
When the switching control signal 42 is changed from `H` level to `L` level, the inverted switching signal 80 is changed from `L` level to `H` level, and the on-delay circuit 67 changes the lower arm control signal 82 from `L` level to `H` level with the time delay TD. When the lower arm control signal 82 is changed to `H` level, the power transistor 71 is turned ON. There exists an operation delay time TX2 between the operations of the base drive circuit 69 and the power transistor 71.
When the operation delay time TX1 or TX2 is compared with the operation delay time TY1 or TY2, usually, the operation delay time TY1 or TY2 tends to be longer than the operation delay time TX1 or TX2. Provided that, considering the worst conditions, the smallest value of the operation delay times TX1 and TX2 is indicated by TXW and the longest value of the operation delay times TY1 and TY2 is indicated by TYW, the on-delay time TD is usually set to have a value which is the sum of a small margin and a value obtained by subtracting TXW from TYW.
In the case where bipolar power transistors are used, the on-delay time TD is set to be about 10 to 50 microseconds. In the case where IGBTs (Insulated gate bipolar transistor) are used, the on-delay time TD is set to be about 5 to 30 microseconds, and, in the case where power MOS-FETs are used, set to be about 2 to 10 microseconds. When the switching control signal 42 is changed from `H` level to `L` level or from `L` level to `H` level, the on-delay time prevents the power transistors 70 and 71 from being simultaneously turned ON so as to short-circuit the plus and minus terminals of the main DC power source 14.
Then the states of the switching control signal 42 and a motor winding terminal voltage 51 will be considered. When the switching control signal 42 is fixed to `L` level, the power transistor 71 is in the ON-state under the state where the power transistor 70 is turned OFF. Therefore, the motor winding terminal 52 is connected to the minus terminal of the main power source 14. When the switching control signal 42 is fixed to `H` level, the power transistor 71 is in the OFF-state under the state where the power transistor 70 is turned ON. Therefore, the motor winding terminal 52 is connected to the plus terminal of the main power source 14.
In the above-described configuration of the prior art, when the switching control signal 42 is changed from `L` level to `H` level or vice versa in the case where the motor release signal 156 is in `H` level or instructs the motor not to be the free running state, both the power transistors 70 and 71 are in the OFF-state for a certain time period. This causes a control error in voltage control of the motor winding terminal 52. The control error produces problems in that the torque and the rotational speed of the motor are varied and that noises and vibrations of the motor are increased in level.
These problems will be described in more detail.
Referring to FIG. 10 and FIG. 11, when the switching control signal 42 is changed from `L` level to `H` level or vice versa, a power transistor which has been in the ON-state is first turned OFF and that which has been in the OFF-state is then turned ON. During a time period, therefore, both the power transistors 70 and 71 are in the OFF-state. This state is called the floating state, and this time period is called the floating time period TZ. Usually, the floating time period TZ is often about 1/2 to 2/3 of the on-delay time TD.
Originally, in the PWM control of a motor, for example, the motor winding terminal 52 is alternatingly connected to the plus and minus terminals of the main DC power source 14. The average voltage of the motor winding terminal 52 is controlled in accordance with the ratio of the period when the winding terminal is connected to the plus terminal to the period when the winding terminal is connected to the minus terminal. Ideally speaking, when the voltage of the main DC power source 14 is fixed, the average voltage of the motor winding terminal 52 is uniquely controlled in accordance with the time ratio of `H` level to `L` level of the switching control signal 42.
In the prior art output circuit for the PWM inverter, however, there exists the floating state and hence the average voltage of the motor winding terminal 52 is varied depending on the direction of the current flowing through the motor winding terminal 52. Specifically, when the floating state is established under the state where the current flows in the direction along which the current flows from the motor winding terminal 52 into the output circuit 53 for the PWM inverter, a diode 78 conducts and hence the state where the motor winding terminal 52 is connected to the plus terminal of the main DC power source 14 is produced. This state is indicated by a terminal voltage 51A of motor winding in FIG. 11. By contrast, when the current flows in the direction along which the current flows from the output circuit 53 for the PWM inverter into the motor winding terminal 52 under the floating state, a diode 79 conducts, and hence the state where the motor winding terminal 52 is connected to the minus terminal of the main DC power source 14 is produced. This state is indicated by a terminal voltage 51B of motor winding in FIG. 11. When no current flows through the motor winding terminal 52 under the floating state, the voltage of the motor winding terminal 52 is determined by voltages such as an induced voltage generated in the motor 60.
As described above, the existence of the floating state causes the average voltage of the motor winding terminal 52 not to be uniquely determined by the switching control signal 42, thereby producing a control error. Usually, since the current passing through the motor winding terminal 52 is an alternating current and changed in the direction, the control error is also changed depending on the change of the direction of current, and thereby the torque and the rotational speed of the motor 60 are varied. This problem can be solved by eliminating the floating state and making the floating time period zero. In the conventional output circuit for the PWM inverter, however, a short circuit between the plus and minus terminals of the main power source 14 occurs and hence it is practically impossible to solve the problem.
Furthermore, when the power transistor is turned ON or OFF, electric noise is produced. In a use wherein such electric noise should be reduced in level, particularly, the switching speed is sometimes lowered by, for example, a method in which a capacitor is connected across the base and the emitter of the power transistor. However, this countermeasure increases variations of the operation delay times TX1, TX2, TY1, and TY2 to a very large value, whereby the floating time is inevitably further prolonged. Therefore, the control error is increased, with the result that the switching speed cannot be largely lowered.
Other conventional output circuits for the PWM inverter are used in which the power transistors 70 and 71 of FIG. 10 are replaced with power MOS-FETs, respectively, or in which the power transistors are replaced with IGBTs, respectively. However, also these circuits operate in the same manner as the conventional output circuit for the PWM inverter shown in FIG. 10 and has the floating state.

Output circuit for PWM inverter with no floating state

Matsushita Electric Industrial Co., Ltd.


A method and system is provided for obtaining data indicative of at least one characteristic of a continuous medium or at least one localized target located within a predetermined volume of space. The system includes a sensor configuration with at least one sensor for acquiring a plurality of signals from the continuous medium or the target. Each one of the plurality of signals is centered at a respective distinguishable frequency. The system also includes a processing circuit for obtaining the data indicative of the characteristic of the continuous medium or the target by calculating a plurality of powered weighted increments using the plurality of signals acquired by the sensor configuration and by relating the plurality of powered weighted increments to the characteristic of the continuous medium or the target using a plurality of models.

1. Field of the Invention
The invention relates to the field of detection and monitoring and specifically to a system and method for measuring the characteristics of continuous medium and/or localized targets in a predetermined volume using at least one remote sensor operating at multiple frequencies.
2. Description of the Related Art
An important problem in the field of detection and monitoring is accurately and reliably measuring as many characteristics of a monitored object as possible. Adequate accuracy and reliability are especially important in the case of remote detection and monitoring under adverse measurement conditions. Characteristics of a monitored object produced by detection and monitoring equipment seldom represent the final product of a measurement system. Typically these characteristics are further interpreted for making decisions and/or recommendations and the decisions and/or recommendations are presented to the system's users. By reliably and accurately measuring more characteristics of the monitored object, one ensures more robust and definite decision making and significantly decreases the probability of making an incorrect decision. Best possible data interpretation is especially important for automated real-time systems.
The monitored object can be a predetermined volume in a continuous medium such as the atmosphere, lakes, rivers, the ocean, surface and subsurface terrain, the human body, a chemical reactor, or any other media. Measured characteristics of such medium in a specified volume are used, for example, in the fields of meteorology, weather forecasting, geology, agriculture, medicine, and astronomy. Additionally, measured characteristics of such medium in a specified volume are also used, for example, in monitoring the airspace around airports, in monitoring conditions in chemical and processing plants, and in monitoring other somewhat similar processes and physical configurations. Monitored objects can also be specified targets located in a predetermined volume, such as, missiles, airplanes, obstacles, defects in a product, intruders, or other specified targets; in these cases the measured characteristics of the targets are used for purposes of national defense and homeland security, collision avoidance, non-destructive product testing, business and personal protection, and the like. It should be noted that in the instant disclosure the general term "monitored object" can be construed to refer to a predetermined volume in a continuous medium or a specified target in a predetermined volume. When a specified target is located in a predetermined volume it may also be referred to as a localized target.
Existing monitoring equipment can be divided into two classes namely, single sensor equipment and multiple sensor equipment. In addition, equipment with both single and multiple sensors can operate at single or multiple frequencies. Single-frequency, single-sensor equipment, such as, for example, standard single-receiver Doppler radars and sonars operating at a single frequency have been and are still widely used for numerous applications. However, such equipment provides a relatively small amount of initial information about the monitored object. This factor significantly limits the number of characteristics of the object that can be determined and also limits the accuracy and reliability of measurements, especially at adverse conditions. Manufacturing and implementing multi-frequency single-sensor or multiple-sensor monitoring equipment capable of performing real-time operations is now possible because of the outstanding progress in electronics and computer technologies that has been made during the last several decades. When compared with single frequency monitoring equipment, multi-frequency monitoring equipment provides a dramatically larger amount of initial information about the monitored object and therefore, enables more reliable measurement of a greater number of characteristics of the monitored object with much higher accuracy under any conditions. Known examples of multi-frequency sensor configurations include arrays of receiving antennas operating at multiple distinct frequencies, which are used in spaced antenna atmospheric profiling radars, telescopes and radio-telescopes collecting signals at multiple distinguishable frequencies, surveillance radars utilizing the frequency modulated chirp pulse compression, and continuous wave radars. Monitoring equipment that obtains signals at multiple frequencies from a single sensor or multiple sensors produce a large amount of initial information about a monitored object in comparison to the information produced with equipment that obtains signals from the same sensors at a single frequency. The objective of data analysis is to accurately and reliably extract as many useful characteristics of the object as possible. All data processing methods using data at multiple frequencies obtained from single or multiple sensors are basically similar in that they utilize the same initial information: time series of signals at multiple frequencies from one or a plurality of sensors. The methods differ by the mathematical functions used for analyzing the signals, the mathematical models for relating these functions to the characteristics of the monitored object, and the assumptions that are adopted for constructing the models.
Traditional correlation function and spectra-based data processing methods for multi-frequency single or multiple sensor monitoring equipment have been widely used for decades in numerous areas of applications. At the same time, the drawbacks of these methods have been well recognized and thoroughly documented. They are as follows: (1) a poor temporal and/or spatial resolution; (2) the inability to operate in adverse measurement conditions such as external interference and strong clutter; (3) a low reliability of measurements due to the adoption of inappropriate, often too restrictive assumptions, and (4) a limitation in the number of characteristics of the monitored object that can be retrieved. For example, the variance of the vertical turbulent velocity is the only characteristic of atmospheric turbulence that can be retrieved with a spaced antenna profiler using traditional data processing methods. Another crucial problem with traditional data processing methods is referred to as the radial velocity ambiguity. This problem is inherent in remote sensors which use the Doppler spectra for measuring the radial velocity of continuous medium and/or localized targets.
Drawbacks of traditional data processing methods described hereinabove have been partly addressed by the structure function-based method. In the particular case of a spaced antenna atmospheric profiler operating at a single frequency, using structure functions allows an improvement of temporal resolution, the mitigation of external interference and clutter effects, the determination of the variances of the horizontal turbulent velocities and the horizontal momentum flux, and the derivation of operational equations by making a smaller number of less restrictive assumptions. Notwithstanding, the limitations of the structure function-based method have also been well recognized.
To understand the limitations, one should consider the definition and interpretation of structure functions for the received signals s({right arrow over (x)}1,t) and s({right arrow over (x)}2,t) from two sensors in close spatial locations {right arrow over (x)}1 and {right arrow over (x)}2 at two close times t1 and t2. The cross structure function of the order p is defined as follows:Dp({right arrow over (x)},δ{right arrow over (x)},t,τ)=Δsp({right arrow over (x)},δ{right arrow over (x)},t,τ), Δs({right arrow over (x)},δ{right arrow over (x)},t,τ)=s({right arrow over (x)},t)−s({right arrow over (x)}+δ{right arrow over (x)},t+τ)  (1)Hereinafter: t is time, {right arrow over (x)}={right arrow over (x)}1, t=t1, δ{right arrow over (x)}={right arrow over (x)}2−{right arrow over (x)}1 and τ=t2−t1 are respectively the spatial separation between the sensors and the temporal separation between the signals, and the angular brackets <> denote ensemble averages. It is important that equation (1) defines only one equation of order p for a pair of sensors. One can see that Dp({right arrow over (x)}, δ{right arrow over (x)}, t, τ) is the pth order statistical moment of the increment Δs({right arrow over (x)}, δ{right arrow over (x)}, t, τ); the latter is customarily interpreted as a band-pass filter extracting fluctuations with spatial and temporal scales |δ{right arrow over (x)}| and τ, respectively. However, it has long been established that this is not the case and that the increment is, in fact, a multi-band filter. For example, the normalized spectral transfer function of the auto increment Δs({right arrow over (x)}, 0, t, τ)=s({right arrow over (x)},t)−s({right arrow over (x)},t+τ) is 1−cos(2πfτ) with maxima occurring at multiple frequencies f=1/(2τ)+k/τ, k=0, 1, 2, . . . . Customarily, only the first band at k=0 is taken into account in the interpretation of structure functions, while others of the same intensity and bandwidth are merely ignored. The next issue is that a cross structure function is not a rigorous mathematical tool. It follows from equation (1) that the temporal Dp({right arrow over (x)}, 0, t, τ) and spatial Dp({right arrow over (x)}, δ{right arrow over (x)}, t, 0) auto structure functions at |τ|→0 and |δ{right arrow over (x)}|→0 are the first-order finite approximations of the respective temporal derivatives and spatial derivatives in the direction δ{right arrow over (x)}. The first order approximation of a cross derivative at |δ{right arrow over (x)}|→0, |τ|→0 is:
                                                        ∂              2                                                  s                                            (                                                      x                    ⇀                                    ,                  t                                )                                                                        ∂              t                                                  ∂                              x                ⇀                                                    ≈                              1                          τ                                                                              δ                                                        x                    _                                                                                                                      [                                          s                                                  (                                                                                x                        ⇀                                            +                                              δ                                                                                x                          ⇀                                                                                ,                                          t                      +                      τ                                                        )                                            -                              s                                                  (                                                                                x                        ⇀                                            +                                              δ                                                                                x                          ⇀                                                                                ,                    t                                    )                                            -                              s                                                  (                                                            x                      ⇀                                        ,                                          t                      +                      τ                                                        )                                            +                              s                                                  (                                                            x                      ⇀                                        ,                    t                                    )                                                      ]                          ≡                              -                          1                              τ                                                                                        δ                                                              x                      ⇀                                                                                                                                        {                                          [                                                      s                                                              (                                                                        x                          ⇀                                                ,                        t                                            )                                                        -                                      s                                                              (                                                                                x                            ⇀                                                    +                                                      δ                                                                                x                              ⇀                                                                                ,                                                  t                          +                          τ                                                                    )                                                                      ]                            -                              [                                                      s                                                              (                                                                        x                          ⇀                                                ,                        t                                            )                                                        -                                      s                                                              (                                                                                x                            ⇀                                                    +                                                      δ                                                                                x                              ⇀                                                                                ,                        t                                            )                                                                      ]                            -                              [                                                      s                                                              (                                                                        x                          ⇀                                                ,                        t                                            )                                                        -                                      s                                                              (                                                                        x                          ⇀                                                ,                                                  t                          +                          τ                                                                    )                                                                      ]                                      }                                              (        2        )            One can see from equations (1) and (2) that the increment Δs({right arrow over (x)}, δ{right arrow over (x)}, t, τ) corresponds to the first bracketed term in the derivative while the second and third terms are merely ignored. Therefore, the cross structure function is a truncated representation of the cross derivative ∂2s({right arrow over (x)},t)/(∂t∂{right arrow over (x)}).
These theoretical issues lead to serious practical drawbacks when using structure function-based data processing methods with monitoring equipment operating at multiple frequencies and having a single sensor or multiple sensors. For example, in the case of an atmospheric spaced antenna profiler, the major drawbacks are as follows: (1) an inability to retrieve the vertical momentum fluxes, (2) a high sensitivity to white noise, (3) an inability to directly measure the correlation between noise from different sensors, and (4) an inability to provide more than one equation for each pair of sensors. Importantly, the structure function-based data processing methods do not allow measuring the radial velocity with single-frequency monitoring equipment in most practical sensor configurations. These drawbacks complicate the operational use of existing data processing methods and cause degradation in the performance of monitoring equipment with one or more sensors operating at multiple frequencies.

System and method for measuring characteristics of continuous media and/or localized targets using at least one multi-frequency sensor


An output circuit has an output transistor, or a complementary pair of output transistors, that generate a bi-level voltage signal with a high output level and a low output level. The signals applied to the gates of the output transistors have high and low levels that are more narrowly separated than are the output high and low levels. For example, one gate signal may swing between the output high level and an intermediate level, and another gate signal may swing between the output low level and the same or a different intermediate level. The relatively narrow voltage swing reduces current consumption, and the intermediate level or levels can be adjusted to adjust the rise time and fall time of the output signal.

1. Field of the Invention
The present invention relates to an output circuit in a semiconductor integrated circuit, more particularly to an output circuit with reduced power consumption.
2. Description of the Related Art
Conventional output circuits are generally structured as shown in FIG. 1, comprising a buffer B1 that receives an input signal S1 and drives two output transistors P3, N3. As shown in FIG. 2, the input signal S1, the signal SG1 applied to the gate electrodes of the output transistors P3, N3, and the output signal (OUT) all swing between the same power supply potential (VCC) and ground potential (GND). Since the output transistors are normally designed with large gate widths to provide adequate driving capability, the amount of current consumed in charging and discharging the capacitance of their gates is not negligible, particularly in a high-voltage output circuit.
Japanese Patent Application Publication No. 2000-49584 describes a high-voltage output circuit with a pair of level shifters that convert a narrow-swing input logic signal to two gate-driving signals, one with a raised high logic level, the other with a lowered low logic level. This scheme reduces the gate voltage swings, but the voltage shifters have fixed output ranges that overlap and cannot be adjusted.

Output circuit with reduced gate voltage swings


Disclosed herein is a plate-shaped secondary battery constructed in a structure in which an electrode assembly of a cathode/separator/anode structure is mounted in a battery case, and the battery case is sealed by thermal welding, wherein the secondary battery has at least one valve (one-way exhaust valve), having a small thickness, mounted at a sealed portion, formed at the outer circumference of an electrode assembly receiving part of the battery case, for allowing internal high-pressure gas to be exhausted out of a battery cell and preventing external gas from being introduced into the battery cell. The secondary battery according to the present invention has the effect of effectively exhausting internal high-pressure gas generated during the abnormal operation of the battery, such as overcharge, out of the battery case, while maintaining the sealability of the battery case, thereby simultaneously improving the efficiency and safety of the battery.

As mobile devices have been increasingly developed, and the demand of such mobile devices has increased, the demand of secondary batteries has also sharply increased as an energy source for the mobile devices. Among them is a lithium secondary battery having a high energy density and a high discharge voltage, on which much research has been carried out and which is now commercialized and widely used.
Based on its external shape, the lithium secondary battery may be generally classified as a cylindrical battery, a prismatic battery, or a pouch-shaped battery. Based on its electrolyte, on the other hand, the lithium secondary battery may be classified as a lithium-ion battery, a lithium-ion polymer battery, or a lithium polymer battery.
As the mobile devices have been miniaturized, the demand of the rectangular battery and the pouch-shaped battery, which have a relatively small thickness, has increased. Especially, much interest is currently generated in the pouch-shaped battery because the shape of the pouch-shaped battery is easily changed, the manufacturing costs of the pouch-shaped battery are low, and the weight of the pouch-shaped battery is small.
Generally, the pouch-shaped secondary battery is manufactured by mounting an electrode assembly, including cathodes, anodes, and separators disposed respectively between the cathodes and the anodes, in a pouch-shaped battery case, constructed in a laminate structure of a resin layer/a metal film layer/a resin layer, and thermally welding a sealed portion, formed along the outer circumference of the battery case, to seal the battery case.
The sealed portion is a region formed by thermally welding the outer circumferential portions of the battery case surrounding the outer surface of the electrode assembly while the outer circumferential portions of the battery case are in contact with each other. It is required for the sealed portion of the battery case to exhibit sealability for preventing external air from being introduced into the battery case during the normal operation of the battery. Also, it is required for the sealing portions of the battery case to release the sealability, when high pressure is generated in the battery due to the abnormal operation of the battery, such as continuous charge and discharge for a long period of time or application of high temperature to the battery, to exhaust gas out of the battery case. Consequently, the sealed portion of the battery case is very important to improve the safety of the battery as well as the efficiency of the battery. However, the sealing function and the gas exhaust function are opposite action mechanisms, and therefore, it is difficult to effectively achieve both the sealing function and the gas exhaust function.
In this connection, there has been restrictively proposed only a structure for releasing the sealed portion when high pressure is generated in a plate-shaped secondary battery; however, there has been not proposed a structure for exhausting pressurized gas out of a plate-shaped secondary battery while maintaining the sealability of the secondary battery.
For example, Japanese Patent Application Publication No. 2005-116235 discloses a technology for forming a specific gas exhaust mechanism in a battery constructed in a structure in which the outer circumferential portions of a laminate film, in which an electrode assembly is mounted, are thermally welded to seal the laminate film. The disclosed technology includes a method of forming partially a non-welded part at the sealed portion, during the thermal welding process, to concentrate the pressure of internal gas to the non-welded part, and a method of deforming the innermost sealing layer of the laminate film such that the innermost sealing layer has an adhesive strength less than that of the remaining region of the laminate film.
However, experiments carried out by the inventors of the present invention revealed that the adhesive force of the sealed portion where the gas exhaust mechanism is formed is small, and therefore, moisture continuously permeates into the battery cell through the sealed portion where the gas exhaust mechanism is formed and an electrolyte continuously leaks from the battery cell through the sealed portion where the gas exhaust mechanism is formed, even during the normal operation of the battery, whereby the safety of the battery is seriously deteriorated. In consideration of a fact that the size of the non-welded part and the size of the adhesive strength must be precisely controlled within a specific range due to the above-mentioned problems, the disclosed technology has a fundamental problem in that it is difficult for the corresponding region to be reliably operated under a high pressure condition requiring the exhaust of gas.
On the other hand, Japanese Patent No. 3,638,765 discloses a battery constructed in a structure in which a plate-shaped electrode assembly is mounted in a sheathing member, and the outer circumferential portions of the sheathing member are attached to each other by thermal welding or an adhesive layer to seal the sheathing member, wherein the sheathing member is sealed while a polymer resin sheet, having a thermal safety higher than that of the sheathing member, is partially inserted between the outer circumferential portions, whereby the sealed portion having the polymer resin sheet exhibits a pressure resistance less than that of the remaining sealed portion. Also, Japanese Patent Application Publication No. 2001-093489 discloses a battery constructed in a structure in which an electrode assembly is mounted in a pouch-shaped battery case made of a laminate sheet, and cathode and anode leads, connected to cathode and anode plates of the electrode assembly, are exposed outward from the sealed portion of a sheathing case, wherein the thermal welding is carried out while a thermal welding resin sheet, having a melting point lower than that of the laminate sheet, is partially inserted in the sealed portion of the sheathing case.
However, the above-mentioned technologies do not secure the sealability and operational reliability of the battery.
On the other hand, technologies for exhausting gas from some devices in one direction are known, although the devices are not plate-shaped secondary batteries. For example, U.S. Pat. No. 5,004,655 discloses a lead battery including a spacer mounted around a battery receiving part, wherein an opening is formed at one side of the spacer, and silicon oil is applied to the opening, thereby preventing external moisture from permeating into the battery while allowing internal gas to be exhausted in one direction. Also, Japanese Patent Application Publication No. 2003-037028 discloses a condenser including a sheathing case constructed in a structure in which a metal film and a plastic film are stacked, wherein a gas exhaust valve of an oil sealing structure is mounted at the inside of the sheathing case, and a pin hole for exhausting gas out of the sheathing case is formed at the sheathing case outside the gas exhaust valve.
However, the one-way gas exhaust structure of these technologies is applicable to devices that are not seriously affected by moisture introduced into the devices, and therefore, the one-way gas exhaust structure is not structurally applicable to a plate-shaped secondary battery. In conclusion, no attempts have been made to apply the one-way gas exhaust structure to the plate-shaped secondary battery.

Secondary battery including one-way exhaust valve


A wafer inspection system comprises a camera having a field of view, an object mount configured to position at least a portion of surface 5 of an object 3 at an object plane 15 relative to the camera and within the field of view of the camera and at least one surface portion 41 carrying a multitude of retroreflectors 95 disposed at a greater Δd distance from the camera than the object plane and within the field of view of the camera.

1. Field of the Invention
The present invention relates to semiconductor wafer inspection systems and semiconductor wafer inspection methods.
2. Brief Description of Related Art
Semiconductor circuits are manufactured by forming micro-patterned structures on a flat semiconductor wafer substrate using lithographic methods. A wafer substrate may have a diameter of about 300 mm, wherein several hundred circuits are arranged in individual dies typically having diameters in the order of some millimeters to some 10 mm, wherein the structures of the semiconductor circuits may have dimensions below 0.1 μm. It is desirable to detect defects in the manufactured patterns and deficiencies of a manufacturing process at early stages of the semiconductor manufacture.
Several techniques are known for inspection of semiconductor substrates. These techniques try to locate defects on a wafer substrate in a coordinate system defined relative to the wafer substrate. The coordinate system of the wafer may be defined such that it has its origin in a center of the wafer, wherein an orientation of the coordinate system is defined relative to a wafer notch.
In a process of semiconductor wafer inspection it is necessary to map coordinates of defects as detected in a coordinate system of an inspection tool to the coordinate system of the wafer. Conventional inspection methods involve special tools and methods for detecting a wafer edge to finally determine the center of a particular wafer on the inspection, and to detect the wafer notch to determine the orientation of the wafer.
The tools and methods for wafer edge and notch detection have sometimes been found to be insufficient and complicated.

Semiconductor wafer inspection system and method


A conferencing unit, comprising an array of microphones embedded in a diffracting object configured to provide a desired high frequency directivity response at predetermined microphone positions, and a low frequency beamformer operable to achieve a desired low frequency directivity response, wherein the beamformer is linearly constrained to provide a smooth transition between low and high frequency directivity responses.

Directional microphones are well known for use in speech systems to minimise the effects of ambient noise and reverberation. It is also known to use multiple microphones when there is more than one talker, where the microphones are either placed near to the source or more centrally as an array. Moreover, systems are also known for determining which microphone or combination to use (i.e. higher noise and reverberation requires that an increased number of directional microphones be used). In teleconferencing situations, it is known to use arrays of directional microphones associated with an automatic mixer. The limitation of these systems is that they are either characterised by a fairly modest directionality or they are of costly construction.
Microphone arrays have been proposed to solve the foregoing problems. They are generally designed as free-field devices and in some instances are embedded within a structure. The limitation of prior art microphone arrays is that the inter-microphone spacing is restricted to half of the shortest wavelength (highest frequency) of interest. This means that for an increase in frequency range, the array must be made smaller (thereby losing low frequency directivity) or microphones must be added (thereby increasing cost). The other problem with this approach is that the beamwidth decreases with increasing frequency and side lobes become more problematic. This results in significant off axis "coloration" of the signals. As it is impossible to predict when a talker will speak, there is necessarily a time during which the talker will be off axis and this "coloration" will degrade the signal.
It is an object of this invention to provide a microphone array having a reasonably constant beampattern over a frequency range that extends beyond the traditional limitation of inter-sensor spacing to half a wavelength.
The following references illustrate the known state of the art:    [1] Michael Brandstein, Darren. Ward, "Microphone arrays", Springer, 2001.    [2] Gary Elko, "A steerable and variable first-order differential microphone array", U.S. Pat. No. 6,041,127, Mar. 21, 2000.    [3] Michael Stinson, James Ryan, "Microphone array diffracting structure", Canadian Patent Application 2,292,357.    [4] Jens Meyer, "Beamforming for a circular microphone array mounted on spherically shaped objects", Journal of the Acoustical Society of America 109 (1), January 2001, pp. 185-193.    [5] Marc Anciant, "Modélisation du champ acoustique incident au décollage de la fusée Ariane", July 1996, Ph.D. Thesis, Université de Technologie de Compiègne, France.    [6] A. C. C. Warnock & W. T. Chu, "Voice and Background noise levels measured in open offices", IRC Internal Report IR-837, January 2002.    [7] S. Dedieu, P. Moquin, "Method for Broadband Constant Directivity Beamforming for Non Linear and Non Axi- Symmetric Arrays Embedded in an Obstacle", U.S. Patent Application Publication No. 2004/0120532.    [8] Morse and Ingard, "Theoretical Acoustics", Princeton University Press, 1968.
Brandstein and Ward [1] provide a good overview of the state of the art in free-field arrays. Most of the work in arrays has been done in free field, where the size of the array is necessarily governed by the frequency span of interest.
The use of an obstacle in a microphone array is discussed in Elko [2]. Specifically, Elko uses a small sphere with microphone dipoles in order to increase wave-travelling time from one microphone to another and thus achieve better performance in terms of directivity. A sphere is used since it permits analytical expressions of the pressure field generated by the source and diffracted by the obstacle. The computation of the pressure at various points on the sphere allows the computation of each of the microphone signal weights. The spacing limit is given as 2λ/π (approx. 0.64λ) where λ is the shortest wavelength of interest.
M. Stinson and J. Ryan [3] extend the principle of microphone arrays embedded in obstacles to more complex shapes using a super-directive approach and a Boundary Element method to compute the pressure field diffracted by the obstacle. Stinson and Ryan emphasise low frequency, trying to achieve strong directivity with a small obstacle and a specific treatment using cells (i.e. reactive impedance) thereby inducing air-coupled surface waves. This results in an increase in the wave travel time from one microphone to another and increases the "apparent" size of the obstacle for better directivity at low frequencies. Stinson and Ryan have proven that using an obstacle provides correct directivity in the low frequency domain, when generally other authors use microphone arrays of large size. Additionally Stinson and Ryan invoke the use of acoustic absorbent materials to provide impedance treatment. However, the application is designed for narrow band telephony.
The benefit of an obstacle for a microphone array in terms of directivity and localisation of the source or multiple sources is also described in the literature by Jens Meyer [4] and by Marc Anciant [5]. Jens Meyer demonstrates the benefit of adding a sphere on a microphone array compared to a free-field array in terms of broadband performance and noise rejection. Anciant describes the "shadow" area for a 3D-microphone array around a mock-up of the Ariane IV rocket in detecting and characterising the engine noise sources at take-off.
With the exception of Elko [2] (who sets the spacing limit at 2λ/π), the prior art explicitly or implicitly concedes the requirement for a high frequency performance limit defined by an inter-element spacing of λ/2 to avoid grating lobes in free-field.
The superdirective beamformers that are commonly used for microphones are discussed in chapter 2 of Brandstein [1] and the essential elements are noted below, to better understand the background of the present invention.
Beamforming may be used to discriminate a source position in a "noisy" environment at a frequency ω in a band [ω0, ωn]. Let d(ω) be the signal vector containing the signal di(ω) of each microphone of the array when the source is active. Let n(ω) be the vector of noise signal at each microphone and Rnn(ω) the noise correlation matrix. Depending on the environment, this matrix can be defined in different ways, such as for diffuse spherical or cylindrical isotropic noise or more simply for white noise. Reference [5] provides a detailed discussion of how the noise correlation matrix may be defined.
Beamforming consists of finding a vector wopt(ω) of coefficients wi(ω) such that weighting the signal di(ω) at each microphone with each wi(ω) creates a beam towards the source. For a super directive approach, the problem can be written in the following way:
                                                                        Min                w                                                          1                2                                                          w                H                                                                                R                nn                                          w                                                                                subject                                                                                to                                                                                w                  H                                                                                d                            =              1                                                          (        1        )            where the dependency in ω has been omitted for clarity purposes.
The optimal weight vector is:
                              w          opt                =                                            R              nn                              -                1                                                  d                                              d              H                                                  R              nn                              -                1                                                  d                                              (        2        )
As described in U.S. Patent Application Publication No. 2004/0120532, linear or quadratic constraints can be added to impose a specific pattern to a beam, to reduce the coupling between the microphone beam and a loudspeaker or to keep the beam constant vs. frequency or vs. angle when the obstacle is not axi-symmetric.

Method for extending the frequency range of a beamformer without spatial aliasing


A three-dimensional image is produced using an imaging medium having a lenticular screen, the lenticles of the screen dividing the opposed surface of the imaging medium into a plurality of elongate image areas, the imaging medium having on the opposed side thereof a radiation-sensitive layer, the radiation-sensitive layer comprising a color-forming composition adapted to undergo a change of color upon increase in the temperature of the radiation-sensitive layer above a color-forming temperature for a color-forming time. The radiation-sensitive layer is imagewise exposed to actinic radiation which does not pass through the lenticular screen, thereby causing the color-forming composition to undergo its change in color in exposed areas and to form in the radiation-sensitive layer a composite image, the composite image comprising, in each of the image areas, a plurality of image strips extending lengthwise along the image area, each of the image strips containing information from a view of the object, each of the plurality of image strips in one image area containing information from a different view of the object thereby forming a copy of the composite image in the radiation-sensitive layer, so that a three-dimensional orthoscopic image of the object will appear to an observer seeing the composite image in the radiation-sensitive layer through the lenticular screen.

Modern computer drawing and modelling programs (usually known as "computer assisted design" or "CAD" programs) can display complicated three-dimensional objects in great detail, can generate shadows showing the appearance of the object in various types and directions of lighting, and permit the observer to rotate the three-dimensional object about any axis, so that he can see any desired aspect of the object. So realistic are the images produced by sophisticated CAD programs that it is difficult for the user not to believe that he is watching a real object rather than just a computer simulation of a non-existent object. (Hereinafter for convenience, the term "real object" will be used to denote an object which physically exists in space-time, while the term "virtual object" will be used to denote a model which exists only as a mathematical construct in a computer.)
Unfortunately, when the user of a CAD program wishes to produce a hard copy of a three-dimensional virtual object, he finds that most available forms of output are essentially two-dimensional. Typically, the user will generate a hard copy of his results as a series of two-dimensional sections through the object. While such a series of sections may be convenient for preparing working drawings for manufacture of the corresponding real object, such a series does not readily convey an idea of the three-dimensional structure of the virtual object to most observers, particularly those not skilled in interpreting technical drawings.
Alternatively a series of images of the virtual object (showing, for example, rotation of the object about one or more axes) may be recorded on video tape. However, not only is special equipment needed to convert computer data to conventional video standards, but the resultant video images are typically of low resolution, and restrict an observer of the tape to watching a series of two-dimensional views of the virtual object chosen and fixed by the program's user, rather than allowing the observer to choose his own selection and sequence of views of the virtual object.
Holographic techniques can of course record full details of a three-dimensional virtual object and permit an observer to view the hologram as if it were a three-dimensional real object. However, holographic recording requires the use of a laser, and holograms of a type which can be viewed in white light display distracting color changes as the parallax of the hologram is observed.
Various techniques are known for recording three-dimensional images in lenticular media having one or more photosensitive layers. As early as 1908, Gabriel Lippman invented a method for producing a true three-dimensional image of a scene with vertical and horizontal parallax; see, for example, De Montebello, "Processing and Display of Three-Dimensional Data II" in Proceedings of SPIE, San Diego, 1984. In Lippman's method, a photographic plate is exposed through a "fly's eye" lens sheet, so that each lenslet forms a miniature image of the scene being reproduced, as seen from the perspective of the point on the sheet occupied by that lenslet. After the photographic plate has been developed, an observer looking at the composite image on the plate through the lenticular sheet sees a three-dimensional representation of the scene photographed; this representation will be in color if a color plate is used. If a lenticular sheet using hemicylindrical elongate lenticles is used instead of a fly's eye sheet, a similar three-dimensional image is seen, but this image has parallax in only one direction, across the length of the lenticles.
Unfortunately, because in Lippman's method the composite image has to be viewed from the same side of the lenticular screen as that on which the scene photographed originally stood, and because the image formed by the lenticles during exposure of the plate has undergone only a single inversion of each miniature image, the three-dimensional representation produced is pseudoscopic, that is to say the depth perception in the image is inverted so that the object appears "inside out". To overcome this problem, a number of variations of Lippman's method have been devised to achieve two inversions of each miniature image in order to provide an orthoscopic ("right side out") three-dimensional image; see, for example, U.S. Pat. No. 3,895,867. However, most of these variations of Lippman's method are complex, involving multiple exposures with a single camera, or multiple cameras or multi-lens cameras to record a plurality of views of the same object, and require extremely accurate registration of multiple images to provide a single three-dimensional image. Moreover, any method for producing three-dimensional images which relies upon conventional cameras necessarily requires the presence of a real object before the camera, and such a method is ill-adapted for producing three-dimensional images of a virtual object, since it is highly undesirable to have to produce a real copy of the virtual object merely in order to effect the imaging process.
Thus, there is a need for a method of producing a three-dimensional image of an object which can readily be applied to imaging of virtual objects without a need to first produce a real copy of the object.

Three-dimensional image, and methods for the production thereof


A buoyancy-based lifting system can be dynamically controlled to lift, move, or hold a load an object of arbitrary size at a fixed depth. The control system can control the trajectory of a flexible gas-filled lift bag and attached load by opening or closing inflation and deflation valves based on ambient pressure readings obtained during a lift. Stable control can be achieved and maintained without having to directly measure the actual volume of gas in the lift bag, and without having to accumulate measurements of gas flows into and out of the bag. A controller can pre-determine limits of instability and lift control parameters, then use this information in conjunction with ambient pressure readings to prevent the system from becoming unstable during a lift. User intervention is generally unnecessary to maintain the system's instability.

1. Technical Field
This disclosure relates generally to lifting loads using buoyancy-based lifting systems, and more particularly to controlling buoyancy-based lifts.
2. Description of Related Art
The marine salvage industry, off-shore oil & gas industry, nautical archeology, and military operations often use air lift bags to move or recover objects in bodies of water. Two types of lift bags exist: the open-bottom or parachute-type, and the enclosed type. Both types are constructed of flexible fabric and filled with air, another gas, or sometimes another lighter-than-water fluid, to create a buoyant force to lift an object. Rigid, fixed volume devices, such as ballast tanks have also been used for buoyant lifts.
Conventional flexible lift bag systems tend to become unstable during a lift, because the partially-inflated lift bag changes volume inversely with depth, and therefore tends to accelerate upward or downward when displaced even slightly from a position of neutral buoyancy. The risks of instability include diver entanglement in a rapid, uncontrollable ascent or descent, potentially causing injury or death. Also, the lift bag, and load being lifted, may broach the surface at high speed, possibly causing the loss of gas from an open-bottom bag, followed by uncontrolled descent. The high speed ascent or broaching itself may damage the object being lifted. Using lift bags to overcome seabed suction, or to free mechanically-locked or snagged equipment, can also be problematic, as the amount of buoyant force needed to lift the load becomes suddenly less as soon as the load is freed.
In practice, elaborate precautions are often needed in lift-bag operations, such as dead-man anchors and restraining lines, and/or vertically-staged multiple lift-bag arrays which prevent the load from going up in an uncontrolled fashion.
Although rigid volume lifting devices, such as ballast tanks may not suffer from the volume-change instability of flexible lift bags, the rigid volume devices can be excessively cumbersome due to their large size and weight, making them more difficult to transport than flexible lift bags.


Cutting tool has a substrate and a multilayer coating deposited by PVD. The coating comprises a base layer of one or more identical or different layers of a nitride or carbonitride which contains at least aluminium (Al) and a chromium-containing, oxidic functional layer. Attachment of the chromium-containing functional layer is improved by an intermediate layer of one or more oxides or oxide nitrates of the metals Al, Cr, Si, and/or Zr provided between the base layer and the functional layer. The intermediate layer has a cubic structure and the chromium-containing functional layer is selected from chromium oxide (Cr2O3), chromium oxynitride, aluminium-chromium oxide (AlCr)2O3, aluminium-chromium oxynitride or a mixed oxide or mixed oxynitride of aluminium, chromium and further metals of (AlCrMe1, Men)2 oxide or (AlCrMe1, Men)2 oxynitride, where Me . . . Men means one or more further metals, selected from Hf, Y, Zr and Ru, and wherein the functional layer has a rhombohedral structure.

Cutting tools which are used for example for metal-removing metal-machining as a rule consist of a base (substrate) of hard metal carbide, cermet, steel or high-speed steel with a wear-resistant single-layer or multi-layer coating of hard metallic substances, oxide layers and the like. Such coatings are applied using CVD (chemical vapour deposition) processes and/or PVD (physical vapour deposition) processes.
From EP 1 253 215 it is known for a multi-layer coating with a base layer of TiAlN and a functional layer of aluminium oxide or aluminium-chromium oxide to be deposited on a hard metal carbide substrate using the PVD process. Here, aluminium oxide is deposited with the single magnetron process during which gamma aluminium oxide is produced predominantly. Aluminium-chromium oxide is deposited using the arc PVD process, producing stable alpha aluminium-chromium oxide, but this has poor bonding to the underlying TiAlN base layer, and depending on the process large numbers of macro particles, so-called droplets, are formed which severely impair the quality of the functional layer.
DE 10 2010 028 558 describes a hybrid PVD process for depositing aluminium-chromium oxide mixed crystal layers in which the cathode atomisation and arc evaporation PVD processes are used simultaneously. Aluminium-chromium oxide mixed crystal layers are obtained predominantly in the stable alpha phase, which are essentially free of macro particles (droplets).
According to the known processes representing the state of the art, it is possible to produce aluminium oxide, aluminium-chromium mixed oxide or mixed oxides with further alloying elements in the stable alpha modification. However, these layers are characterised by poor bonding to the underlying substrate, for example a nitridic base layer, such as a TiAlN layer. The provision of such a base layer is desirable because oxide layers deposited directly onto the surface of the substrate are frequently too brittle to function as a wear prevention layer.

Tool with chromium-containing functional layer


A simulation device and a system and method for using the simulation device are disclosed. The simulation device may contain a plurality of antenna elements positionable on or near a radar or other sensing device. The simulation device may be configured to control the plurality of antenna elements to transmit signals that simulate a reflection of an electromagnetic signal off of one or more targets of particular sizes at particular azimuths, elevations, distances, trajectories, and/or velocities.

In recent years, advances in the accuracy and portability of sensing and radar systems have led to their increased use in the detection of target objects. As a result, more people now rely on the accuracy of these systems than ever. For example, the portability and accuracy of the Lightweight Counter-Mortar Radar (LCMR) system has led to its increased use in field operations. People stake their lives on the accuracy of these radar systems when used in the field. As such, testing an LCMR system for accuracy is of utmost importance.
FIG. 1 illustrates a real-world application of an LCMR system in the field. LCMR systems are used to detect and locate one or more moving objects and to calculate a prior location of the one or more moving objects. One typical application of an LCMR system is to determine the firing locations of launchers. Portable LCMR systems can be transported into the field by vehicles or parachutes, or can be disassembled and carried by one or more individuals. Once in the field, an LCMR system can quickly be assembled. In the illustration of FIG. 1, LCMR system 10 provides 360-degree surveillance by scanning with a cylindrically phased array antenna 12 mounted on a tripod 14. Antenna 12 scans the surrounding area by generating beams of radio frequency radiation 15. When an object 16 is within the field of the LCMR system, the beam of radiation is reflected off of the object and reflected beam 17 is detected by LCMR system 10. The detected object is then tracked to determine the object's trajectory. A processor (not shown) then performs a calculation based on the trajectory to determine the location of a launcher 18 that fired the object. Having determined the location of firing launcher 18, appropriate action can be taken to disable launcher 18. Nevertheless, the accuracy of the location information generated by an LCMR system is important in taking these countermeasures. As such, LCMR systems need to be thoroughly tested before use.
One traditional method for testing LCMR systems and other sensing and radar systems involves live-fire testing. With live-fire testing, a real-world field scenario is created at an outdoor range. For example, testing personnel set up a launcher in a specific location on an outdoor range, fire a shell, and determine whether the LCMR system accurately determines the firing location. This testing scenario looks just like the real-world example in FIG. 1 with the exception that, rather than being operated in the field, the LCMR is operated on a controlled outdoor testing range. However, live-fire testing is suboptimal, because it is time consuming, harmful to the environment, and expensive, both in terms of the quantity of shells that need to be fired and in the amount of testing ground resources that need to be consumed.
FIG. 2 illustrates another method for testing sensor and radar systems, called "near field scanning." With near field scanning, an antenna probe 21 is moved to a position in a two-dimensional frame 22. The probe is moved along a vertical axis along a vertical arm 23 of the frame and a horizontal axis along a horizontal arm 24 of the frame. The probe moves around the frame to cover the whole array of the frame, similar to a raster scan. By probing the radiation from the sensor or radar system at the different locations, the near field scanner is able to characterize the beam pattern of the system. However, these near field testing systems are also suboptimal, because they only characterize the electric and magnetic fields of the antenna radiation and do not accurately test real-world applications of sensor and/or radar systems.
FIGS. 3a and 3b illustrate alternative approaches being used to test real-world applications of scanning and/or radar systems. FIG. 3a illustrates a mechanical live-fire test set (MLFTS) for testing an LCMR system. Using this approach, LCMR system 10 is taken off of its tripod stand and placed on a rotator device 31. A vertical motion rail 32 with a controllable antenna probe 33 is placed in the field of LCMR system 10. A target object can be simulated at various elevations by controllably moving antenna probe 33 vertically up and down motion rail 32. Various azimuths of the target object can be simulated by rotating LCMR system 10 with rotator device 31. In testing a simulated target object at a specific desired location, rotator device 31 rotates LCMR system 10 to a desired azimuth and motion rail 32 moves probe antenna 33 vertically to the desired elevation. LCMR system 10 then sends a beam of radio frequency radiation 34 into the field, where it is detected by antenna probe 33. Antenna probe 33 acts as a repeater and transmits a beam of radio frequency radiation 35 that is calibrated to simulate the reflected radiation off of the simulated target and back to LCMR system 10.
FIG. 3b illustrates an electronic live-fire test set (ELFTS) for testing an LCMR system 10. The ELFTS operates similarly to the MLFTS, but uses a column of antenna elements 41 rather than a single antenna probe on a motion rail. When an antenna element at a particular vertical placement along the electronic rail, location 42 for example, detects a radiation beam 43 from LCMR system 10, the antenna element at location 42 acts as a repeater and transmits a beam of radio frequency radiation 44 that is calibrated to simulate the reflected radiation off of the simulated target back to LCMR system 10.
While the MLFTS and ELFTS testing approaches are improvements over prior sensor and/or radar testing approaches, they still have significant costs and inefficiencies associated with them. For example, MLFTS and ELFTS testing is performed in an anechoic chamber in order to mitigate electronic interference from the environment. These chambers must be large to accommodate the radar structure and testing apparatus, are expensive to create, and require LCMR systems to be transported to the chamber facility. Furthermore, radar target simulation using antennas normally requires that the injection antenna be placed in the radar antenna far-field. If the target trajectories involve high elevation angles, an impractically tall injection antenna support is needed. This is especially true for high radar bands and/or large radar apertures. As a result, the motion rail of the MLFTS must be very tall in height and cannot be easily transported to different locations. The vertical column of antenna elements of the ELFTS has been modified into ruggedized, all-weather versions that can be disassembled for transport into the field. Nevertheless, these versions require a great deal of time and effort in setup, as the column of antenna elements must be assembled to great height and the LCMR system must still be placed on a rotator device in the field.
Accordingly, there is a need for a portable, efficient, and inexpensive approach for testing LCMR systems and other sensor and/or radar systems that can be used to more easily test these systems in a variety of desired locations. There is also a need for a system and method for variable geometry moving target injection that is compact and that does not compromise normal radar operation. Furthermore, there is a need to broaden the scope and application of radar testing systems and methods to more sensor and target types both inside and outside anechoic chambers.
The systems and methods of the present disclosure address one or more of the problems set forth above.

Systems and methods for near field target simulation


The present invention relates to an anthrapyridone compound represented by the following formula (1):

In the recording method using an inkjet printer which is one of the typical methods among various color recording methods, various methods for discharging ink have been developed, and in any of them, ink droplets are generated and adhered onto various record-receiving materials (such as paper, film and cloth) to perform recording. This has been rapidly prevailing lately and is expected to continue growing remarkably in the future because of features such as quietness without noise generation due to no contact of a recording head with a record-receiving material and as easiness in downsizing, speeding up and colorizing.
Conventionally, as an ink for fountain pens, felt-tip pens or the like and as an ink for inkjet recording, water-based inks where a water-soluble dye is dissolved in an aqueous medium have been used. To these water-based inks, a water-soluble organic solvent is generally added in order to prevent ink from clogging at a pen tip or an inkjet nozzle. These conventional inks are required to provide recorded images with sufficient density, not to clog at a pen tip or a nozzle, to dry quickly on a record-receiving material, to bleed less, to have an excellent storage stability, and so on. In addition, formed images are required to have fastnesses such as water fastness, light fastness and moisture fastness.
Meanwhile, images or character information on color displays of computers are generally expressed by subtractive color mixing of 4 color inks of yellow (Y), magenta (M), cyan (C) and black (K), for color recording by an ink jet printer. In order that images expressed by additive color mixing of red (R), green (G) and blue (B) on CRT displays and the like is reproduced, as faithfully as possible, with images expressed by subtractive color mixing, it is desired that each of Y, M and C has a hue as close to each standard as possible and is also vivid. In addition, it is required that ink compositions are stable in storage for a long period of time, and that images printed therewith have a high concentration and also said images are excellent in fastnesses such as water fastness, light fastness, and gas fastness.
The application of inkjet printers has been widely spread in the fields ranging from small printers for office automation to large printers for industrial use, and therefore fastnesses such as water fastness, moisture fastness, light fastness and gas fastness have been required more than ever.
Water fastness has been largely improved by coating a paper surface with inorganic particles which can absorb the coloring matter in an ink, such as porous silica, cation polymer, aluminasol, special ceramic and the like, together with a PVA resin.
"Moisture fastness" means durability against a phenomenon that the dye in a record-receiving material bleeds during storage of the colored record-receiving material under an atmosphere of high humidity. Dye bleeding extremely deteriorates image quality of images particularly required to have a photo-like and high resolution image quality, and therefore it is important to reduce such bleeding as far as possible.
As for light fastness, any technique for large improvement thereof has not established yet. In particular, many of coloring matters for magenta among 4 primary colors of Y, M, C and K originally have low light fastness, and therefore improvement thereof is an important problem. In addition, with recent spread of digital cameras, there are more opportunities to print pictures at home, and image discoloration by oxidizing gas in the air where printed matters obtained are stored is acknowledged as a problem. The oxidizing gas reacts with dyes on or in a recorded paper, causing discoloration or fading of the printed image. Among oxidizing gasses, ozone gas is regarded as a causative agent accelerating color-fading phenomenon of inkjet-recorded images. This phenomenon of discoloration or fading is characteristic of inkjet images, and therefore improvement of ozone gas fastness is also an important problem.
As a magenta coloring matter used in water-based inks for inkjet recording, typical are xanthene-based coloring matters and azo based coloring matters using H acid. However, xanthene-based coloring matters are very excellent in hue and vividness but very inferior in light fastness. On the other hand, some of the azo-based coloring matters using H acid are good in terms of hue and water fastness, but many are inferior in light fastness, gas fastness and vividness. As for this type, a magenta dye excellent in vividness and light fastness has been developed but it still has a low level in light fastness compared with dyes having a different hue such as a cyan dye represented by a copper phthalocyanine-based coloring matter and a yellow dye.
Examples of the magenta coloring matter excellent in vividness and light fastness include an anthrapyridone-based coloring matter (see, for example, Patent Literatures 1 to 12), but a coloring matter for magenta satisfying all the requirements for hue, vividness, light fastness, water fastness, gas fastness and solution stability has yet to be obtained.
In particular, Patent Literatures 9 and 12 disclose a compound having a structure of cross-linking two molecules of anthrapyridone compounds with a cross-linking group, and an ink composition containing said compounds.    Patent Literature 1: JP H10-306221 A (pp. 1 to 3 and 7 to 18)    Patent Literature 2: JP 2000-109464 A (pp. 1 to 2 and 8 to 12)    Patent Literature 3: JP 2000-169776 A (pp. 1 to 2 and 6 to 9)    Patent Literature 4: JP 2000-191660 A (pp. 1 to 3 and 11 to 14)    Patent Literature 5: JP 2000-256587 A (pp. 1 to 3 and 7 to 18)    Patent Literature 6: JP 2001-72884 A (pp. 1 to 2 and 8 to 11)    Patent Literature 7: JP 2001-139836 A (pp. 1 to 2 and 7 to 12)    Patent Literature 8: WO 2004/104108 (pp. 20 to 36)    Patent Literature 9: JP 2003-192930 A (pp. 1 to 4 and 15 to 18)    Patent Literature 10: JP 2005-8868 A (pp. 1 to 3 and 15 to 22)    Patent Literature 11: JP 2005-314514 A (pp. 1 to 3 and 15 to 20)    Patent Literature 12: WO 2006/075706

Anthrapyridone compound or salt thereof, magenta ink composition containing the same, and colored product

Abstract: wherein, R represents a hydrogen atom, an alkyl group, a hydroxy lower alkyl group, a cyclohexyl group or a (mono- or di-alkylamino) alkyl group, X represents a cross-linking group represented by the formula:—NH—(CH2)n-NH—  (201)wherein, n is 2 to 8and another cross-linking group, respectivelyor a salt thereof, a magenta ink composition containing the anthrapyridone compound, and a colored product therewith; said compound has a hue having a high vividness suitable for inkjet recording, a recorded matter therewith has strong fastnesses particularly such as light fastness and ozone fastness, and the ink composition has an excellent storage stability, whereby said compound is useful as a magenta coloring matter suitable for inkjet recording.


A paste composition for solar cell electrodes includes conductive particles, a glass frit, an organic binder and a solvent. The conductive particles include at least two groups of conductive particle having different particle diameter distributions. The conductive particle may have an average particle diameter (D50′) of about 1.85 μm or less and a particle diameter (D90′) at 90% of the cumulative particle diameter distribution of about 3.10 μm or less.

1. Field
Embodiments relate to a paste composition for solar cell electrodes, an electrode fabricated using the same, and a solar cell including the same.
2. Description of the Related Art
A sintering type paste for solar cell electrodes may be prepared under different optimal sintering conditions, depending on the surface treatment of a silicon substrate, the formation of an anti-reflection layer, and the unevenness of the thickness of an emitter layer.

Paste composition for solar cell electrode, electrode fabricated using the same, and solar cell including the same