An electro-optical modulator is disclosed that has a microwave input, chip with a thin film resistor or a lumped resistor located between an input RF connector and an RF electrode on a Lithium Niobate chip. The accessory connection chip has a broadband attenuator like a thin film resistor which is placed in a microstrip line for effecting the electrical transmission to Lithium Niobate chip. The insertion of the thin film resistor before the RF electrode lowers the electrical return loss value as a function of frequency, allowing a lower driving voltage design or a reduced chip length without degrading the performances.

1. Technical Field of the Invention
The invention relates generally to the field of fiber optics and more particularly to electro-optical modulators.
2. Description of Related Art
Electro-optical modulators in a recent trend are moving toward conjugating smaller dimensions and lower driving voltages to enable system vendors to design their opto-electronic boards, e.g. transponders, by adopting smaller footprints, with inexpensive and low power electronic components. Conventional solutions employ three design techniques for reducing a RF driving voltage in a Lithium Niobate ("LN") travelling wave modulator: (1) adopting a longer RF electrode, and thus resulting in a longer, instead of a shorter, chip; (2) decreasing the buffer-layer thickness, resulting in an overall worsening of the performances; and (3) decreasing the gap width between hot and ground electrodes of the CoPlanar transmission line, resulting once more in an overall worsening of the performances.
Each of these three techniques has shortcomings. First, if the RF electrode is lengthened, the chip and package dimensions in turn must be lengthened. In addition, the total electrical losses increase, thereby decreasing the electro-optical bandwidth. Thus, such a solution is not suitable for designing metro application-oriented components. Second, if the buffer-layer thickness is decreased, the electro-optical bandwidth also decreases due to the total electrical losses increasing and microwave effective refractive index being more difficult to be matched to the optic. Furthermore, the characteristic impedance of the microwave lines becomes worse, rendering more difficult to have a good electrical return loss vs. frequency profile. A good impedance matching between the driver output port and the modulator input port is desirable for a correct working of the entire transmission chain. A typical specification for the electrical return loss of the modulator (S11 parameter) is <−10 dB over the whole operating bandwidth. Third, if the gap width is decreased between hot and ground electrodes of the CoPlanar transmission line, the electro-optical bandwidth decreases due to the increasing in total electrical losses, while the characteristic impedance of the microwave lines becomes worse. A graphical diagram 100 in FIG. 1 illustrates typical profiles of S11 parameters versus frequency for a standard x-cut modulator, which shows values well below the required specification, i.e. −10 dB.
Accordingly, there is a need to design a system for reducing the electrical return loss of Lithium Niobate traveling wave electro-optical modulators with low characteristic impedance.

System for reducing the electrical return loss of a lithium niobate traveling wave optical modulator with low characteristic impedance


An x-ray inspection apparatus includes a sample image obtaining unit, an ideal curve generating unit, a curve adjustment unit, and a mass estimation unit as a function block generated by a control computer. The sample image obtaining unit obtains 10 x-ray transmission images of sample inspected products each of whose mass is known in advance. The ideal curve generating unit generates a table based on a formula that indicates a relationship between the brightness of an area included in the x-ray transmission images and the estimated mass of the area. The curve adjustment unit refers to the input actual mass of each x-ray transmission image and adjusts the table such that the estimated mass approximates the actual mass. The mass estimation unit determines the estimated mass per unit area based on the post-adjusted table and adds up these masses to determine the total estimated mass of the product.

In recent years, an x-ray mass estimation apparatus is used in which x-rays are irradiated to a measurement target object and the mass of the measurement target object is estimated (calculated) based on the amount of x-rays transmitted through the measurement target object.
With this x-ray mass estimation apparatus, an x-ray transmission image of the measurement target object is obtained, and then, by utilizing a characteristic that the image appears darker when the thickness of material in the x-ray transmission image is larger, the mass of the measurement target object is estimated according to the brightness per unit area included in the x-ray transmission image, for example, when the brightness is low, the mass is large, and when the brightness is high, the mass is small.
Specifically, given that the image brightness when there is no material is I0, the image brightness of a portion where x-rays are transmitted through material is I, and the thickness of material is t, a relationship among these factors is expressed by the following relational expression (1).I/I0=e−μt  (1)
Here, the value μ denotes a linear mass coefficient determined by x-ray energy and the type of material, indicating that the higher the value is, the greater the amount of x-rays that is absorbed.
Also, in order to estimate the thickness of the material from the brightness of the image, the following relational expression (2) is used.t=−1/μ×ln(I/I0)  (2)
In order to convert these values to the mass m, the following relational expression (3) is used in which an adequate coefficient is used as a multiplication factor.m=ct=−c/μ×ln(I/I0)=−α ln(I/I0)  (3)
(Note that the value "c" denotes a coefficient for converting the thickness of the material to the mass m)
Typically, an x-ray transmission image is formed by a plurality of pixels, thus it is possible to estimate the mass of the entire material by determining the mass m for each pixel and adding up these masses for the entire image. This can be expressed by the following formula (4).M=ΣΣm(x,y)  (4)
For example, in the Japanese Laid-Open Patent Application Publication No. 2002-296022 (published on Oct. 9, 2002), an x-ray mass estimation apparatus is disclosed, in which x-rays are irradiated to the measurement target object; x-rays transmitted therethrough are detected; the mass of the measurement target object is calculated per unit transmission area based on the amount of transmitted x-rays from a predetermined formula; and the calculated unit mass of the measurement target object per unit transmission area is integrated over the entire x-ray transmission area.


According to various embodiments, a method for an electronic device includes receiving an input of a first word from a keypad, recognizing a voice input and converting the voice input into a text including a second word, in response to determining that the second word is erroneously recognized based on the first word, correcting the text by replacing the second word with the first word, and entering the corrected text. An electronic device for recognizing a voice includes a keypad configured to receive an input of a first word, a sensor configured to recognize a voice input, a controller configured to convert the voice input into a text including a second word, in response to determining that the second word is erroneously recognized based on the first word, correct the text by replacing the second word with the first word, and enter the corrected text.

Electronic devices have become necessities of modern people since they are easily carried, and the electronic devices have developed as multimedia devices that provide various services such as voice and video call, message transmission and reception, information input/output function, and data transmission.
The electronic device may input text using a keypad, and may input text using voice recognition.

Method of controlling a text input and electronic device thereof


An alarm device for use with a vehicle includes an input connector for electrical connection with a vehicle wiring harness of a vehicle, an output connector for electrical connection with a trailer lighting receptacle of a trailer, and an alarm circuit electrically connected in series between the input connector and the output connector. The alarm circuit is configured to detect a presence or absence of an electrical signal supplied to the input connector for delivery through the output connector to an electrically powered component of the trailer. The alarm circuit is configured to deliver an alert signal when the alarm circuit detects the absence of the electrical signal.

Trailers can be designed to couple or otherwise attach to a truck, sports utility vehicle, or other such vehicle capable of towing the trailer. Trailers can be designed for towing large and heavy items and as a result, trailers often carry valuable items. For example, trailers often are used to tow boats, automobiles, all terrain vehicles, motorcycles, and commercial goods. Such goods and items are often transported across large distances. During such a trip, the vehicle and the attached trailer carrying the valuable items are often left unattended while the driver stops to rest for the night or eat a meal. Such circumstances leave the trailer and cargo susceptible to theft.
The trailer itself can also be a valuable item. Many trailers are designed for a specific purpose, such as towing a boat or a pair of wave runners, and, as a result, can be relatively expensive. Boats or wave runners are often towed to a lake or other such body of water, removed from the trailer, and put into use. This leaves the vehicle and the trailer coupled to the vehicle unattended and a potential target of theft.


The application relates to a method for analyzing, in particular for imaging, and/or processing of an object as well as a particle beam device for carrying out this method. In particular, the particle beam device of this application is an electron beam device and/or an ion beam device. The method in particular comprises the control unit providing a first control parameter, wherein a beam guiding unit is controlled using the first control parameter for guiding the particle beam and/or wherein a moving unit is controlled using the first control parameter for moving an object holder, correlating a position of the object holder in a second coordinate system to the object position on the surface of the object, identifying a first coordinate transformation between the first coordinate system and the second coordinate system, identifying an orientation position of a distinctive feature on the surface of the object and identifying first coordinates of the orientation position in the first coordinate system, the control unit providing a second control parameter, wherein the second control parameter is used for at least one of: controlling the beam guiding unit for guiding the particle beam, controlling the moving unit for moving the object holder or controlling a detector, identifying again the orientation position of the distinctive feature and identifying second coordinates of the orientation position in the first coordinate system, comparing the first coordinates with the second coordinates, identifying a local displacement of the first coordinates to the second coordinates, identifying a second coordinate transformation using the first coordinate transformation and the local displacement and identifying a position of an area to be analyzed and/or processed on the surface of the object.

Particle beam devices are used for examining samples (hereinafter also called objects) in order to obtain insights with regard to the properties and behaviour of the samples under specific conditions. One of those particle beam devices is an electron beam device, in particular a scanning electron microscope (also known as SEM) or a transmission electron microscope (also known as TEM).
In the case of an SEM, an electron beam (hereinafter also called primary electron beam) is generated using a beam generator. The electrons of the primary electron beam are accelerated to a predeterminable energy and focused by a beam guiding system, in particular an objective lens, onto a sample to be analyzed (that is to say an object to be analyzed). A high-voltage source having a predeterminable acceleration voltage is used for acceleration purposes. Using a deflection unit, the primary electron beam is guided in a raster-type fashion over a surface of the sample to be analyzed. In this case, the electrons of the primary electron beam interact with the material of the sample to be analyzed. In particular, interaction particles and/or interaction radiation arise(s) as a consequence of the interaction. By way of example, electrons are emitted by the sample to be analyzed (so-called secondary electrons) and electrons of the primary electron beam are backscattered at the sample to be analyzed (so-called backscattered electrons). The secondary electrons and backscattered electrons are detected and used for image generation. An image of the sample to be analyzed is thus obtained.
Furthermore, it is known from the prior art to use combination devices for processing and/or for analyzing a sample, wherein both electrons and ions can be guided onto a sample to be processed and/or to be analyzed. By way of example, it is known for an SEM to be additionally equipped with an ion beam column. Using an ion beam generator arranged in the ion beam column, ions are generated which are used for processing a sample (for example for removing a layer of the sample or for applying material to the sample) or else for imaging. In this case, the SEM serves, in particular, for observing the processing, but also for further analysis of the processed or non-processed sample.
It is desirable to exactly identify, on the surface of the object, the position of the area(s) which is/are to be analyzed or processed. If the position is exactly known, the particle beam of a particle beam device can be guided to this position such that only this area or those areas are analyzed and/or processed. Additionally or alternatively it is known to position the object and, therefore, the area on the surface of the object to be analyzed and/or processed with the best possible precision in the particle beam device such that the particle beam can be guided to the area. It is known to arrange the object on an object holder which is also known as a stage. The object holder is transitionally movable in three directions which are oriented perpendicular to each other. Additionally, the object holder may be rotated around a first rotation axis and/or a second rotation axis, the axes being oriented perpendicular to each other.
For positioning the object holder and, therefore, also the object to be analyzed and/or processed, the object holder is moved in such a way that, for positioning the object to a specific position, the object holder is moved to a specific position which is given by coordinates of a coordinate system. It should be noticed that several coordinate systems in a particle beam device might be relevant for positioning the object, wherein the coordinate systems are related to each other. As a matter of fact, each assembly unit of a particle beam device has its own coordinate system. The object to be analyzed and/or processed also has its own coordinate system.
A specific position on the surface of the object to be analyzed and/or processed has first coordinates in the coordinate system of the object which correspond to second coordinates in the coordinate system of the object holder, wherein the first coordinates and the second coordinates do not have to be identical with respect to their absolute values. For adjusting to a specific position on the surface of the object, it is known to use a coordinate transformation with respect to the above mentioned two coordinate systems and/or further coordinate systems which might be relevant.
When adjusting the object to a specific position by using the object holder, errors might occur. Due to mechanical errors with respect to the object holder or with respect to the movable parts of the object holder and due to the weight of the object on the object holder, movements of the object holder might occur, which do not allow an accurate positioning of the object and/or guiding the particle beam to the object. It may not be possible to determine the values of such errors, for which reason they may be irreproducible. However, they should be considered when positioning the object.
An exposure method for drawing a pattern on a substrate using a charged particle beam device is known. The method includes a detection step of placing a calibration substrate having a plurality of marks on a stage and detecting positions of the plurality of marks by a first position detection section using a charged particle beam and by a second position detection section using light while adjusting a position of the stage, and a correction step of correcting a position where the charged particle beam is incident on the substrate on which the pattern is to be drawn, in accordance with the position of the stage on the basis of the difference between the results detected by the charged particle beam, on one hand, and by the light in the detection step, on the other hand.
It is referred in particular to references US 2009/0039285 A1 and U.S. Pat. No. 6,864,488 B2 as prior art.
A particle beam device providing a particle beam comprising charged particles may be operated using different beam parameters which influence the characteristics of the particle beam. Such beam parameters are, for example, an acceleration voltage influencing a landing energy of the charged particles, the landing energy being the energy which the charged particles have when impinging on the object, a beam current of the particle beam which impinges on the object and voltages of the electrode units used for deflecting and/or shaping the particle beam. Those parameters and further parameters not mentioned here may influence the particle beam.
As mentioned above, an image of a surface of an object may be obtained using a particle beam. The image may be used to identify an area of the surface which is going to be analyzed and/or processed. However, after having identified the area using first beam parameters characterizing a first operation mode of the particle beam device, it might be necessary to change the first beam parameters used for operating the particle beam device into second beam parameters characterizing a second operation mode. The second beam parameters are used to analyze and/or to process the identified area on the object. For example, a lower or higher beam current has to be chosen to achieve a specific effect on the area. Furthermore, the acceleration voltage may be varied to achieve a specific effect. However, it has been discovered that the image characteristics of the particle beam are often changed when varying the beam parameters. In particular, it may happen that a local displacement in the image may occur. In other words, the area on the surface of the object, which has been identified and is to be analyzed and/or processed, cannot be found at coordinates in the second operation mode of the particle beam device which coordinates were identified in the first operation mode of the particle beam device. If this local displacement is not considered, the particle beam of the particle beam device being in the second operation mode may be guided to an area which has not been identified before. Therefore, a wrong area on the surface of the object may be analyzed and/or processed. It may not be possible to determine the values of such local displacements, for which reasons they may be irreproducible. However, they should be taken into consideration.
Therefore, it is desirable to provide a method and a particle beam device for carrying out the method, which method and particle beam device allow for guiding a particle beam device to an identified area on the surface of an object, even if beam parameters of the particle beam device are varied.

Method for analyzing and/or processing an object as well as a particle beam device for carrying out the method


A foldable bicycle designed so when the bicycle is folded, the front and rear frames bypass each other (non-overlapping) to permit a complete folding position and using a fold on or near the seat tube, and to maintain a rigid open riding position with simple standard fold restraining devices.

A. Field of the Invention
This invention relates to a foldable bicycle that folds on or near the seat tube having non-overlapping front and rear frames and using quick release clamps or other means to lock a front and a rear frame together in the open riding position. In this application, the term "quick release" or other locking devices are referred to as restraining devices.
B. Prior Art
Many folding bicycles such as the Dahon, U.S. Pat. No. 4,067,589, require many folding steps while setting the folding axis in the middle of the structural members making a bicycle that is too complicated to fold and structurally weak. To date the strongest folding bicycles have been those that fold about the seat tube using a minimum number of quick release levers. U.S. Pat. No. 4,448,437 and U.S. Pat. No. 4,900,047 define a fold about the seat tube construction, with the rear member collared about the front member and the seat post attached to the front member.
Other bicycles, such as the Bridgestone "Grandtech", U.S. Pat. No. 4,579,360, employ the fold about the seat tube concept and involved only a few steps to fold the bicycle but had to sacrifice the strength of the open bicycle by distorting the seat post to achieve the limited number of folding steps. Likewise, U.S. Pat. No. 5,222,751 uses the concept defined in U.S. Pat No. 4,448,437 by having the same bottom bracket area collar as shown in FIG. 2B of U.S. Pat. No. 4,448,437. The design has a collared bent seat tube attaching a front and a rear frame, at the bottom near the crank and at the top near the seat tube.
All of these bicycles and tandems, including the prior configurations of the present inventor, had front and rear frames that partially or completely overlapped each other. U.S. Pat. No. 4,448,437 shows both the condition where the front frame surrounds the rear frame and where the rear frame surrounds the front frame. The current application has the front and rear frames partially overlapping. U.S. Pat. No. 4,579,360, Bridgestone's "Grandtech" has the back frame surrounding the front frame and U.S. Pat. No. 5,222,751 has the two frames overlapping.
There are however still areas for design improvement, to reduce the number of components, to increase strength of the frame and to enhance and simplify the folding operation. In this application a novel non-overlapping frame design of this invention has neither the front nor the back frame overlapping the other. The hinge points or restraining points may project into the opposite frame area but they are not the basic mass of the distinct frames. There are no other folding bicycles or tandems with non-overlapping back and front frames. There have been many recumbants and bicycles designed with a continuous single bar running from the head set to the back wheel axle, those that folded had a door type hinge in the middle, creating overlapping frames when folded. None of these had non-overlapping front and rear frames.


In a method of perceptual transform coding of audio signals in a telecommunication system, performing the steps of determining transform coefficients representative of a time to frequency transformation of a time segmented input audio signal; determining a spectrum of perceptual sub-bands for said input audio signal based on said determined transform coefficients; determining masking thresholds for each said sub-band based on said determined spectrum; computing scale factors for each said sub-band based on said determined masking thresholds, and finally adapting said computed scale factors for each said sub-band to prevent energy loss for perceptually relevant sub-bands.

An encoder is a device, circuitry, or computer program that is capable of analyzing a signal such as an audio signal and outputting a signal in an encoded form. The resulting signal is often used for transmission, storage, and/or encryption purposes. On the other hand, a decoder is a device, circuitry, or computer program that is capable of inverting the encoder operation, in that it receives the encoded signal and outputs a decoded signal.
In most state-of-the-art encoders such as audio encoders, each frame of the input signal is analyzed and transformed from the time domain to the frequency domain. The result of this analysis is quantized and encoded and then transmitted or stored depending on the application. At the receiving side (or when using the stored encoded signal) a corresponding decoding procedure followed by a synthesis procedure makes it possible to restore the signal in the time domain.
Codecs (encoder-decoder) are often employed for compression/decompression of information such as audio and video data for efficient transmission over bandwidth-limited communication channels.
So called transform coders or more generally, transform codecs are normally based around a time-to-frequency domain transform such as a DCT (Discrete Cosine Transform), a Modified Discrete Cosine Transform (MDCT) or some other lapped transform which allow a better coding efficiency relative to the hearing system properties. A common characteristic of transform codecs is that they operate on overlapped blocks of samples i.e. overlapped frames. The coding coefficients resulting from a transform analysis or an equivalent sub-band analysis of each frame are normally quantized and stored or transmitted to the receiving side as a bit-stream. The decoder, upon reception of the bit-stream, performs de-quantization and inverse transformation in order to reconstruct the signal frames.
So-called perceptual encoders use a lossy coding model for the receiving destination i.e. the human auditory system, rather than a model of the source signal. Perceptual audio encoding thus entails the encoding of audio signals, incorporating psychoacoustical knowledge of the auditory system, in order to optimize/reduce the amount of bits necessary to reproduce faithfully the original audio signal. In addition, perceptual encoding attempts to remove i.e. not transmit or approximate parts of the signal that the human recipient would not perceive, i.e. lossy coding as opposed to lossless coding of the source signal. The model is typically referred to as the psychoacoustical model. In general, perceptual coders will have a lower signal to noise ratio (SNR) than a waveform coder will, and a higher perceived quality than a lossless coder operating at equivalent bit rate.
A perceptual encoder uses a masking pattern of stimulus to determine the least number of bits necessary to encode i.e. quantize each frequency sub-band, without introducing audible quantization noise.
Existing perceptual coders operating in the frequency domain usually use a combination of the so-called Absolute Threshold of Hearing (ATH) and both tonal and noise-like spreading of masking in order to compute the so-called Masking Threshold (MT) [1]. Based on this instantaneous masking threshold, existing psychoacoustical models compute scale factors which are used to shape the original spectrum so that the coding noise is masked by high energy level components e.g. the noise introduced by the coder is inaudible [2].
Perceptual modeling has been extensively used in high bit rate audio coding. Standardized coders, such as MPEG-1 Layer III [3], MPEG-2 Advanced Audio Coding [4], achieve "CD quality" at rates of 128 kbps and respectively 64 kbps for wideband audio. Nevertheless, these codecs are by definition forced to underestimate the amount of masking to ensure that distortion remains inaudible. Moreover, wideband audio coders usually use a high complexity auditory (psychoacoustical) model, which is not very reliable at low bit rate (below 64 kbps).

Transform coding of speech and audio signals


A voltage control method includes producing an error signal based on a difference between a reference signal and an adaptor voltage and an adaptor current corresponding to the adaptor voltage, regulating, based on the error signal, the adaptor voltage, comparing a reference voltage to a voltage proportional to a potential corresponding to an identifying voltage corresponding to the adaptor voltage, detecting, based on the comparison result, whether or not a couplable external power source is suitable, and setting based, on the detection result, a potential corresponding to the identifying voltage.

Typical electronic devices are provided with a secondary battery as a drive power source. Such electronic devices include a charging circuit for charging the secondary battery using a charging current supplied from an external power source.
It is desirable that the main unit of an electronic device be able to control an AC adaptor to regulate the output voltage supplied from the AC adaptor to the main device. In this case, the AC adaptor includes a voltage regulating circuit, and a detection circuit included in the main device detects a voltage or the like to produce a control signal for controlling the voltage regulating circuit. Furthermore, since the main device needs to detect whether or not the coupled AC adaptor is suitable for the device, the AC adaptor outputs information identifying the AC adaptor to the main device. For example, the detection circuit of the main device monitors a voltage of the coupling terminal and determines whether or not the coupled AC adaptor is suitable for the device. The main device may not control an AC adaptor which is not suitable for the device, so the main device turns off a switch disposed in the power supply path to protect system circuits and the like of the main device.
In the above electronic device, the AC adaptor is coupled to the main device via, for example, a DC plug 90 illustrated in FIG. 1. In the DC plug 90, a cylindrical power terminal 92 is formed in the outer circumference surface of a cylindrical insulator 91; a cylindrical ground terminal 93 is formed in the inner circumference surface of the insulator 91; and a rod-like control terminal 94 is arranged at the axial center of the insulator 91. The length of the control terminal 94 is set shorter than the lengths of power terminal 92 and ground terminal 93 in a direction of inserting the DC plug 90. That is, the tip ends of the power terminal 92 and ground terminal 93 protrude further relative to the tip end of the control terminal 94. The AC adaptor outputs an identification signal via the control terminal 94 to the main device; and the main device outputs a control signal via the control terminal 94 to the AC adaptor.
As depicted in FIG. 1, the ground terminal 93 and power terminal 92, and then the control terminal 94 are electrically coupled in order to terminals of the main device. With this configuration, the signal (information) is supplied to the detection circuit of the main device after supplying the power supply voltage. Thus, in case the DC plug 90 coupled to the AC adaptor after the AC plug has been inserted in an AC outlet is coupled to the main device, the main device is prevented from being damaged. Such configuration in which coupling of the control terminal 94 is done after coupling of the power terminal 92 and ground terminal 93 is used not only by the DC plug 90 having this shape but also by a DC plug having another shape.
As further depicted in FIG. 1, in the above electronic device, during a period from coupling of the power terminal 92 and ground terminal 93 of the DC plug 90 to coupling of the control terminal 94, the terminal of the main device to be coupled to the control terminal is still not coupled. As a result, the potential of the terminal of the main device may become unstable, causing a malfunction.

Electronic device, detection circuit and voltage control method


In a radiological imaging apparatus, a radiation detecting section includes semiconductor detectors arranged in four columns and four rows. Each of the semiconductor detectors includes a semiconductor base material, and an anode electrode film (first electrode film) and a cathode electrode film (second electrode film) lying opposite each other so as to sandwich the semiconductor base material between them. A first conductive member is installed on each first electrode film. Second electrode films of four semiconductor detectors within a row are connected together using one second conductive member. A shaping amplifier connected to the first conductive members with a wire executes a waveform shaping process using a shaping time shorter than that of a shaping amplifier connected to the second conductive member with a wire; the first conductive members are provided for the four semiconductor detectors within a column.

The present invention relates to a radiological imaging apparatus comprising a semiconductor radiation detector which detects incident radiation to output a detection signal for it.
Semiconductor radiation detectors using Si, Ge, or CdTe collect both plural electrons and holes resulting from ionization in the detector substance caused by radiation to generate an electric signal (generally a voltage pulse). The semiconductor radiation detectors thus obtain information on the energy and incident timing of the radiation, the number of incident radiations, and the position of incidence.
Migration of charges in the semiconductor generates signal induced charges at a signal read electrode. Accordingly, if the charges are captured or recoupled owing to the level of impurities in the semiconductor, the charges do not contribute to the radiation signal having generated the charges. The phenomenon in which the signal becomes detective by the capture or recoupling is called a capture defect.
In a semiconductor radiation detector using a compound semiconductor device such as CdTe or HgI2, the mobility of holes is generally lower than that of electrons. Consequently, the time required to collect all the holes is insufficiently short compared to the lifetime of the holes before capture. When a long time is required to collect all the holes, a more serious capture defect occurs depending on the lifetime of the holes.
Since an anode collects the electrons, while a cathode collects the holes. Accordingly, when a radiation reaction position is close to the anode, the holes migrate a long distance before collection (a long time is required to collect the holes). As a result, the capture defect is most significant. In contrast, when the radiation reaction position is close to the cathode, the electrons must migrate a long distance before collection. However, owing to their high mobility, almost no capture defect occurs in the electrons. Further, only an insignificant capture defect occurs in the holes because they move only a short distance before collection.
Accordingly, the output signal varies depending on the interaction position of the radiation in the semiconductor. Different output signals thus result from the same input energy. This is a major cause of degradation of energy resolution.
To avoid the degradation of the energy resolution, a method corrects the capture defect by connecting two shaping amplifiers to the semiconductor radiation detector and using output signals from these shaping amplifiers for one radiation incidence event. That is, one of the shaping amplifiers has a shaping time that is insufficient for the charge collection time, to intentionally generate what is called a ballistic defect that is a signal defect correlated markedly with the capture defect. Thus, the pulse height values of the output signals from the shaping amplifiers are corrected for each event (see, for example, JP-A-61-14590 (Page 5, FIG. 1). This makes it possible to obtain a high energy resolution with a low applied voltage resulting in a significant capture defect, for a certain combination of mobility, lifetime, and anode-cathode distance.
JP-A-61-14591 (FIGS. 2(a) and 2(b)) describes a radiological imaging apparatus in which a plurality of semiconductor radiation detectors are arranged in a plurality of columns and a plurality of rows. In each column, the semiconductor radiation detectors contained in the column have first electrodes connected together using first interconnects. In each row, semiconductor radiation detectors contained in the column have second electrodes connected together using second interconnects. A shaping amplifier is connected to each of the plurality of first interconnects and the plurality of second interconnects. Outputs from these shaping amplifiers are input to a concurrency determining device. The outputs from the shaping amplifiers connected to the first interconnects are input to a main amplifier including an integrator and an amplifier to shape waveform and an auxiliary amplifier including a differentiator to shape waveform (the time constant of the auxiliary amplifier is smaller than that of the main amplifier). The radiological imaging apparatus described in JP-A-61-14591 compares the pulse heights of output signals from the main and auxiliary amplifiers to estimate a ballistic defect. The apparatus then uses the ballistic defect to correct the pulse height of the output signal from the main amplifier.
However, if semiconductor radiation detectors are installed in an actual apparatus, for example, a radiological imaging apparatus, it is indispensable to densely mount the semiconductor radiation detectors because of the need for both high positional resolution and high sensitivity. This makes it difficult to provide sufficient intervals between the electrodes of adjacent semiconductor radiation detectors. The inventors have thus found that this configuration may pose a new problem, that is, the occurrence of a large parasitic capacity. The occurrence of a large parasitic capacity degrades the characteristics of a process for shaping the waveform of waves from the shaping amplifiers connected to the electrodes. This precludes correction of the pulse height values of radiation detection signals.


A system and method for establishing a gaming session via cloud services with a first device, receiving information at the first device to establish a connection with a second device, and receiving at the first device instructions from the second device via the connection, wherein the instructions control an aspect of the gaming session.

A video game may provide in-game quests or challenges to players. The challenges may require the use of in-game tools by the player's in-game character for the player to, e.g., complete the challenge or achieve an objective. The video game may provide a variety of items, e.g., weapons, tools, health recovery items, etc., that may make the challenges more or less difficult to accomplish. The character may also have variable attributes, e.g., speed, strength, health, etc., that are adjustable by acquiring the items or otherwise. In-game features, such as map layouts, non-player characters, etc. may make game objectives more or less difficult to accomplish. The player may acquire items/characteristics over the normal course of the gameplay (e.g., by discovering the items), may purchase items/characteristics with in-game money (e.g., earned for various reasons during game play) or real-world money (e.g., through microtransactions), or may unlock items/characteristics (e.g., by defeating a boss character). In multiplayer games, items/characteristics may be tradable amongst characters, winnable from other characters, etc.
The gameplay experience for a player may be dependent on the aforementioned features. A player may wish for a gameplay experience that is more or less challenging or variable than current gameplay rules allow. Gameplay mechanisms exist where a character may find items/characteristics or be granted items/characteristics as, e.g., a reward for accomplishing objectives. However, these mechanisms are typically built into the standard gameplay of the game and are executed based on predefined rules of the gameplay.


A control system for monitoring and managing operation of a rotary disc cutterbar used in an agricultural machine. A controller in the system receives inputs on cutterbar drive power, machine travel speed, and crop cut quality. An operator interface allows suitable operational tolerances to be established. The controller examines crop cut quality, a determination of cut uniformity across the transverse width of the cutting swath, and determines changes in cutterbar drive speed and/or vehicle travel speed, if needed, to maintain crop cut quality within specified tolerances. Controller output may be directed to a display for instructing a machine operator to make necessary adjustments or it may initiate changes in machine subsystems to effect the necessary adjustments automatically.

This invention relates generally to a machine for severing standing crops from the ground to initiate a harvesting process and, more particularly, to a control system for monitoring the cutting quality of a rotary disc cutterbar and managing operational parameters for optimal cutterbar performance.
During crop cutting operations, a machine operator is tasked with observing the cut crop stubble to determine crop cut quality and altering cutterbar or machine parameters to achieve optimum cutting. The operator must also monitor cutterbar power and adjust machine and/or cutterbar parameters to prevent stalling the engine. These activities in addition to the primary task of piloting the machine through a field of standing crop may not always result in optimal crop cutting efficiency and can lead to operator fatigue.
Conventionally powered cutterbars typically include adjustments for rotational speed and cutting angle (a measure of the difference between the cutting plane and the ground). Machine travel speed may also be varied, typically as a means to manage the power necessary to operate the cutterbar. An electric motor driven rotary disc cutterbar is disclosed in Applicant's currently pending application Ser. No. 13/332,213. Advantages of a cutterbar with individual electric motor driven cutterheads include the capability to easily adjust rotational speed and rotational direction of the modules on the cutterbar. In order to fully realize the advantages of individually controllable disc cutter modules, a means for monitoring crop cutting performance and providing performance feedback to the module control is necessary.
It would be advantageous to have a system for monitoring the cutting performance of an agricultural rotary cutterbar and providing feedback to the machine operator, the control system, or a combination thereof so that cutting performance and vehicle operational efficiency may be optimized while making the task of machine operation easier for the machine operator. Still further advantages would be realized by a control system that enables the machine operator to pre-select specific operating parameters or operating parameter ranges based on previous performance and subsequently optimizes cutterbar operation within specific pre-defined operational ranges. Additional advantages would be realized by a control system capable of monitoring available inputs and controlling adjustable cutterbar performance parameters affecting crop cut quality and machine efficiency.

Control system for a disc cutterbar using stubble cut quality feedback


The universal input device provides a common user interface for a variety of different computing platforms including printed documents. Using the present system, one may use the universal input device to control various computing devices as well as capture handwritten electronic ink and have the electronic ink be associated with new or stored documents. The universal input device can be identified by a specific identification in order to allow for multiple users to operate on a document and/or within an application program simultaneously or not. An off-set optical system with infrared illumination handles perspective and helps detect positional encoding which can be covered by existing ink under common visible light illumination.

Computing systems have dramatically changed the way in which we live. The first wave of computers was prohibitively expensive, and was only cost effective for use in business settings. As computers became more affordable, the use of personal computers both in the workplace and at home have become so widespread that computers have become as common as desks in the office and kitchen tables in the home. Microprocessors have been incorporated in all aspects of our daily lives, from use in television and other entertainment systems to devices for regulating the operation of our automobile.
The evolution of computing devices, from data crunching devices that occupied entire floors of large office facilities, to laptop computers or other portable computing devices, has dramatically impacted the manner in which documents are generated and information is stored. Portable computing capabilities have enabled individuals to type letters, draft memorandum, take notes, create images, and perform numerous tasks in places other than the office using these computing devices. Professionals and nonprofessionals alike are empowered to perform tasks while on the move using devices that fulfill their computing needs in any location.
Typical computer systems, especially computer systems using graphical user interface (GUI) systems, such as Microsoft® Windows, are optimized for accepting user input from one or more discrete input devices such as a keyboard (for entering text), and a pointing device (such as a mouse) with one or more buttons for activating user selections.
One of the original goals of the computing world was to have a computer on every desk. To a large extent, this goal has been realized by the personal computer becoming ubiquitous in the office workspace. With the advent of laptop computers and high-capacity personal data assistants, the office workspace has been expanded to include a variety of non-traditional venues in which work is accomplished. To an increasing degree, computer users must become masters of the divergent user interfaces for each of their computing devices. From a mouse and keyboard interface for the standard personal computer to the simplified resistive stylus interface of personal data assistants and even to the minimalistic keys of a cellular telephone, a user is confronted with a variety of different user interfaces that one needs to master before he can use the underlying technology.
Despite the advances in technology, most users tend to use documents printed on paper as their primary editing tool. Some advantages of printed paper include its readability and portability. Others include the ability to share annotated paper documents and the ease at which one can archive printed paper. One user interface that is bridging the gap between advanced computing systems and the functionality of printed paper is a stylus-based user interface. One approach for the stylus-based user interface is to use resistive technology (common in today's PDAs). Another approach is to use active sensors in a laptop computer. One of the next goals of the computing world is to bring the user interface for operating the computer back to the user.
A drawback associated with the use of a stylus is that such devices are tied to the computing device containing the sensor board. In other words, the stylus may only be used to generate inputs when used in conjunction with the required sensor board. Moreover, detection of a stylus is affected by the proximity of the stylus to the sensing board.
Prior portable computing devices may lack a specific form of identification for multiple user configurations. As such, if two such portable computing devices operated simultaneously, a host computer becomes confused and senses the annotations to be from the same computing device. If one user annotates a document with the computing device and then a second user annotates the same document with a second computing device, the host PC that receives the data frames from the computing device interprets the data as originating from the same computing device. Without an ability to identify the computing device from which an annotation occurs, a host PC cannot track changes specifically to a particular computing device.
Prior portable computing devices may lack the ability to track writing that a user may perform on top of existing ink. Prior computing devices may track writing of a user on clean, ink free surfaces; however, the image capturing capabilities of these devices cannot track writing that occurs on existing ink. Further, prior portable computing devices may lack the ability to handle perspective that naturally exists when a writing implement, such as a pen, is held. An image sensor of an associated computing device operates efficiently when a user holds the computing device at an angle that is perpendicular to the writing surface. However, most individuals do not hold a pen at a 90 degree angle to a surface. As such, perspective becomes a problem for the sensor to adequately compensate for the angle of the computing device.
There is a need in the art for a portable computing device that may function as an input device for any one of a variety of computing devices and which may operate in a variety of situations. There is a further need in the art for a portable computing device that can be identified by a specific identification in order to allow for multiple users to operate on a document and/or within an application program simultaneously. Also there is a need in the art for a portable computing device that may decrease the effect of perspective in capturing images on a surface and may be configured to track writing by a user on existing ink.

Optical system design for a universal computing device


An optical transmitting device suitable for use in a wavelength division multiplexing optical transmission system for transmitting a plurality of optical signals different in wavelength through a transmission line. The optical transmitting device includes a plurality of electro-optical converters for respectively converting electrical signals into a plurality of optical signals different in wavelength, a plurality of pre-compensators for chromatic dispersion respectively connected to the plural electro-optical converters, for respectively giving certain chromatic dispersions to the plural optical signals, and an optical multiplexer connected to the plural pre-compensators for chromatic dispersion, for multiplexing the plural optical signals to which the certain chromatic dispersions have been given. Each pre-compensator for chromatic dispersion compensates for a chromatic dispersion difference in the transmission line due to a wavelength difference between a wavelength of each optical signal and a specific wavelength at which a chromatic dispersion in the transmission line becomes zero.

1. Field of the Invention
The present invention relates generally to a wavelength division multiplexing optical transmission system, and more particularly to an optical transmitting device suitable for use in this transmission system.
2. Description of the Related Art
In a conventional long-distance optical transmission system traversing the ocean over a distance of thousands of kilometers, a plurality of regenerative repeaters for converting an optical signal into an electrical signal and performing retiming, reshaping, and regenerating are used to transmit the optical signal. At present, however, an optical amplifier has been progressively put into practical use, and an optical amplification repeating transmission system using the optical amplifier as a linear repeater is examined. The replacement of the regenerative repeater by the optical amplification repeater allows a great reduction in number of parts in the repeater, ensuring of reliability, and expectation of a great reduction in cost.
Further, as one of methods for realizing a large capacity of an optical transmission system, attention is focused on a wavelength division multiplexing (WDM) optical transmission system for multiplexing a plurality of optical signals different in wavelength in one optical transmission line and transmitting the multiplexed optical signals in the optical transmission line. In a WDM optical amplification repeating transmission system configured by combining the WDM optical transmission system and the optical amplification repeating transmission system, it is possible to collectively amplify a plurality of optical signals different in wavelength by using optical amplifiers, so that large-capacity and long-distance transmission of optical signals can be realized with a simple configuration.
As a conventional wavelength division multiplexing optical transmission system, there has been proposed a report on an optical amplification repeating transmission test employing eight channels, a transmission speed per channel of 5 Gb/s (total capacity of 40 Gb/s), and a transmission distance of 8000 km (circular length of 1000 km) (OFC'95, PD19, N. S. Bergano et al. AT&T). In the above report, the wavelengths of the eight optical signals are set at regular intervals of 0.53 nm in the range of 1556.0 nm to 1559.7 nm, and channel numbers are allocated to these different wavelengths from the shorter wavelength side. A 1.5 .mu.m zero-dispersion fiber (dispersion-shifted fiber, DSF) and a 1.3 .mu.m zero-dispersion fiber (high-dispersion fiber, HDF) are used as a transmission line.
The dispersion in the dispersion-shifted fiber is -2 ps/nm/km in average at a wavelength of 1558 nm. The dispersion in the high-dispersion fiber can be estimated to about 20 ps/nm/km. A circular loop is constructed of an optical transmission line and twenty-two optical amplification repeaters and one signal light level compensating optical amplifier inserted in the optical transmission line. The repeater spacing is 45 km. The dispersion-shifted fiber is used in the first repeating section to the twentieth repeating section, and the high-dispersion fiber is used in the twenty-first and twenty-second repeating sections. After circulating the circular loop eight times, each optical signal is subjected to dispersion compensation (post-compensation) by using a dispersion compensating fiber (DEF) on the receiving side. The length of the dispersion compensating fiber for each channel (signal light wavelength) is adjusted in performing the dispersion compensation.
In the above report, a bit error rate of 2.times.10.sup.-10 is reached, and there is almost no system margin. To enlarge a system margin, a method of increasing the output light power of the optical amplification repeater may be considered. In this case, however, since this method is largely affected by a non-linear effect of the transmission line, it is important to design the chromatic dispersion in the transmission line in sufficient consideration of the non-linear effect. FIG. 18 shows a chromatic dispersion map in the case where the signal light wavelength is 1558.0 nm. As apparent from FIG. 18, a chromatic dispersion of -1800 ps/nm occurs upon 900 km transmission, and this chromatic dispersion can be subsequently compensated up to almost 0 ps/nm by using the high-dispersion fiber having a total length of 90 km. Thereafter, this pattern is repeated.
FIG. 19 shows a chromatic dispersion map of the signal light having a wavelength of 1556.0 nm as the first channel. As apparent from FIG. 19, a chromatic dispersion of -1960 ps/nm occurs upon 900 km transmission, but a chromatic dispersion of about -160 ps/nm remains even after performing the dispersion compensation by the use of the high-dispersion fiber having a total length of 90 km. Accordingly, the final chromatic dispersion upon 8000 km transmission reaches -1280 ps/nm. FIG. 20 shows a chromatic dispersion map of the signal light having a wavelength of 1559.7 nm as the eighth channel. As apparent from FIG. 20, the final chromatic dispersion upon 8000 km transmission reaches +1100 ps/nm.
Accordingly, the difference between the remaining chromatic dispersion of the first channel and the remaining chromatic dispersion of the eighth channel becomes 2000 ps/nm or more. In the case where the output light power of the optical amplification repeater is small enough, an allowable chromatic dispersion quantity can be obtained in no consideration of the non-linear effect, and there is almost no problem because the allowable chromatic dispersion quantity is relatively large. However, in the case where the output light power of the optical amplification repeater is large, the allowable chromatic dispersion quantity is affected by the non-linear effect to become small. Therefore, there is a limit in the chromatic dispersion compensation (post-compensation) on the receiving side as described in the above report.
FIG. 21 shows the wavelength dependence of transmission characteristics in the case where only the post-compensation for chromatic dispersion is performed. In FIG. 21, a minimum eye aperture deterioration obtained by optimizing a post-compensation quantity is shown. As apparent from FIG. 21, a large eye aperture deterioration occurs in wavelength regions shorter and longer than a reference wavelength of 1558 nm. However, the output of the optical amplifier is assumed as +4 dBm.
In a long-distance wavelength division multiplexing optical amplification repeating transmission system, a chromatic dispersion quantity in each channel is largely slipped during transmission by the influence of chromatic dispersion slope (secondary dispersion) even when the chromatic dispersion in the transmission line is divisionally compensated, because of different signal light wavelengths in all channels. While the above report shows that the chromatic dispersion compensation (post-compensation) is performed by giving an optimal chromatic dispersion quantity to each channel on the receiving side, there is a limit in the extent of improvement as mentioned above.

Wavelength division multiplexing optical transmission system and optical transmitting device used in the transmission system


Heptamethine cyanine fluorophore conjugates and conjugate precursors are disclosed. Methods of using the conjugates and conjugate precursors are also disclosed. The disclosed conjugates are neutral zwitterionic molecules and exhibit little or no aggregation.

Near-infrared (NIR) wavelengths can facilitate the visualization of biological processes in vivo. The use of fluorophore-labeled biomacromolecules is an enduring strategy employed across the spectrum of fundamental to applied biomedical science. However, fluorophore conjugation often alters the properties of both the fluorophore and the molecule to which it is attached. Specifically, important parameters such as brightness, target binding, in vivo stability and pharmacokinetics (PK) are often impacted. An important component of these issues is the formation of dye aggregates. In particular, H-aggregates, which are characterized by the appearance of a hypsochromic (blue-shifted) absorption band and a reduction in fluorescence intensity, are a common consequence of fluorophore bioconjugation.
A common strategy to avoid aggregation is the introduction of multiple anionic sulfonate groups. However, while dye sulfonation is a highly successful strategy for fluorophores in the visible range, persulfonated near-infrared (NIR) fluorophores are still prone to the formation of aggregates at even moderate labeling density. Since NIR fluorophores intrinsically less emissive than their counterparts in the visible range, strategies to circumvent the formation of non-emissive aggregates remain a pressing need.

Non-aggregating heptamethine cyanine fluorophores for in vivo imaging

The USA, as represented by the Secretary, Department of Health and Human Services


A power converter for compensating a maximum output power includes a power switch, a control circuit, an oscillator and a frequency modulator. The control circuit generates a PWM signal in response to the pulse signal generated by the oscillator. The frequency modulator generates a second discharge signal to the oscillator for controlling the maximum output power of the power converter. The second discharge signal is decreased for prolonging a switching period of the PWM signal under a high-line voltage of the power converter.

1. Field of Invention
The present invention relates to a power converter, and more particularly, to a PWM controller having a frequency modulator used for compensating a maximum output power of a switching power converter.
2. Description of Related Art
Power converters are generally used to power many of electronic devices. The pulse-width modulation (PWM) technique is a conventional technology used in a power converter to control and regulate the output power. Various protection functions are built-in in the power converter to protect the power converter from permanent damage. The functions of compensating maximum output power are commonly used for overload and short-circuit protections.
FIG. 1 shows a circuit diagram of a traditional power converter used in prior art. The power converter comprises a power transformer T1 having a primary winding NP and a secondary winding NS. The power transformer T1 is to provide galvanic isolation between an AC line input and an output of the power converter for safety. The primary winding NP is supplied with an input voltage VIN of the power converter. In order to regulate an output voltage VO of the power converter, a PWM controller coupled in series with the primary winding NP of the power transformer T1 generates a PWM signal VPWM in response to a feedback signal VFB. The PWM controller comprises an oscillator 10, a first comparator 31, a second comparator 32, a logic circuit 33, and a flip-flop 20. The PWM signal VPWM controls a power switch Q1 to switch the power transformer T1. A sense resistor RS is connected in series with the power switch Q1 to determine the maximum output power of the power converter. The sense resistor RS turns the switching current of the transformer T1 to a current signal VCS. If the current signal VCS is greater than a maximum threshold VM through the first comparator 31, the PWM controller is coupled to disable the PWM signal VPWM, and it also restricts the maximum output power of the power converter.
FIG. 2 shows the signal waveforms of the PWM signal and the current signal of the power converter in FIG. 1. As the PWM signal VPWM becomes logic-high, a primary-side switching current IP will be generated accordingly. A peak value IP1 of the primary-side switching current IP can be given by,
                              I                      P                                                                          1                          =                                            V              IN                                      L              P                                ×                      T            ON                                              (        1        )
The maximum output power PO can be expressed by,
                              P          O                =                                                            L                P                                            2                ×                                  T                  S                                                      ×                          I                              P                                                                                1                            2                                =                                                    V                IN                2                            ×                              T                ON                2                                                    2              ×                              L                P                            ×                              T                S                                                                        (        2        )
In Equations (1) and (2), LP is the inductance of the primary winding NP of the transformer T1, and TON is an on-time of the PWM signal VPWM while the power switch Q1 is switched on, and TS is the switching period of the PWM signal VPWM.
From Equation (2), we find that the output power varies as the input voltage VIN varies. The input voltage VIN ranges between 90VAC and 264VAC when the safety regulations are taken into consideration, and wherein the power limit in high-line voltage is many times higher than the power limit in low-line voltage. There is a delay time TD from the moment the voltage in current signal VCS is higher than the maximum threshold VM to the moment the PWM signal VPWM is actually turned off. The maximum output power is also affected by the delay time TD of the PWM controller. In the period of the delay time TD, the power switch Q1 is still turned on, and it keeps on-status for delivering the output power. Therefore, the actual on-time of the PWM signal VPWM is equal to TON+TD, and the actual maximum output power PO becomes as follows:
                              P          O                =                                            V              IN              2                        ×                                          (                                                      T                    ON                                    +                                      T                    D                                                  )                            2                                            2            ×                          L              P                        ×                          T              S                                                          (        3        )            Although the delay time TD is short, generally within the range of 200 nsec˜350 nsec, the higher operating frequency and smaller switching period TS, the more influential impact is caused by the delay time TD. Therefore, the input voltage VIN should be compensated properly, such that the input voltage VIN does not affect the maximum output power.

Power converter for compensating a maximum output power


A mold, system and method for manufacturing a part includes injection molding a substrate in a single injection mold and optionally trimming the panel substrate. The substrate can have a first configuration or a second, different configuration. Trimming of the substrate can occur when the substrate has the first configuration to define an aperture in the substrate.

Injection molded panel substrates are used conventionally in a variety of applications. One such application is as part of the instrument panel assembly on a vehicle that is arranged with a generally horizontal portion disposed over the instrument panel components of the vehicle (e.g., speedometer, etc.) that extends toward the front windshield. Sometimes, different vehicles and/or vehicle types have such instrument panel assemblies and injection molded panel substrates therefor configured differently. For example, a base model of a particular vehicle may include a panel substrate configured according to a first configuration and a higher end model of the same vehicle may include a similar panel substrate but configured according to a second configuration. For example, when the panel substrate is to be a part of an instrument panel assembly, the base model may include a generally solid upper portion, whereas the higher end model may include an aperture formed therethrough into which an audio speaker of a vehicle sound system can be accommodated.
Conventionally, separate process lines were needed to form injection molded panel substrates having varying designs or configurations. For example, a first process line could include a first injection mold for injection molding the panel substrate according to a first configuration for use on the base model and a second process line could include a second injection mold for injection molding the panel substrate according to the second configuration for use in the higher end model.

Mold, system and method for manufacturing a molded part


A three-dimensional image simulation device for managing a live event comprising an image capturing device for capturing live captured data corresponding to a presenter and generating, in real-time, hologram data based on the live captured data. An output interface for broadcasting the hologram data in real-time to at least one additional location containing an audience, wherein the hologram data is used to create a hologram of the presenter at the at least one additional location based on an apparent parallax effect in a simulated three-dimensional display device, the hologram creating a three-dimensional illusion for the audience regarding actual presence of the presenter at the at least one additional location. Furthermore, an input interface for receiving audience data from the at least one additional location regarding interaction between the hologram and the audience and a display device for displaying images based on audience data to the presenter.

The present disclosure finds its genesis in a theatrical illusion which is widely known as "Pepper's ghost". In this illusion, a viewer is made to believe that he is seeing an article which does not, in fact, exist in the setting or circumstances being viewed. The techniques involved in presenting Pepper's ghost are described hereafter. However, for now, a brief description and history of Pepper's ghost is provided.
In order for the classical Pepper's ghost illusion to work properly, the viewer must see clearly into a main setting, but not see into a hidden room. Unknown to the viewer, the viewer is also viewing the main setting through an angled piece of glass which, because of its placement, may be both translucent and reflective. By changing the lighting in the hidden room, the viewer may view a reflection of the lit contents of the hidden room, on the glass panel. Thus, the illusion is controlled by its illumination, and will appear and disappear when the lighting of the object, person, or the like, is turned on or off, respectively. As a result, an object or person which is reflected in the "mirror" section of the glass (e.g. the reflective surface of the glass) may seem to appear or disappear, or change into another object. While this illusion is over 100 years old, the same effect has been employed since at least the 1960's in certain modern theme parks, where objects such as reflected animated props may create the appearance of translucent "ghosts" which appear to be moving through a particular setting and interacting with props in that physical particular setting. Moreover, the images appear to be three dimensional and demonstrate a parallax effect with respect to other items on the stage.
Typically, in recent applications, a polymeric film, drawn tight within a metal frame, is used to replace the glass panel, and a projection device is used to create the image to be displayed on the polymeric film. Construction of the film and associated frame, and the projectors to be used, are well known in the art, and outside of the scope of the present invention.
As an example, U.S. Pat. No. 8,172,400 (O'Connell et al.) describes a projection apparatus which requires a first projection device that is arranged to generate a virtual three dimensional object by projection of the image onto to a reflected/translucent polymer film. A second projection device projects a background image; and a light source projects light onto the virtual three dimensional image. A stage arrangement may also be provided, which is placed behind the screen, upon which a presenter or actor, or a prop, or both, may be located, in order that the presenter or prop, interact with the virtual image.
In more recent applications, such as those described in US Patent publication No. US 2013/0300728 (Reichow et al.), the polymeric film or glass panel showing the reflection is replaced by a transparent front display device, such as an transparent LCD display device. In this approach, the reflective surface with its projected image, is no longer required since the virtual image may be displayed directly on the transparent front display. A background display device is positioned visually behind the transparent front display, and a background image is shown or projected directly on the background display device. The images shown on the background display device may be coordinated with the images on the transparent front display in order to create an apparent parallax effect which provides images which are similar to images from the Pepper's Ghost technique.
Additional display panels may be provided between the front display and the background display, in order to provide additional image content. However, for simplicity, the use of a two panel approach will be discussed in the present document.
Current uses of this simulated 3D presentation technique may include, for example, the display of advertising materials in a simulated 3D environment, or the simultaneous presentation of a speech to numerous groups in many different locations, using a virtual image. Other applications have included providing a virtual performance by a performer, even though, in some cases, the performer is no longer alive.
However, unless a visual "ghost" effect is desired, it has typically been necessary to employ a black background surface behind the virtual image so as to avoid any background image showing through the virtual image. This is because if the viewer were to see the background image through the front image, it would destroy the "holographic" effect of the virtual image.
More recently however, the background image is adjusted so as to be coordinated with the transparent front image so that the two images are mated one to the other. As an example, a blacked-off "masked" area may be provided on the background display which masked image moves and/or is otherwise coordinated with the image on transparent front display so as to minimize or eliminate the background image from bleeding through the image on the front display.
In order to provide a simulated 3D effect using a front panel and a background panel (or any additional intermediate display panels), it is necessary to provide at least some distance between the transparent front display and the background display. This distance typically varies depending on the size of the display, and is used to create the parallax effect.
A common problem with this approach is that the light from the background panel is used to provide the lighting effect on the front panel. As such, with normal background panels and projection apparatuses, the combined 3D image is dark and/or dull, and is typically only useful in darkened display areas. While this is acceptable in some display areas, it is not practical for use in well-lit areas, such as in outdoor displays, or displays in a mall setting.
To address this issue, the prior art displays may be enclosed in a box so as to minimize the amount of ambient light that falls on the screen. However, these boxes require a relatively large profile, which increases the overall size of the screen, and thereby, limit their use in commercial applications. Also, because of the darkened box approach, typically only those standing directly in front of the box display may see the images on the screen. Thus, the ability to show the images to a larger group of people is limited.
A further problem with prior art display systems is the creation of an undesirable visual effect, call moire, wherein false patterns are observed in the final image, as a result of interaction between the visual display lines from the images on the front and background panels. These typically appear as a pattern of roughly parallel lines, or the like. This leads to unacceptable image quality, and is particularly prevalent in systems having lower image quality, or low resolution, display systems. Using higher resolution screens may therefore be expected to reduced the amount of moire observed in the combined image, however, this leads to an increased cost for the simulated 3D screen apparatus.
As such, it would be beneficial to provide a simulated 3D display device of the type described herein, wherein the screen apparatus is capable of being used in higher lighting situations. Furthermore, it would be beneficial to also provide a simulated 3D display device, having a low profile. Still further, it would be beneficial to also provide a simulated 3D display device which has been modified to reduce and/or ameliorate the moire effect, observed in other simulated 3D projection devices.
The present inventors have unexpectedly discovered that the at least some of these benefits may be provided in a novel, low profile simulated 3D display device, which may be viewed simultaneously by a plurality of viewers, in normal ambient lighting conditions.

Methods and systems for generating and using simulated 3D images


There is provided an evaluation apparatus capable of measuring the I-V characteristic in the MOSFET AC operation with a high accuracy. There are also provided a circuit design method and a circuit design system used for the evaluation apparatus. In the evaluation apparatus (1), an AC input signal superimposing circuit (11) applies DC voltage to the MOSFET gate•source•drain•substrate and superimposes an AC input signal of very small voltage on the gate. An AC component measurement circuit (12) measures an AC component of the current flowing between the source and the drain at that time. A mutual conductance calculation circuit (13) compares the amplitude of the AC component of the current with the amplitude of the AC input signal and calculates, from this ratio, the mutual conductance in the frequency of the AC input signal of the MOSFET.

All of patents, patent applications, patent publications, scientific articles and the like, which will hereinafter be cited or identified in the present application, will hereby be incorporated by references in their entirety in order to describe more fully the state of the art, to which the present invention pertains.
In a SOI MOSFET, it is well known that On-current (current at ON) changes depending on its operation history by a history effect. Therefore, it is necessary to know a dynamic I-V characteristic as well as a DC I-V characteristic for the SOI MOSFET.
Conventionally, a pulse measurement method as shown in FIG. 1 has been used for measuring the dynamic I-V characteristic. In FIG. 1, the source of MOSFET 105 is grounded, the drain is connected to a power source through inductive load (L1) 121, and also to oscilloscope 120 through a capacitive element (C1). In addition, pulse generator 119 is connected to the gate.
If a square wave is inputted into MOSFET 105 from pulse generator 119, a current flowing in inductive load (L1) 121 changes according to a change of drain current of MOSFET 105, thereby resulting in change of a drain voltage. The change of the drain voltage is measured by oscilloscope 120. If a characteristic of inductive load (L1) 121 is known, a change of the drain current can be obtained from the change of the drain voltage. A relation between amplitude of the inputted square wave and the drain current constitutes the I-V characteristic during pulse input. This has been disclosed in, for example, IEEE Electron Device Letters, Vol. 16, No. 4, p145, 1995.
Other than the above measurement method, there exists a method called a drain conductance method as shown in FIG. 2. In this method, an impedance analyzer is connected to the source and the drain, while applying a DC voltage to the gate, and a differential conductance gD between the source and the drain is measured by applying an AC signal. If the differential conductance gD is integrated by the drain voltage, the I-V characteristic at a frequency of the AC signal can be obtained. This has been disclosed in, for example, IEEE Journal of Solid-State Circuit, Vol. 27, No. 8, p1186, 1992.
For designing a circuit of SOI MOSFET, SOI-enabled SPICE (circuit simulator) parameters, for example, BSIM SOI is used. For extracting the parameters, a value of a DC I-V measurement is used. This has been disclosed in, for example, BSIM PD2.1 MOSFET MODEL Users Manual BSIM Research Group 1999.
Voltage is measured with an oscilloscope in the pulse measurement method. However, since the voltage dissolution of the oscilloscope is low compared with that of a DC current meter and a DC voltage meter, an accuracy of the measured voltage is low. In addition, since various frequency signals are included in the square signal, it is impossible to obtain the I-V characteristic at a specified frequency.
The drain conductance method has a higher accuracy than the pulse measurement method because of the use of impedance analyzer. However, since the measurement is conducted at a constant gate voltage, the I-V characteristic is different from that of a practical operation of the MOSFET. Then, there exists a problem that the dynamic I-V characteristic at the practical operation of the MOSFET can not be obtained.
Furthermore, since the dynamic I-V characteristic at the practical MOSFET operation is not known, a parameter fitting for the dynamic I-V characteristic is not implemented at SOI-enabled SPICE parameter extraction.

Evaluation device and circuit design method used for the same


A microplasma emission spectrometer is described that includes a chamber for confining a sample volume of gas. A microplasma source that includes a resonant antenna structure generates a microplasma in the chamber from the sample volume of gas. A RF power supply provides power to the resonant antenna structure that generates the microplasma from the sample volume of gas. A spectrally sensitive detector is optically coupled to the microplasma. The entrance of the spectrally sensitive detector has dimensions and is positioned so that emissions from at least one-tenth of a total volume of the microplasma are transmitted through the entrance of the spectrally sensitive detector.

Many industrial and scientific applications require chemical analysis of gas and liquid phase materials to obtain data for these applications. Also, many environmental applications require chemical analysis of gas and liquid phase materials to obtain data useful for health and safety analysis.
Numerous techniques and apparatus have been developed to perform chemical analysis of gas and liquid phase materials. One common analytical technique used for gas phase analysis is plasma emission spectrometry. Plasma emission spectrometry is performed by electrically exciting gas to form a plasma where one or more species undergo excitation and decay via emission at UV, visible, or infrared wavelengths. Detailed spectral analysis of these emissions can be used to determine the gas composition or the composition of liquid phase analytes that are volatilized into the gas stream. The spectral analysis can include ultraviolet and infrared spectral analysis depending upon the particular application.
One known method of performing plasma emission spectrometry uses a plasma torch to breakdown the material under test. Typical operating powers for the plasma torch are several kilowatts. Typical gas flow rates are on order of several liters/min. Such systems are relatively large having a footprint on the order of several cubic feet, which limits their application to laboratory installations.


A scanning module is used in a scanner with a glass for placing documents. The scanning module contains a convergent lens set comprised of lenses with different curvatures and a long-stripe shape lined up from a reflector, and starting with the reflector, the lengths of the lenses are shorter and shorter one by one. All the light reflected by the document can be converged by the convergent lens set to an image sensor so that an optimal image completely falls in the image sensor. The convergent lens set shortens the length of the scanning module, rendering a compact scanner.

1. Field of Invention
The invention relates to a scanning module in a scanner.
2. Related Art
In addition to pictures, videos, multimedia, and computer briefing, daily business document processing also demands for digitalization of information. Although paperless offices have not realized yet, scanning has been used in businesses to reduce the use of paper.
The scanner has always been a useful input device. Its operation is very easy. One only needs to open the lid of the scanner, puts the original document on the glass, and covers the lid. The rest of the scanning task is done by using operating software to control the scanning module.
The basic principle of the scanner is to use a mechanical or electronic scanning module to read image points on a document and the convert them into digital information. Since the scanner converts the brightness of light cast from a light source and reflected by the image points on the original document, it is thus called the photoelectric conversion. During the process of the image sensor's reading the original document, light emitted from the light source is projected onto the surface of the document. The light reflected by the document passes lenses and forms an image on the sensor. Through the photoelectric conversion, an output voltage proportional to the concentration of the image is generated. The optical path can be controlled by the lenses.
In recent years, there is a trend to make all electronics as compact as possible, and so are scanners. As shown in FIG. 1, the lenses used in the scanning module 1 of a scanner are in a lens set 11 with a specific total track available on the market. The lens set 11 is provided with a circular lens (not shown). When using this lens set 11, the length L of the scanning module 1 has to be at least 250 mm. If one wants to shorten the total track, there will be distortion at the boundary of the image received by the image sensor 12 and the lens set 11 will have a larger size. Therefore, it is very difficult to minimize the volume of scanners.


The present invention is directed to a flat panel display device and a method for driving thereof. According to the present invention, in the flat panel display for processing and displaying a display signal outputted from the graphic source via a serial bus, the graphic source fetches and interprets the display characteristics information of the flat panel display from the flat panel display module via the serial bus so that a new corresponding standard of display signal can be outputted. Here, the display characteristics information is adjustable by the input of predetermined data by use of a predetermined key installed outside the flat panel display by a user and includes more than one of standard information of the display signal with its blanking interval defined and screen display information. A flat panel display according to an embodiment of the present invention is essentially comprised of a graphic source including a graphic source unit; and a liquid crystal display module including a connector, a D/A converter, a memory, and a timing controller.

(a) Field of the Invention
The present invention relates generally to a flat panel display, and more particularly to an apparatus and a method for driving the flat panel display.
(b) Description of the Related Art
A typical flat panel display in commercial use includes a liquid crystal display (LCD) and a plasma display panel (PDP) and, in addition, such display as an electro luminescence (EL) has been developed.
A flat panel display module has a flat panel in which pixels are arranged in a matrix form between two glass substrates, a PCB (printed circuit board) module for driving the flat panel, and a case for protecting and integrating them.
As shown in FIG. 1 illustrating an entire circuit configuration of a typical flat panel display module, the PCB module for driving the flat panel 40 typically includes a main PCB 10 for receiving RGB image data, synchronization signals, etc., from an external apparatus like a PC. Such signals are processed by a timing controller T-con, a customized integrated circuit in the form of FPGA (flat pin grid array), so that image data and a variety of control signals are produced in accordance with structure of the flat panel 40. It also includes a row driver 20 for supplying scanning signals for row signal lines based on row driver control signals 50 and power signals 51 received from the main PCB 10, and a column driver 30 for supplying gray level voltages 61 for the flat panel 40 after receiving the image data and the control signals 60 processed in the main PCB and the gray level voltages 61.
However, as conventional driving circuits implemented on the main PCB 10 have a masking timing setting scheme that combines timing and various input driving interface conditions within a specification prescribed for the panel, it is impossible to modify timing and operation of the driving circuits depending on the changes of user conditions and input conditions of display source and monitor product. In other words, the timing and operation of the driving circuits are fixed, and even within a range of possible operation, it is impossible to flexibly support the optimization of display characteristics unless processed by a hardware option in the driving circuits. This is because the timing conditions for input of the flat panel display is basically set to be suitable for VESA specification, and allows a graphic source to produce and display digital interface timing control signals for driving the panel on the basis of digital data communication (DDC) information stored in the flat panel display module. In addition, flat panel display monitor products on the market set gamma voltages and various power sources for differentiating gray.
According to the conventional art, a user can adjust gamma voltages, flicker voltages, brightness, scaling, frame rate control (FRC), I/O format, etc., by identifying and adjusting a screen display state using an On Screen Display (OSD) function or directly adjusting a hardware. However, only by using these functions, although an optimal screen can be driven by modifying timing (modifying a driving frequency or modification to least and optimal blanking time) on the flat panel driving circuit or a very good driving environment can be achieved by processing a standard signal through an additional circuit in the graphic source so that the driving frequency is modified or the modification to the least and optimal blanking time is made, as referred to above, as an I/O format is required to satisfy the requirement to a general display standard, however good the above conditions may be, a risk to the modification is very high.
In addition, particularly, an interface is required to drive a different I/O format of display source for use in a monitor, and if a difference occurs in a frame frequency or the number of blanking interval, an additional system board (such option board as A/D board, D/D board, etc.), which is capable of FRC adjustment, should be supported. Furthermore, the I/O format of the flat panel display is limited and efficiency of the display products cannot be fully facilitated. Furthermore, a jitter caused by the option board and a mismatch of bi-directional interface conditions result in poor picture quality. It neither contributes to optimizing the monitor products.
As described above, a difference in display manner from a CRT display and the flat panel display causes this problem. The CRT can drive widely up to from 40 Hz to 85 Hz in the frame frequency while the driving manner of the flat panel display is determined by the characteristics of the panel. In other words, if the characteristics of the current panel is optimized at the frame frequency of 60 Hz, the driving conditions also becomes necessarily optimized at 60 Hz. In addition, since a graphic card or the display source does not exactly follow a VESA standard, different manufacturers supply data of various timing slightly different from standard timing. Therefore, when the timing for the optimal driving conditions of the flat panel should be different from the timing of the VESA standard signal or a slight deviation occurs in the standard signal dependent on manufacturers, though an additional option board is used in order to adjust such a changeable timing, this is insufficient to perform completely the function described above and the additional board incurs a high cost.
In addition, a blanking interval (horizontal synchronization signal, back porch, front porch)) taken to return to the next line after line of electron beam is scanned with the standard of input timing of VESA display as the CRT standard and a blanking interval (vertical synchronization signal, back porch, front porch) taken to return from last position, where one frame is scanned, to first position are specified for each frequency. However, since an active matrix scheme and the like other than a scanning scheme are used in driving the flat panel, after transfer of last display signal of line or frame, a blanking interval may have only a blanking interval of as much as least pixel (in case of a horizontal blanking) or line (in case of a vertical blanking), unlike the CRT. In addition, by using such option board as an A/D board, when the operation frequency is increased and the blanking interval becomes long and unstable so that an interface process or an I/O becomes unstable due to an unnecessary blanking interval in the VESA conditions, the driving conditions of the flat panel also becomes considerably unstable. Accordingly, there is a need that the flat panel can be driven on optimal driving timing conditions by reducing the blanking time described above so that display characteristics becomes stable and reliable.
In addition, there is a case that the display characteristics should be adjusted based on product tolerance or user environment and conditions. As these flat panel monitor products are conventionally set with the optimal driving conditions determined by the characteristic of the flat panel, an adjustment should be made by an additional option board or an interface board. However, by adjustment of gamma, contrast, brightness, flicker, and other display characteristics, when the optimal driving conditions fixed in accordance with characteristic of the flat panel is modified, there were the problems that the flat panel characteristics can be used with 100% efficiency since contrasted upper and lower gray levels are fitted to the flat panel in a truncated state by clamping when the A/D board or the option board is used.
Therefore, there is a desirable need to provide an essential driving scheme that eliminates cost rise due to the option board as well as prevents the jitter caused by the mismatch of interface conditions. In other words, there is a need to facilitate the modification to FRC, I/O format, and other information on the display characteristics so that resolution information, information on such operation frequency as vertical and horizontal frequency of the picture signal and main frequency of the picture signal, as well as digital information on gamma voltage, flicker voltage, and brightness and the like can be shared by the graphic source and the flat panel display module can be updated by users. Particularly, there is a need to utilize the signal outputted from the graphic source to the maximum so that it is adapted to the driving of the flat panel display device by using the signal as the standard signal as well as the picture signal modified in its blanking interval and then its frequency based on a definition by the user.