A digital modulator comprises a power control circuit for producing a digital power control signal, first and second digital multipliers for multiplying digital signals having orthogonal phase relationships with the digital power control signal, and first and second digital-to-analog (D/A) converters for converting digital output signals from the first and second multipliers into analog signals. First and second low-pass filters are connected to outputs of the D/A converters, respectively, to filter out high frequency components. An orthogonal modulator is provided for mixing orthogonal phase carriers with the outputs of the first and second low-pass filters to produce first and second orthogonally modulated signals and combining the modulated signals to produce a transmit signal, which is amplified for transmission.

The present invention relates generally to digital modulators, and more specifically to a base-station digital modulator for mobile communications system in which the transmission power of the base station is varied to compensate for variations in distance to mobile units.
In mobile communications systems, the transmission power level of the base station is controlled in response to the power level of a signal received from the mobile unit so that the signal transmitted from the base station can be received at the mobile unit at a constant power level. With conventional digital modulators, this transmission power control is performed by a variable gain amplifier in the power stage in response to a gain control signal supplied from a power control circuit. This power control circuit includes a selector switch which is responsive to a select command signal to select one of prescribed discrete gain control voltages. If these control voltages are switched from the lowest to the highest value, the switched output would linearly vary in the range of power levels required for compensating for possible base-to-mobile distance variations. Sharp voltage transitions occur at the output of the selector switch as it switches from one level to another. The selected voltage is smoothed by an analog integrator since such transitions would result in the spreading of the frequency spectrum of the transmitted signal if it is directly applied to the variable gain amplifier. However, one disadvantage of the prior art power control circuit is that, due to analog circuit components of the power control circuit manual adjustments must be made before shipment to compensate for variabilities circuit parameters.

Digital modulator with digital power control circuit


A reflector includes a body having a reflective surface formed therein and a reflector opening defined in the body, the reflector opening having a plurality of ridges.

Digital projectors, such as digital micro-mirror devices (DMD) and liquid crystal devices (LCD) projectors, project high quality images onto a viewing surface. Both DMD and LCD projectors utilize high intensity burners and reflectors to generate the light needed for projection. Light generated by the burner is concentrated as a 'fireball' that is located at a focal point of a reflector. Light produced by the fireball is directed from the reflector into a projection assembly that produces images and utilizes the generated light to illuminate the image.
The image is then projected onto a viewing surface. Misalignment of the reflector focal point causes degradation of the image since less light is captured and creates 'hot spots' on the screen instead of a uniform brightness. The alignment of the focal point of the fireball with respect to the reflector may depend, at least in part, on the relative alignment between the reflector opening and the reflective surface of the reflector. In conventional devices, once the burner has surpassed its useful life, the entire assembly is typically discarded, including the reflector.
Throughout the drawings, identical reference numbers designate similar, but not necessarily identical, elements.

Hewlett-Packard Development Company, L.P.


Apparatus for cleaning, assembling, testing and inspecting contamination sensitive hardware. The apparatus includes an environmental process enclosure having an inner processing chamber, and a carbon dioxide jet spray cleaning system. The enclosure includes a loadlock pass-through having front and rear access doors for providing access to the inner processing chamber. A blower is disposed in the enclosure for circulating purified gas therethrough. A prefilter disposed prior to an inlet of the blower, and a high purity filter and laminar flow screen are disposed in the inner processing chamber. A heater is provided for heating the purified gas and a temperature controller is coupled to the heater for controlling the temperature of the purified gas. A table is disposed in the inner processing chamber upon which contamination sensitive hardware and testing and assembly apparatus may be placed. The carbon dioxide jet spray cleaning system includes a carbon dioxide delivery system for storing liquid carbon dioxide, and a valve assembly coupled to the carbon dioxide tank that is disposed in the inner processing chamber. The valve assembly is coupled to a nozzle and orifice assembly, which produces a spray of gas and solid carbon dioxide that is used to clean the contamination sensitive hardware.

The present invention relates generally to process tooling, and more particularly, to a process tool comprising a carbon dioxide jet spray cleaning system and controlled environment for cleaning, assembling, testing and inspecting precision components, such as those used in optical and hard drives, and the like.
The routine cleaning of precision hardware, such as disks used in computer hard drives, for example, is relatively inefficient, and currently available process tooling is costly. Currently available cleaning processes require unnecessary handling of the hard disks and creates the potential for hardware damage during such handling and transportation.
In commercially available process tools, hardware is removed from the process tool, cleaned, then returned for assembly or test. The transportation of the hardware from the process tool to an exterior cleaning area increases contamination through migration from handling equipment and the shipping container or carrier. The testing of contamination sensitive hardware using currently available process tools typically results in tested hardware that does not meet the original requirements of the product.
A large number of commercially available process tools used for ultra-clean applications have inadequate environment cleanness and control. Currently available process and inspection tools do not provide an environment that is compatible with liquid carbon dioxide jet spray cleaning processes. More particularly, presently available process inspection technology used in process or inspection tools that have self-contained environments, do not supply humidity control, high flow laminar gas recirculation, or liquid carbon dioxide jet spray cleaning capability.
There presently is not a system that provides for an in-situ carbon dioxide jet spray cleaning system used in conjunction with or disposed within an ultra clean environment process tool. Liquid carbon dioxide jet spray cleaning systems and ultra clean environments have separately been developed by the assignee of the present invention as part of its EcoSnow.TM. product line. However, these two separate technologies have not heretofore been combined to provide process tool for use in jet spray cleaning precision components, such as those used in hard drives, and the like. Furthermore, heretofore, there has been no process tool wherein hardware is cleaned using a combined gas and solid carbon dioxide jet spray while it remains in an ultra clean environment of the process tool.
Accordingly, it is an objective of the present invention to provide for a process tool comprising a carbon dioxide jet spray cleaning system and controlled environment for cleaning, assembling, testing and inspecting precision components.

Apparatus for cleaning and testing precision components of hard drives and the like


The invention provides a particulate composition adapted for forming a bone graft substitute cement upon mixing with an aqueous solution, comprising i) a calcium sulfate hemihydrate powder, wherein the calcium sulfate hemihydrate is present at a concentration of at least about 50 weight percent based on the total weight of the particulate composition; ii) a monocalcium phosphate monohydrate powder; iii) a non-porous β-tricalcium phosphate powder; and iv) a porous β-tricalcium phosphate powder. Bone graft substitute cements made therefrom, a bone graft substitute kit comprising the particulate composition, methods of making and using the particulate composition, and articles made from the bone graft substitute cement are also provided.

Defects in bone structure arise in a variety of circumstances, such as trauma, disease, and surgery. There is a need for effective repair of bone defects in various surgical fields, including maxillo-craniofacial, periodontics, and orthopedics. Numerous natural and synthetic materials and compositions have been used to stimulate healing at the site of a bone defect. As with compositions used to repair other types of tissue, the biological and mechanical properties of a bone repair material are critical in determining the effectiveness and suitability of the material in any particular application.
After blood, bone is the second most commonly transplanted material. Autologous cancellous bone has long been considered the most effective bone repair material, since it is both osteoinductive and non-immunogenic. However, adequate quantities of autologous cancellous bone are not available under all circumstances, and donor site morbidity and trauma are serious drawbacks to this approach. The use of allograft bone avoids the problem of creating a second surgical site in the patient, but suffers from some disadvantages of its own. For instance, allograft bone typically has a lower osteogenic capacity than autograft bone, a higher resorption rate, creates less revascularization at the site of the bone defect, and typically results in a greater immunogenic response. The transfer of certain diseases is also a danger when using allografts.
To avoid the problems associated with autograft and allograft bone, considerable research has been conducted in the area of synthetic bone substitute materials that can be used in lieu of natural bone. For example, various compositions and materials comprising demineralized bone matrix, calcium phosphate, and calcium sulfate have been proposed.
Cements comprising calcium sulfate have a long history of use as bone graft substitutes. Modern surgical grade calcium sulfate cements offer high initial strength, good handling properties, and are consistently replaced by bone in many applications. However, calcium sulfate cements are characterized by relatively rapid resorption by the body, which can be undesirable in certain applications.
Hydroxyapatite is one of the most commonly used calcium phosphates in bone graft materials. Its structure is similar to the mineral phase of bone and it exhibits excellent biocompatibility. However, hydroxyapatite has an extremely slow resorption rate that may be unsuitable in certain applications. Other calcium phosphate materials have also been used in the art, such as β-tricalcium phosphate, which exhibits a faster resorption rate than hydroxyapatite, but has less mechanical strength. Certain calcium phosphate materials that set in situ have also been attempted, such as mixtures of tetracalcium phosphate and dicalcium phosphate anhydrate or dihydrate, which react to form hydroxyapatite when mixed with an aqueous solution.
The presently available synthetic bone repair materials do not present ideal functional characteristics for all bone graft applications. As noted above, some compositions exhibit a resorption rate that is either too slow or too rapid. Further, many bone graft cements are difficult to implant because they fail to set or cannot be injected. Other drawbacks are inadequate strength and difficulty in adding biologically active substances for controlled release. Furthermore, certain bone graft cements developed to address these concerns fail to completely set (harden) in the presence of particular additives. For these reasons, there remains a need in the art for bone graft cement compositions that combine a desirable resorption rate with high mechanical strength, ease of handling, osteoconductivity, and workable set time even in the presence of additives.

This patent is subject to a terminal disclaimer.

Multiphasic bone graft substitute material


A support assembly for supporting a plurality of inclined plates (22) arranged in an array around a central axis includes a top support bracket (25) for supporting the upper edges (40) of the plates (22) and a plurality of base brackets (26) for supporting the lower edges (62) of the respective plates (22). The top support bracket (25) has a central axis aligned with the central axis of the array, and a plurality of side edges (28). Each side edge (28) has a downwardly inclined rim (32) at a predetermined angle corresponding to the desired plate orientation and a downwardly facing groove (42) for receiving the upper edge (40) of the respective plate (22). Each base bracket (26) has a base (46) for securing against a substantially flat support surface (16), a snap lock arm (52, 54) extending upwardly from the base (46) towards a respective side edge (28) of the top bracket (25) at a predetermined angle equal to the rim angle for snap engagement in an opening (60) spaced from the lower edge of the respective plate (22), and a groove (55) at the lower end of the snap lock arm (52, 54) for receiving the lower edge (62) of the respective inclined plate (22).

I. Field of the Invention
The present invention relates generally to antenna mounts, and is particularly concerned with a mounting assembly for mounting patch antennae and the like at fixed angles to a surface for receiving and transmitting signals over various angles. The invention further relates to a mounting assembly for mounting patch antennae in combination with other types of antennae.
II. Description of the Related Art
A variety of new wireless communication systems have been designed that employ communication terminals at fixed locations often referred to as "fixed telephones". Some of these communication terminals communicate using Earth orbiting satellites in non-geosynchronous orbits. A discussion of such systems can be found for example in U.S. patent application Ser. No. 08/368,570, filed Jan. 4, 1995, entitled "Method And Apparatus For Using Full Spectrum Transmitted Power In A Spread Spectrum Communication System For Tracking Individual Recipient Phase Time And Energy"; U.S. patent application Ser. No. 08/627,830, filed Apr. 2, 1996, entitled "Pilot Signal Strength Control For A Low Earth Orbiting Satellite Communications System"; and U.S. patent application Ser. No. 08/627,831, filed Apr. 2, 1996, entitled "Using Orthogonal Waveforms To Enable Multiple Transmitters To Share A Single CDM Channel," which are assigned to the assignee of the present invention, and is incorporated herein by reference.
One type of antenna being used for fixed installations in advanced communication systems, is the well known "patch" type of antenna. This type of antenna has radiation pattern characteristics that may offer certain advantages useful in communicating through multiple orbiting satellites. In addition, this class of antenna is naturally a "low profile" antenna which is suitable for minimizing visual impact. For example, they can help satisfy aesthetic requirements for minimal, or non-obtrusive, structures in many applications. The low profile of patch antennas can also reduce exposure of antenna elements to damage from certain environmental elements such as wind or flying objects.
Patch antennas have typically been positioned as planar elements parallel to the local horizontal of the Earth's surface. However, newer designs are being proposed that position patch antenna elements at an angle from the local horizontal. This type of positioning for the patch antenna elements is designed to improve signal transfer with transmission and reception apparatus that are not directly overhead, but are otherwise positioned off to one side of the antenna assembly and at a shallow angle relative to the planar surfaces. For example, this is useful in communicating through a satellite which is above the Earth's horizon but not yet directly above an antenna assembly. In order to accomplish this, the patch antenna elements, or supporting substrates or plates, must be mounted at fixed angles relative to the horizon or horizontal, and this is normally achieved by fasteners such as screws, bolts or the like and various support brackets or plates. The patch antenna elements are, therefore, relatively difficult to assemble into more complex structures and to remove if service or replacement is required. They are often more labor intensive and expensive to manufacture and service than desired.
At the same time, current patch antenna assembly designs have been limited to using only patch type radiator elements, including one or more elements parallel to the surface of the Earth for upwardly directed radiation patterns. However, advanced communication systems may find it more advantageous to also employ non-patch antenna elements as part of an overall antenna assembly. Unfortunately, current antenna assembly hardware does not provide for easy assembly or support of "mixed type" antenna element or radiator assemblies.
What is needed is a support assembly or support elements that can quickly and reliably secure antenna elements or support substrates in place, which are easy to work with and require few or no tools. The support assembly should result in very rigid and strong support while allowing simplified disassembly for servicing an antenna structure or associated components. At the same time, it is desirable that angled antenna elements be secured in a manner that allows them to also easily be used in conjunction with non-planar antennas or patches, as desired.


Provided is a technique for monitoring energy consumption in an electric vehicle (EV) charging network. The technique is based on using messages from one or more EV charging stations, each of which comprises a timestamp, a station ID, a charging session ID, and an energy meter reading. Whenever a new message is received, it is first stored in a database, whereupon it is checked whether the database comprises an older message with the same station ID and charging session ID as the new message. If the older message is present in the database, a time difference and an energy difference between the new and older messages are calculated. Then, a time granularity level is selected based on the time difference. An energy consumption distribution between the timestamps of the new and older messages is obtained based on the time granularity level and the energy difference.

At the present time, electric vehicles are being used more frequently for land, sea and air travel. However, due to a limited battery capacity, the electric vehicles often need to be charged one or more times at EV charging stations located on the way to destination points. The location and density of the EV charging stations directly depend on the use rate of the electric vehicles within a geographical area of interest. It is therefore important to know how often EV owners use particular EV charging stations during the day, in order to optimize EV charging and energy production at those EV charging stations.
Given the above, each EV charging station is usually equipped with an energy meter configured to take energy measurements at a given time and send information about the energy measurements to a specialized data center for further processing. However, different EV charging stations may send such information by using different communication protocols and time intervals. On top of that, there may be errors such as data communication problems, which cause the EV charging stations to miss sending the above-mentioned information to the data center. All of this does not allow obtaining a suitable accuracy of energy consumption distribution in time, and makes it difficult or even impossible to calculate a total average energy consumed by the electric vehicles at the EV charging stations of interest at a certain time.

Method, apparatus and computer program product for monitoring energy consumption in an electric vehicle charging network


A character display apparatus of the present invention is a character display apparatus for displaying a character on a screen based on stroke data containing character information, comprising a control section for setting a color element level for a subpixel overlapping a basic portion of the character, based on both or either a distance between a center of the subpixel and at least one dot contained in a stroke or a line width set for the stroke. According to the present invention, the resolution of subpixels can be apparently improved and the line width of a character can be freely changed without a large amount of working memory.

A conventional character display apparatus for displaying characters with high definition using a display device capable of color display, is disclosed in, for example, Japanese Laid-Open Publication No. 2001-100725.
In the character display apparatus of Japanese Laid-Open Publication No. 2001-100725, the color element levels of subpixels corresponding to a basic portion of a character are set to a predetermined color element level. The color element levels of subpixels adjacent to the subpixels corresponding to the basic portion of the character are set to color element levels other than the predetermined color element level, based on at least one correction pattern. The set color element levels are converted to brightness levels based on a predetermined table. As a result, the character is displayed on a display section (display device).
In this conventional technology, the basic portion of a character refers to a core (central backbone) of the character.
Data, such as RGB, CYM, or the like, are assigned as color elements to individual subpixels contained in pixels. A color element level indicates how much a color element contributes to a character color. In this conventional technology, a color element level is represented by a value of "0" to "7". "7" indicates a character color. "0" indicates a background color. Thus, by using color element levels assigned on a subpixel-by-subpixel basis, it is possible to construct a logical model which does not rely on a combination of actual character and background colors.
In order to actually display characters on the character display apparatus, color element levels need to be converted to brightness values. To achieve this, a brightness table for use in converting color element levels to brightness values is provided, depending on a combination of a character color and a background color. For example, when a black character is displayed in a white background, the color element level "7" is converted to a set of brightness values for R, G and B, which are all "0" while the color element level "0" is converted to a set of brightness values for R, G and B, which are all "255".
FIG. 16 is a diagram showing an example, in which the color element levels of subpixels corresponding to the basic portion of a character "/" are set to a predetermined value, and the color element levels of subpixels adjacent to the basic portion of the character are set based on a certain correction pattern.
Each rectangle corresponds to a single subpixel. A hatched rectangle is a subpixel, the color element level of which is represented by the concentration thereof. The color element level is increased with an increase in the concentration. In this example, there are four color element levels, i.e., "0", "1", "2" and "3". When a luminous level ranges from "0" to "255", the color element levels are converted to respective luminous levels "255", "170", "85" and "0", which are displayed on a display section.
Thus, by controlling the color element levels of subpixels separately, a resolution can be apparently improved in a direction along which the subpixels are arranged. Further, by appropriately controlling the color element levels of subpixels adjacent to subpixels corresponding to the basic portion of a character, colors other than black imparted to a character cannot be easily recognized by human eyes. As a result, the contour of a character as well as the character itself can be displayed with high definition on a display screen.
Another conventional technology for displaying a character by controlling subpixels separately is disclosed in Japanese Laid-Open Publication No. 2002-91369.
In a conventional display apparatus disclosed in Japanese Laid-Open Publication No. 2002-91369, for the size of a character to be displayed, a rasterized character image has a 3-fold size in a longitudinal direction of a subpixel and a 3-fold size in an arrangement direction of subpixels. A subpixel is associated with each picture element array of three picture elements (pixels) successively arranged in the longitudinal direction of a subpixel contained in the character image. The brightness value of a subpixel is calculated based on the picture element values of its associated picture elements successively arranged in the longitudinal direction.
FIG. 17 is a diagram for explaining a specific operation of the conventional display apparatus of Japanese Laid-Open Publication No. 2002-91369.
Generally, an image, such as character or graphics, is represented by binary picture element values. As shown in FIG. 17(a), for example, when a slant line is displayed on a display screen, one of two brightness values is simply mapped to each picture element (pixel). In FIGS. 17(a) and 17(b), each rectangle represents a pixel constituting a display screen, and a filled portion corresponds to a slant line.
In this case, in the conventional display apparatus disclosed in Japanese Laid-Open Publication No. 2002-91369, simple mapping to each picture element on a display screen is not performed. Initially, a character image having a resolution three times that of the display apparatus is produced. For example, when it is assumed that one picture element of the display apparatus is composed of a 3×3 matrix, a rasterized character image has a size three times larger than an image to be displayed. For example, when a slant line as shown in FIG. 17(a) is rasterized with a resolution three times that of the display apparatus, a rasterized image as shown in FIG. 17(b) is obtained.
An average value of a plurality of picture elements contained in the above-described character image having the 3-fold size, which are associated with each subpixel of the display apparatus, is mapped to the picture element. For example, the character image of FIG. 17(b) is mapped to subpixels shown in FIG. 17(c). In FIG. 17(c), a rectangle corresponds to a subpixel. A subpixel with a character R thereabove exhibits a red color. A subpixel with a character G thereabove exhibits a green color. A subpixel with a character B thereabove exhibits a blue color. In addition, a filled portion indicates six subpixels to which an average value of picture element values is mapped. Each of the six subpixels, which are longer than are wide, corresponds to three adjacent picture elements in the vertical direction of FIG. 17(b).
As a result, the resolution of the arrangement direction of subpixels can be improved. In addition, since the intensity of color exhibited by each subpixel is determined depending on how much a portion of a character generated with a 3-fold resolution is associated with a single subpixel, the resolution in the longitudinal direction of the subpixel can be apparently improved.
However, in the above-described conventional technology of Japanese Laid-Open Publication No. 2001-100725, the resolution in the longitudinal direction of subpixels is not taken into consideration. Therefore, when a slant line is displayed, jaggies are significant depending on the degree of the slant angle.
In the above-described conventional technology of Japanese Laid-Open Publication No. 2002-91369, a rasterized character image has a 3-fold resolution in the process. Therefore, a problem arises that a large amount of working memory is required. Moreover, there is a limitation such that the width or font of characters cannot be freely changed.
The present invention provides a solution to the above-described conventional problems. An object of the present invention is to provide a character display apparatus and a character display method, which apparently improve resolutions of subpixels in an arrangement direction and a longitudinal direction without a large amount of working memory and are capable of freely changing the width of a character; and a character display program for causing a computer to perform the steps of the method; and a computer readable recording medium.

Character display apparatus, character display method, character display program, and recording medium


Compositions derived from a novel viral isolate designated feline immunodeficiency virus (FIV) include the whole virus, proteins, polypeptides and, polynucleotide sequences derived from the virus; and antibodies to antigenic sites on the virus. These compositions are useful in a variety of techniques for the detection of and vaccination against FIV. Detection methods disclosed include immunoassays for both the virus and antibodies to the virus, and the use of polynucleotide probes to detect the viral genome. Vaccines include both wholly and partially inactivated viruses inactivated cell lines expressing FIV antigens, and subunit vaccines. Whole, live virus is also useful as a model system for predicting the behavior of human immunodeficiency virus (HIV).

1. Field of the Invention
The present invention relates generally to the detection and treatment of viral infection. More particularly, the invention relates to compositions and methods useful for the diagnosis of and vaccination against infection with a newly-discovered lymphotropic retrovirus, initially designated as feline T-lymphotropic lentivirus and presently designated feline immunodeficiency virus (FIV).
Domestic cats may become infected with several retroviruses, including feline leukemia virus (FeLV), feline sarcoma virus (FeSV), endogenous type C oncornavirus (RD-114), and feline syncytia-forming virus (FeSFV). Of these, FeLV is the most significant pathogen, causing diverse symptoms, including lymphoreticular and myeloid neoplasms, anemias, immune-mediated disorders, and an immunodeficiency syndrome which is similar to human acquired immune deficiency syndrome (AIDS). Recently, a particular replication-defective FeLV mutant, designated FeLV-AIDS, has been more particularly associated with immunosuppressive properties.
While immunodeficiency syndrome in cats has normally been associated with FeLV, immunodeficiency-like symptoms have been observed in cats which are seronegative for FeLV, usually without alternative explanation. It would be desirable to identify etiological agents other than FeLV which are responsible for causing immunodeficiency in cats. It would be particularly desirable to provide methods and compositions for the detection of and vaccination against such newly-identified etiological agents, and in particular, against FIV.
2. Description of the Background Art
The discovery of feline T-lymphotropic lentivirus (now designated feline immunodeficiency virus) was first reported in Pedersen et al. (1987) Science 235:790-793 Abstracts concerning the discovery of the virus have been presented at the American Association for Cancer Research on May 23, 1987 (Abstract No. 3337); and The Third International Conference on Acquired Immune Deficiency Syndrome, Jun. 1-5, 1987. A poster concerning discovery of the virus was presented at a meeting of the Federation of American Society for Experimental Biology on April 2, 1987.
Characteristics of FIV have been reported in Yamamoto et al. (1988) Leukemia, December Supplement 2:204S-215S; Yamamoto et al. (1988) Am. J. Vet. Res. 49:1246-1258; and Ackley et al. (1990) J. Virol. 64:5652-5655. Cloning and sequence analysis of FIV have been reported in Olmsted et al. (1989) Proc. Natl. Acad. Sci. U.S.A. 86:8088-8092 and 86:4355-4360; and Talbott et al. (1989) Proc. Natl. Acad. Sci. U.S.A. 86:5743-5747. Hosie and Jarret (1990) AIDS 4:215-220, describes the serological response of cats infected with FIV.
A portion of the experimental data presented in this application was published in AIDS 1990 4 (Suppl. 1):S163-S165.
Inactivated cell-virus and cell-free whole simian immunodeficiency vaccines have been reported to afford protection in macaques (Stott et al. (1990) Lancet 336:1538-1541; Desrosiers et al. PNAS U.S.A. (1989) 86:6353-6357; Murphey-Corb et al. (1989) Science 246:1293-1297; and Carlson et al. (1990) AIDS Res. Human Retroviruses 6:1239-1246). A recombinant HIV gp120 vaccine has been reported to afford protection in chimpanzees (Berman et al. (1990) Nature 345:622-625).

Methods and compositions for vaccinating against feline immunodeficiency virus

The Regents of the University of California


The present invention utilizes simple dimethylsilicone fluids of the proper viscosity/molecular weight added to modify the low temperature properties of polycyclic hydrocarbons. One preferred embodiment of a polycyclic hydrocarbon is a perhydro dimer of alpha-methyl styrene. Addition of the dimethylsilicone fluid to the perhydo dimer of alpha-methyl styrene improves the low temperature performance without degrading the requisite low shear stress shear strength properties. Low viscosity dimethylsilicone lubricating fluids combined with polycyclic hydrocarbons are suitable for use in infinitely variable transmissions providing good low temperature flow properties and high shear strength at high temperature and low contact stress conditions.

An infinite variable transmission is a for of a traction drive which is a device whereby torque is transmitted from one smooth rolling element to another and typically the rolling elements are in nominal point or line contact. Variable speed traction drives can be made by proper selection of the number, size, shape and geometrical configuration of the roller elements typically comprising one or more parallel cylindrical elements spaced apart from one another. Variable speed transmissions provide a means for smooth and quiet operation and increased fuel efficiency.
For example, infinitely variable transmission ("IVT") are configured to provide a continuous range of ratio from reverse through stationary to high overdrive utilizing a variator comprising a set of discs and rollers. The rollers do not touch the discs and there is no metal to metal contact, but are separated by traction fluid.
The variable speed transmission, (traction fluid), behaves as a lubricant and coolant in the variable speed transmission. The fluid is required to exhibit high pressure and high shear conditions found I the area of contact between the plate or roller elements which are separated by a thin film of the fluid. The fluids resistance to shear provides the torque transmitting ability of the fluid composition. The torque transmitting ability of the fluid composition can be measured by its traction coefficient.
Traction fluid works by rolling the edge of the roller against the surface of the discs which traps a microscopic oil film between them. The long chain molecules of the traction fluid interlock with one another when the fluid is compressed and becomes highly viscous under pressure. Thus, as pressure is exerted at the contact points between the roller and/or discs the oil "traction fluid" resists the tendency to slip and transmits the power effectively.

Variable transmission traction fluid composition

Ashland Licensing and Intellectual Property, LLC


A control device for a high pressure fuel pump (33) for fuel injection (14) in which values of at least seven parameters of an engine speed, an engine load, a lubrication oil temperature, an amount of fuel supplied to the high pressure fuel pump (33), a temperature of intake air fed into the engine, a temperature of fuel discharged from the high pressure fuel pump (33), and a vehicle speed are acquired, and a learned neural network learned in weights using acquired values of the seven parameters as input values of the neural network and using as training data the temperature of fuel discharged from the high pressure fuel pump (33) acquired after a fixed time period from when acquiring the values of the seven parameters is stored, At the time of an engine operation, the temperature of fuel discharged from the high pressure fuel pump (33) after the fixed time period is estimated by using the learned neural network from the current estimated temperature of fuel discharged from the high pressure fuel pump (33).

In fuel, there is a vapor generating region in which fuel vapor is generated inside the fuel. In this case, whether fuel vapor is generated inside the fuel is determined from the fuel temperature and fuel pressure. If the fuel temperature exceeds a certain temperature determined from the fuel pressure, fuel vapor will be generated inside the fuel. If fuel vapor is generated inside the fuel, at the time of engine startup, the fuel pressure will not easily rise even if operating a high pressure fuel pump for fuel injection, and a long time will be required until the fuel pressure reaches the target fuel pressure. On the other hand, a high pressure fuel distribution pipe for distributing fuel discharged from the high pressure fuel pump to fuel injectors usually is not equipped with a fuel temperature sensor for detecting the fuel temperature, but is equipped with a fuel pressure sensor for detecting the fuel pressure. Further, the engine body is usually equipped with a water temperature sensor for detecting an engine cooling water temperature.
Therefore, known in the art is an internal combustion engine where the engine cooling water temperature is used in place of the fuel temperature and if there is request for startup of the engine, the state of generation of fuel vapor is estimated from the results of detection of the fuel pressure sensor and the water temperature sensor, the operation of the high pressure fuel pump is made to start before starting up the engine when it is estimated that fuel vapor is being generated, and the greater the estimated amount of generation of fuel vapor, the longer the operating time of the high pressure fuel pump before engine startup is made (for example see Japanese Unexamined Patent Publication No. 2007-285128).

Control device for high pressure fuel pump for fuel injection


A PTC element has an element body in which an electroconductive filler is dispersed in a crystalline polymer, a pair of lead terminals compressed with the element body in between, and a protecting film covering a portion of the element body not compressed against the pair of lead terminals. Each of the pair of lead terminals has an overlap region overlapping with the element body, and a nonoverlap region not overlapping with the element body. An anchor projection embedded in the element body is formed in the overlap region of each of the pair of lead terminals. A peel prevention region for preventing peeling of the protecting film is formed in a region adjoining the element body in the nonoverlap region. The anchor projection is formed as crushed in a region except for at least the peel prevention region in the nonoverlap region.

1. Field of the Invention
The present invention relates to a PTC (Positive Temperature Coefficient) element.
2. Related Background Art
A PTC element is known as an element for protecting a circuit element from overcurrent. The PTC element is an element that rapidly increases the positive temperature coefficient of resistance at a specific temperature region. One of such known PTC elements is the one described in Japanese Patent Application Laid-Open No. 60-196901 (Japanese Patent Publication No. 5-9921).


An emergency vehicle detection system is provided including a first microphone mounted to a front end of a vehicle for receiving audio signals and a second microphone mounted to a rear end of the vehicle also for receiving audio signals. A pair of wires are provided having a first end connected to an associated one of the microphones. An indicator light is positioned on a dash of the vehicle for illuminating upon the actuation thereof. A high pass filter resides in communication with the wires for abating frequencies of the audio signals that reside below a predetermined amount. Finally, a level detector is connected between the high pass filter and the indicator light. In use, the level detector is adapted to actuate the indicator light upon the detection of an audio signal with a magnitude greater than a predetermined level.

1. Field of the Invention
The present invention relates to an emergency vehicle detection system and more particularly pertains to alerting a user of an approaching emergency vehicle by audibly detecting the emergency vehicle.
2. Description of the Prior Art
The use of emergency vehicle alert systems is known in the prior art. More specifically, emergency vehicle alert systems heretofore devised and utilized for the purpose of preventing collisions with are known to consist basically of familiar, expected and obvious structural configurations, notwithstanding the myriad of designs encompassed by the crowded prior art which have been developed for the fulfillment of countless objectives and requirements.
By way of example, the prior art includes U.S. Pat. Nos. 4,587,522; 3,992,656; 5,307,060; 3,902,123; 3,891,980; and 3,836,959.
In this respect, the emergency vehicle detection system according to the present invention substantially departs from the conventional concepts and designs of the prior art, and in so doing provides an apparatus primarily developed for the purpose of alerting a user of an approaching emergency vehicle.
Therefore, it can be appreciated that there exists a continuing need for a new and improved emergency vehicle detection system which can be used for alerting a user of an approaching emergency vehicle by audibly detecting the emergency vehicle. In this regard, the present invention substantially fulfills this need.


The present invention is a film deposition method of a metal film comprising the steps of: placing an object to be processed having a recess formed in a surface thereof, on a stage in a processing vessel; evacuating the processing vessel to create a vacuum therein; ionizing a metal target in the evacuated processing vessel to generate metal particles including metal ions, by means of a plasma formed by making the plasma from an inert gas; and by applying a bias electric power to the object to be processed placed on the stage to draw the plasma and the metal particles into the object to be processed, scraping a bottom part of the recess to form a scraped recess, and depositing a metal film on an entire surface of the object to be processed including surfaces in the recess and in the scraped recess.

When a semiconductor device is manufactured, generally, a semiconductor wafer is repeatedly subjected to various processes such as a film deposition process and a pattern etching process, so as to manufacture a desired device. In view of recent demand for higher integration degree and further miniaturization of a semiconductor device, a line width thereof and/or a hole diameter thereof have been made smaller and smaller. In accordance with such smaller dimensions, electric resistance has to be made smaller. Thus, there is a tendency to use copper as a wiring material and/or an embedded material, because copper has smaller electric resistivity and is inexpensive (see, JP-A-2000-77365). When copper is used as a wiring material and/or an embedded material, a tantalum metal (Ta) film or a tantalum nitride (TaN) film is used as a barrier layer in consideration of adhesive properties between the copper material and a lower layer thereof.
In order to form such a barrier layer, a tantalum nitride film (hereinafter also referred to as "TaN film") or a tantalum film (hereinafter also referred to as "Ta film") is formed at first as a base layer on a surface of a wafer in a plasma sputtering apparatus. Then, in the same plasma sputtering apparatus, an additional tantalum film is formed (when the base layer is a Ta film, the film deposition conditions are varied). Thus, a barrier layer is formed. Thereafter, a thin seed film made of a copper film is formed on a surface of the barrier layer, and the entire wafer surface is plated with copper to fill a recess.
A lower wiring layer and an upper wiring layer, which are stacked with an insulation film therebetween, are electrically connected in the following manner. Firstly, the insulation layer is formed on the lower wiring layer. Then, a communication hole, such as a via hole and a through hole, is formed in the insulation layer to expose the lower wiring layer at a bottom part of the communication hole. Thereafter, the communication hole is filled with a material of the upper wiring layer, and the upper wiring layer is deposited at the same time. As described above, since the line width is to be narrowed and the hole diameter is to be reduced in accordance with the demand for miniaturization, it is necessary to take measures to lower electric resistance in the connecting structure between the upper and lower wiring layers. As an example of the measures, the through hole is formed such that the bottom part thereof is "embedded" to a predetermined thickness of the lower wiring layer, so that contact resistance between an embedded material to be "embedded" in the bottom part of the through hole and the lower wiring layer is reduced. Such a structure is referred to as a so-called "punch-through structure". A method of forming this structure is referred to as a so-called "punch-through process".
An example of the punch-through process is described with reference to FIGS. 12A to 12C and FIGS. 13A to 13E. FIGS. 12A to 12C show a communication hole formed in a semiconductor wafer which is not yet filled. FIG. 12A is a plan view of the semiconductor wafer whose communication hole is not yet filled. FIG. 12B is a sectional view of the semiconductor wafer taken along the line A-A shown in FIG. 12A. FIG. 12C is a perspective view of the semiconductor wafer shown in FIG. 12A. FIGS. 13A to 13E are views for explaining a filling step of the communication hole.
As shown in FIGS. 12A to 12C, the semiconductor wafer W is formed of a silicon substrate, for example. A lower wiring layer 102 made of copper, and an insulation layer 104 formed of a silicon oxide film are stacked on a surface of the silicon substrate in this order. A recess 105 is formed in a surface of the insulation layer 104. The recess 105 has a wiring groove of a predetermined width, i.e., a trench 106, for forming an upper wiring layer. In a bottom part of the trench 106, there is partially formed a communication hole 108 which passes through the insulation layer 104 to reach the lower wiring layer 102. The communication hole 108 will function as a via hole or a through hole. A diameter L1 of the communication hole 108 is significantly small, e.g., between about 60 nm and about 200 nm. A width L2 of the trench 106 is, e.g., between about 60 nm and about 1000 nm.
In order that the communication hole 108 and the trench 106 are filled, as shown in FIG. 13A, a barrier layer 110 of a metal film is formed at first by plasma sputtering, for example, on an entire surface of the wafer W including a surface in the trench 106 and a surface in the communication hole 108, for improving adhesive properties between the wafer surface and a base layer and for preventing diffusion and migration of copper into the insulation layer 104. As the barrier layer 110, there is mainly employed a two-layered structure including a tantalum nitride film (TaN film) and a tantalum film (Ta film), or a two-layered structure including two tantalum films which have been deposited under different (varied) deposition conditions.
Then, as shown in FIG. 13B, by plasma etching using an Ar gas as an inert gas, a part of the barrier layer 110 formed on the bottom part of the communication hole 108 is scraped. Further, the lower wiring layer 102 as a base of the barrier layer 110 is etched so that a scraped recess 112 of a predetermined depth is formed.
Then, as shown in FIG. 13C, a very thin electro-plating seed film 114 is formed on the entire surface including the inner surfaces of the scraped recess 112, of the communication hole 108, and of the trench 106, by sputtering, for example. A copper (Cu) film is used as the seed film 114 because copper plating is performed in the subsequent step, for example.
Then, as shown in FIG. 13D, electro-plating is performed from the seed film 114 as a starting point, so that the scraped recess 112, the communication hole 108, and the trench 106 are respectively filled with the material of an upper wiring layer 116. As described above, copper is used, for example, as the material of the upper wiring layer 116.
Thereafter, as shown in FIG. 13E, the upper unnecessary metal material is removed by grinding or the like, whereby there is formed the upper wiring layer 116 which is electrically connected to the lower wiring layer 102.
Due to the provision of the communication hole 108 such as a through hole or a via hole in the bottom part of the trench 106, the recess 105 has a two-stepped cross-section. Such a shape of the recess 105 is referred to as a so-called "Dual Damascen structure".
At the plasma etching step shown in FIG. 13B, particles of the barrier layer, which are scattered by etching at a corner indicated by a point P1, for example, are scattered within a predetermined angle range in a certain direction with a specific directivity. This feature does not pose a serious problem when the line width and the groove width are relatively wide. However, since the groove width is as small as about 100 nm, as described above, there is a possibility that the particles, scattered in the certain direction by this feature may adhere to an opposed wall surface to form a deposition projection 118 on the opposed wall surface. When the deposition projection 118 is formed, at the following plasma sputtering step shown in FIG. 13C, the deposition projection 118 generates a shadow, which invites a so-called shadowing phenomenon, because the sputtered particles have a high directivity. Namely, the seed film 114 does not adhere to a shadow part 120 by the deposition projection 118. When there remains a part on which the seed film 114 does not adhere, a void 122 is undesirably generated at that part, as shown in FIG. 13D.
FIGS. 14A and 14B are views for comparing recesses 105 (trenches 106) whose widths L2 are different from each other. In fact, various recesses 5 having different widths L2 may be formed in the surface of the semiconductor wafer W, as shown in FIGS. 14A and 14B. In that case, as shown in FIGS. 14A and 14B, angles θ1 and θ2, which are viewed upward from the bottom parts of the communication holes 108, may differ from each other (θ1<θ2), when aspect ratios of the trenches 106 are different, even if aspect ratios of the communication holes 108 are the same (the diameters L1 thereof are the same). Thus, thicknesses H1 and H2 of the barrier layers 110, which are deposited on the bottom parts of the communication holes 108 as the lowermost layers in the recesses 105, may differ from each other. Because of the difference in the thicknesses H1 and H2 of the barrier layers 110, depths of the scraped recesses 112 formed by scraping the barrier layers 110 may differ from each other.

Film deposition method and film deposition apparatus of metal film


A rotor position detection circuit detects a position of a rotor in a motor from a detection signal of an induced voltage generated in a stator coil. The circuit includes: a first low pass filter having a first reference potential for filtering the detection signal; a comparator for comparing an output signal from the first low pass filter with a predetermined reference voltage and for outputting a rotation position signal; and a second low pass filter having a second reference potential for filtering a virtual neutral point potential of the motor. The first reference potential is the filtered virtual neutral point potential, and the second reference potential is a ground.

When operation of a brushless direct current motor is controlled, multiple Hall elements for detecting a rotation position of a rotor are arranged on a stator side such that the Hall elements are arranged by each electric angle of 60 degrees or 120 degrees. Based on detected position signals from the Hall elements, an energizing timing to the stator coil is determined. However, it is required to include a power source wiring for energizing the Hall element and a wiring for outputting a detection signal. Accordingly, a structure of the motor becomes complex.
To simplify the structure, a motor driving device having no sensor is proposed in, for example, JP-A-S62-123979. The device detects positioning information of a rotor based on an induced voltage, which is generated in the stator coil when the rotor is rotated, without using a sensor such as a Hall element.
FIG. 5 shows a motor driving device 1 for driving a fan motor of a radiator mounted in a vehicle according to a related art. The device 1 is energized from a battery 2 of the vehicle so that a driving power is supplied from the battery 2. A brushless DC motor 3 is energized through an inverter 4. The inverter 4 includes, for example, six power MOSFETs 5a-5f, which are coupled with one another with a three-phase bridge connection. Each phase output terminal in the inverter 4 is connected to a corresponding stator coil 6U, 6V, 6W of the motor 3.
The inverter 4 is controlled with a control portion 7, which includes a micro-computer or a logic circuit. The control portion 7 inputs a driving signal to a gate of each MOSFET 5a-5f through a gate driver 8. A position of a rotating rotor of the motor 3 is detected by a position detection circuit 9. A position detection signal is inputted to the control portion 7. The position detection circuit 9 includes three low pass filters 10U, 10V, 1W, three buffer amplifiers 11U, 11V, 11W and three comparators 12U, 12V, 12W. Each low pass filters 10U, 10V, 10W is mainly composed of a capacitor C and a resistor R. Each comparator 12U, 12V, 12W compares an output signal of the buffer amplifier 11U, 11V, 11W with a virtual neutral point potential, i.e., VNP potential. The input terminal of each low pass filter 10U, 10V, 10W is connected to a common connection point between two resistors R1U, R2U, R1V, R2V, R1W, R2W. The two resistors R1U, R2U, R1V, R2V, R1W, R2W divide an output voltage of each phase output terminal of the inverter 4.
FIGS. 6A to 6I show a voltage waveform in each portion when the motor 3 is energized through the inverter 4. Specifically, FIG. 6A shows a voltage waveform of a U phase in the induced voltage, FIG. 6B shows a voltage waveform of a V phase in the induced voltage, and FIG. 6C shows a voltage waveform of a W phase in the induced voltage. FIG. 6D shows a voltage waveform of a U phase in a signal after passing through the filter 10U, 10V, 10W, FIG. 6E shows a voltage waveform of a V phase in the signal after passing through the filter 10U, 10V, 10W, and FIG. 6F shows a voltage waveform of a W phase in the signal after passing through the filter 10U, 10V, 10W. FIG. 6G shows a voltage waveform of a EU component in the comparator output signal, FIG. 6H shows a voltage waveform of a EV component in the comparator output signal, and FIG. 6I shows a voltage waveform of a EW component in the comparator output signal. Here, the comparator output signal corresponds to the position detection signal. When the motor 3 starts to activate, the control portion 7 provides a predetermined pattern for energizing. After the motor 3 rotates, the induced voltage generated in each stator coil 6U, 6V, 6W appears as a terminal voltage of the coil 6U, 6V, 6W. Since a switching waveform caused by a PWM control method is overlapped with the terminal voltage of the coil 6U, 6V, 6W, the switching waveform is removed by the low pass filter 10U, 10V, 10W. Thus, an induced voltage waveform having an almost sine waveform is obtained. Then, the comparator 12 compares the output signal of each filter 10U, 10V, 10W with the virtual neutral point potential, so that a position signal of each phase having a rectangular waveform is obtained.
The control portion 7 sets a PWM duty for determining a rotation speed of the motor 3 in accordance with a control signal inputted from an external ECU (i.e., electronic control unit). Further, the control portion 7 determines a commutation timing based on the position signal detected by the position detection circuit 9, and generates a driving signal. Then, the control portion 7 outputs the driving signal to the gate driver 8.
JP-A-H07-337080 discloses a technique for starting energization at an appropriate timing when an activation instruction of a motor is given. This technique is used for a fan motor of an air-conditioner, and a rotational position of a fan in a compressor unit as an external unit is detected when the fan is rotated by catching wind.
When the motor 3 is controlled by the PWM control method without a sensor, it is necessary to remove the switching noise in the induced voltage signal by using the low pass filter 10U, 10V, 10W. As a result, a delay is generated in a phase of the induced voltage signal passing through the low pass filter 10U, 10V, 10W. To set the phase delay to be almost 90 degrees in all frequency range of the induced voltage signal, it is preferred that a CR time constant becomes larger and a cut-off frequency becomes smaller within an allowable range of decay of the signal passing through a CR filter.
In general, a device for driving a fan motor in a vehicle is mounted in an engine compartment of the vehicle. Accordingly, temperature of operating environment is disposed in an extremely wide range. The CR time constant of the low pass filter 10U, 10V, 10W has a tolerance, and, in addition, the CR time constant is easily affected by the temperature. Thus, variation of the CR time constant becomes large, and the CR time constant of each low pass filter 10U, 10V, 10W may deviate from a predetermined value.
Regarding the fan of the radiator in the vehicle, the motor 3 may start to activate from a state where the fan is rotated by catching wind when the vehicle runs. However, if the time constant of the low pass filter 10U, 10V, 10W is deviated largely, an appropriate timing is not obtained when the energization of the device starts or when the energization stops. Therefore, loss of synchronism may occur, and/or commutation pattern may not be changed, so that excess current is supplied to the device.
Further, when the motor for the vehicle is activated, it is necessary for the motor to drive normally even if a power source voltage is deviated from a predetermined value. Similar to the above case, if the time constant of the low pass filter 10U, 10V, 10W is deviated largely, an appropriate timing is not obtained when the power source voltage is rapidly changed. Therefore, loss of synchronism may occur, and/or commutation pattern may not be changed, so that excess current is supplied to the device.
Here, FIGS. 7A to 7I shows a case where the motor 3 is energized and starts to activate from a state where the fan is rotated by catching wind when the time constant of the low pass filter 10U, 10V, 10W is not deviated. Specifically, FIGS. 7A to 7I show a voltage waveform in each portion when the motor 3 is energized. FIGS. 7A to 7C show voltage waveforms of a U phase, a V phase and a W phase in the induced voltage. FIGS. 7D to 7F show voltage waveforms of a U phase, a V phase and a W phase in a signal after passing through the filter 10U, 10V, 10W. FIGS. 7G to 7I show voltage waveforms of a U phase, a V phase and a W phase in the comparator output signal. Here, the comparator output signal corresponds to the position detection signal. VIIA represents a period in which the fan is rotated by catching wind. VIIB represents a timing at which the energization starts. VIIC represents a period in which the energization is performed. In this case, the motor 3 can start to activate without difficulty.
FIGS. 8A to 8I shows a case where the motor 3 is energized and starts to activate from a state where the fan is rotated by catching wind when the time constant of the low pass filter 10U, 10V, 10W is deviated. Specifically, FIGS. 8A to 8I show a voltage waveform in each portion when the motor 3 is energized. FIGS. 8A to 8C show voltage waveforms of a U phase, a V phase and a W phase in the induced voltage. FIGS. 8D to 8F show voltage waveforms of a U phase, a V phase and a W phase in a signal after passing through the filter 10U, 10V, 10W. FIGS. 8G to 81 show voltage waveforms of a U phase, a V phase and a W phase in the comparator output signal. VIIIA represents a period in which the fan is rotated by catching wind, VIIIB represents a timing at which the energization starts, and VIIIC represents a period in which the energization is performed. In this case, since the time constant of the filter 10U, 10V, 10W is deviated, the phase in the position detection signal outputted from the comparator 12 is deviated when the energization starts.
FIGS. 9A to 9D show actual waveforms of the U phase position detection signal and U, V and W phase voltages observed by an oscilloscope after the signal passes through the filter 10U, 10V, 10W. The observation is performed at an input terminal of the buffer amplifier 11U, 11V, 11W. FIG. 9A shows a case where the time constant of the filter 10U, 10V, 10W is not deviated when the energization starts. Specifically, FIG. 9A shows a rising waveform of each phase voltage and the U phase position detection signal. FIG. 9B shows a case where the time constant of the filter 10U, 10V, 10W is not deviated when the energization stops. Specifically, FIG. 9B shows a falling waveform of each phase voltage and the U phase position detection signal. FIG. 9C shows a case where the time constant of the filter 10U, 10V, 10W is deviated when the energization starts. Specifically, FIG. 9C shows a rising waveform of each phase voltage and the U phase position detection signal. FIG. 9D shows a case where the time constant of the filter 10U, 10V, 10W is deviated when the energization stops. Specifically, FIG. 9D shows a falling waveform of each phase voltage and the U phase position detection signal. Here, the deviation of the time constant of the filter 10U, 10V, 10W is about 30% in FIGS. 9C and 9D. IXC and IXD represent a period in which the position detection signal is not obtained since the time constant of each filter 10U, 10V, 10W is deviated.
In FIGS. 9A and 9B, the U phase position detection signal is accurately outputted. In FIGS. 9C and 9D, a rise time of each phase voltage is deviated from a rise time of a reference voltage since the virtual neutral point potential as the reference voltage of the comparator 12U, 12V, 12W is obtained from a summation of three phase induced voltages. Thus, the comparator 12U, 12V, 12W cannot compare a level between the output signal of the buffer amplifier 11U, 11V, 11W with the VNP potential. Accordingly, the U phase position detection signal is not accurately outputted.
Thus, it is required for the motor driving device with a rotor position detection circuit to provide an accurate energization timing even of a time constant of a low pass filter is deviated from a predetermined value.

Rotor position detection circuit and motor driving device


An exercise machine has a swing structure mounted on a frame for both swinging and lateral movement. The frame has a top portion. A ring is pivotally connected to the top portion of the frame. The swing structure is rotatably coupled to the ring and adapted for engaging the feet of a user. A seat is attached to an upper surface of the swing structure.

1. Field of the Invention
This invention relates generally to exercise machines, and more particularly to a multi-functional swing exercise machine.
2. Description of Related Art
It is well known that physical activity is required to develop and maintain physical fitness. Many different types of exercise machines are available that are designed to force one or more muscles to push or pull against a mechanical resistance. However, most exercise machines are large, heavy and structurally complex. It would be beneficial to have an exercise machine that is relatively small and simple, and light enough in weight to be highly portable.
Besides exercising to stay in shape and lose weight, people exercise to build muscles and relieve stress. Unfortunately, it is difficult to tone muscles without the use of weights or a means of resistance. Accordingly, people are limited as to where they can exercise to effectively tone their body areas and parts.
For example, Davis, U.S. Pat. No. 6,752,745, teaches an exercise apparatus utilized for toning and building muscles in different areas of the body, including the arms, chest, shoulders, abdominal muscles, thighs, calves, and hips. The exercise apparatus has a support assembly, having a horizontal bottom support bar, and various components positioned along the support bar. The components include a seat assembly located at the rear end, a pair of thigh press bars located at the middle portion, a foot support assembly located at the front end, and elastic bands. The elastic bands are attached between different movable parts of the apparatus in order to provide resistance to the user when attempting to move such movable parts with respect to each other while exercising. The above-described reference is hereby incorporated by reference in full.
The prior art teaches exercise machines for toning the abdominal portion of a user's body. However, the prior art does not teach a swinging type exercise device that includes the structures and benefits of the exercise machine described below. The present invention fulfills these needs and provides further related advantages as described in the following summary.


A cavity resonator having temperature compensation which comprises a pot and a cover, which together enclose a cavity resonance volume. The pot comprises a first material, which has a first temperature expansion coefficient and the cover comprises a second material, which has a second temperature expansion coefficient. The second temperature expansion coefficient is greater than the first temperature expansion coefficient, and an expansion of the pot and a deformation of the cover results upon a temperature increase, which each independently and also together cause an enlargement of the cavity resonance volume. Simultaneously, the resonance frequency remains essentially constant.

The present invention relates to cavity resonators and particularly their use in oscillator circuits.
Resonators are important components, which may be used in greatly varying applications. Thus, for example, microwave systems require high-quality resonators, which are used in filters and oscillator circuits. A choice must be made between cavity resonators and dielectric resonators, the size, the weight, the costs, and other aspects being able to play a role.
Cavity resonators in the various known embodiments are subject to a change of the resonance frequency in the event of temperature change, which is undesirable for most applications. A temperature change may result due to a change of the ambient temperature, due to a temperature change in an integrated oscillator circuit, or due to losses which occur in the resonant cavity. A change of the dimensions of the resonator results due to a temperature change, which results in the cited change of the resonance frequency.
There are various approaches for reducing the temperature influence on resonators. For example, it is possible to reduce the resonance frequency change caused by a temperature change by inserting a dielectric part into the cavity, the dielectric part having to have a suitable temperature coefficient of the dielectric permittivity.
Another possibility is to construct a cavity from various materials having different temperature expansion coefficients. This possibility is well-known and is used for "coaxial reentrant cavity" resonators. An example of such a resonator is described, for example, in Japanese Patent JP 52075154, which was published on Jun. 23, 1977. FIGS. 1A and 1B show a resonator 10 according to this Japanese patent in a greatly simplified illustration. As may be seen from FIGS. 1A and 1B, there is a rod 12, which penetrates coaxially into a cavity 11 of the resonator 10. A state having lower temperature T is shown in FIG. 1A. If the temperature is increased to T′, the cavity 11 expands, as indicated by arrows around the circumference in FIG. 1B. The rod 12 becomes longer in the event of a temperature increase. If the materials of the cavity 11 in the rod 12 are selected so that the rod 12 experiences a smaller expansion, the capacitive gap (area 13) between the lower rod end and the lower wall of the cavity 11 becomes larger. This change of the capacitive gap (reduction of the capacitive load of the resonator in the event of a temperature increase) in the area 13 results in the resonator frequency of the resonator 10 remaining relatively constant in a specific temperature range. A disadvantage of such a reentrant cavity resonator 10 is the relatively poor quality factor Q. Especially at high frequencies above 10 GHz, the quality factor Q worsens noticeably because of the high field concentration in the capacitive gap and its immediate surroundings.
There are other resonators which are equipped with means for compensating for the temperature influence. These types of resonators are also referred to as "clamped cavity" resonators. An example of such a resonator may be inferred from U.S. Pat. No. 2,528,387. The cavity of the resonator is designed according to this approach in such a way that the geometric changes which would normally result due to a temperature change are locally restricted or even suppressed. This may be performed by a suitable selection of materials and measures which ensure that the volume of the resonator is kept constant by compensating for an enlargement of the cross-section through a reduction of the length. Further similar examples may be inferred from U.S. Pat. No. 4,706,053 and U.S. Pat. No. 6,529,104, which also each suggest means for keeping the volume of a resonator nearly constant in the event of a temperature change.
Other resonators are in turn manufactured from Invar® or similar materials, which have a low temperature expansion coefficient. However, Invar is expensive and difficult to process.

Cavity resonator, use of a cavity resonator and oscillator circuit


In accordance with an embodiment of the present invention an improved equalization system for DMT based modem receiver is provided. It includes a time domain equalizer for processing samples from an analog front end and includes a device for computing differences of time domain samples for every frame and the results are saved. An FFT is provided for calculating a first FFT and the results are saved in a FFT buffer so that at each DMT frame, after a difference and FFT operation, the FFT buffer contains the first FFT and v−1 time domain sample differences. A sliding FFT for each tone reads the first FFT result and v−1 FFTs and recursively computes the rest of v−1 FFTs for the particular tone. An equalizer is responsive to the computed sliding FFT for recursively computes equalizer outputs.

Multi-tone modulation is the basis of the DMT version of ADSL as well as multi-carrier versions of VDSL. This type of modulation is sometimes called orthogonal frequency division multiplexing (ODFM). DMT has more than one encoder and each encoder receives a set of bits that are encoded using a constellation encoder. The output values are the cosine and sine waves and a different cosine and sine frequency is used for each constellation encoder. All the sine and cosine waves are summed together and sent over the channel. Equalization is done by adaptive filters to optimize or nearly optimize transmission. Anytime a channel's frequency response is not flat over the range of frequencies being transmitted inter symbol interference (ISI) occurs.
A per tone equalization for DMT-based systems has recently been proposed. See article by Katleen Van Acker, Geert Leus, Marc Moonen, Oliver van de Weil, and Thierry Pollet, "Per Tone Equalization for DMT Based Systems," IEEE Transactions Communications, vol. 49, No. 1 pp 109-119, January 2001. The method designs an optimum equalizer for each individual tone and has the potential of achieving an optimum design for DMT based modem systems. The method is summarized by the following.
The traditional DMT modem receiver is first formulated mathematically. To simplify the discussion, it is assumed that the time domain equalizer (TEQ) operates on DMT frames that are perfectly aligned and the length of TEQ and the size of the cyclic prefix are the same. The time domain equalizer removes inter symbol interference from the channel that is longer than the cyclic prefix. The cyclic prefix adds the last L sample points of the 512-point time-domain vector to the beginning of the vector. The interference would otherwise cause a symbol to interfere with the next symbol in time. The time domain equalizer also is used to band pass filter the incoming signal and filter out the out-of-band energy. Let y represent a perfectly aligned DMT frame with cyclic prefix as follows:y=[y0, . . . , y1, . . . , yN+v−2, yN+v−1],  (1)                where N is the size of regular DMT framed and v is the size of cyclic prefix. The standard receiver with time equalization (TEQ) can be represented as follows,
                                          [                                                                                z                    1                                                                                ⋮                                                                                z                    N                                                                        ]                    =                                                    (                                                                                D                        1                                                                                0                                                              …                                                                                0                                                              ⋰                                                              0                                                                                ⋮                                                              0                                                                                D                        N                                                                                )                            ·                              F                N                                      *                          (                              Y                *                                  w                  teq                                            )                                                                                where                            (        2        )                                Y        =                              [                                                                                y                                          t                      ,                      o                                                                                y                                              t                        ,                        1                                                                                …                                                                                y                                          t                      ,                                              v                        -                        1                                                                                ]                    =                      (                                                                                y                    v                                                                                y                                          v                      -                      1                                                                                …                                                                      y                    1                                                                                v                                          v                      +                      1                                                                                y                    v                                                                    …                                                                      y                    2                                                                                ⋰⋰                                                                                y                                          N                      +                      v                      -                      1                                                                                y                                          N                      +                      v                      -                      2                                                                                …                                                                      y                    N                                                                        )                                              (        3        )            and wteq=[w0 w1 . . . wv−1]T is real v-tap TEQ. FN is N×N Fast Fourier Transform (FFT) matrix., Di the complex 1-tap frequency equalization (FEQ) for tone i, and Y is an N×v Toepliz matrix which contains exactly the same received signal samples as vector y in equation (1). For a single tone, one can rewrite the equation (2) as:Zi=Di*rowi(FN)*(Y*wteq)=rowi(FN*Y)*wteq*Di=rowi(FN*Y)wfeq,i  (4)
By putting Di to the right, one has wteqDi=(wfreq,i)vxl which is a complex v-tap for tone i. The next step then is to allow each tone to have its own optimal v-tap complex frequency equalization (FEQ) as proposed in the cited Van Acker et al. reference.
A per tone equalizer needs to compute a series of Fast Fourier Transforms (FFTs) for each DMT frame as shown in equation (4). Because for each subsequent FFT its time domain samples is only one sample different from its previous FFT, only the very first FFT needs to be computed. The subsequent FFTs can be efficiently calculated by sliding FFT as discussed in the cited Van Acker et al. reference.
Because each tone has its own equalizer, each filter can be optimally designed using minimum mean squared estimation (MMSE) method which is known in the art. The DMT receiver based on per tone equalizer has the potential to achieve optimum performance. Simulation results show that it outperforms almost all the time equalization (TEQ) design algorithms.
Although a per tone equalizer as proposed by the cited Van Acker et al. reference can potentially achieve optimum equalization performance, it is very complex to implement. Each equalizer is a multi-tap complex filter. It demands both high computational complexity and consumes a large amount of data memory.

Architecture for per tone equalizer with reduced complexity for DMT-based xDSL modems


A progressive power lens (L) is illuminated with a collimated light beam through an illuminating optical system (2) comprising an LED (5), a pinhole plate (6), and a collimator lens (7). The shadow of the hidden mark of the progressive power lens (L) is projected onto a screen (4) by the light beam transmitted through the progressive power lens (L).

1. Field of the Invention
This invention relates to a hidden-mark observing apparatus that observes the hidden marks of a lens to be examined (hereinafter referred to as a subject lens), particularly, of a progressive power lens (i.e., varifocal lens) and relates to a lens-meter that is capable of observing these hidden marks.
2. Description of the Related Art
In general, there are painted marks and stamped marks on the surface of an unprocessed progressive power lens. From a painted mark, the lens maker, lens type, and the distance portion and near portion positions of the lens can be identified. Therefore, when the power of an unprocessed progressive power lens is measured by, for example, a lens-meter, the measurement can be performed at the marked position. However, if once an unprocessed lens is processed and the framing is completed, the painted mark will be wiped off by alcohol and the like and therefore it will be very troublesome to investigate the addition power of the framed progressive power lens even by the use of a latest lens-meter with a progressive measuring function.
On the other hand, the hidden mark stamped on the progressive power lens surface includes the lens' geometrical center position, added lens power, and so on, in addition to the lens maker and the lens type. Therefore, if the stamped mark is deciphered, the added lens power, etc., can be identified.
However, the hidden mark is a very shallow stamp so that it does not become a hindrance when actually used. For this reason, in order to perform the specification or decipherment of the hidden mark position, the hidden mark is held before a fluorescent light, or the reflection at a shallow angle is viewed. However, there is a problem in that the discovery and decipherment of hidden marks are very difficult for an unskilled person.

Hidden-mark observing apparatus and hidden-mark observable lens-meter


A printed board includes: a transmission line that includes a curved region in which a first signal line and a second signal line are arranged separately from each other and curved, wherein the second signal line is arranged on an inner side of the curved region with respect to the first signal line in the curved region and has a portion extending away from the first signal line on a path arranged to be circuitous and extending partially toward the first signal line in the curved region.

Differential transmission is a transmission method that causes currents with opposite phases to flow in two signal lines and transmits signals using the potential difference between the signal lines. The differential transmission has advantages of high-speed data transmission, high tolerance to noise, and low emission of electromagnetic interference (EMI) noise, compared with single-ended transmission.
In the differential transmission, if phases of two signals, pulse widths of the signals, or amplitudes of the signals are shifted from each other, an unbalanced component that is called a skew may occur. The unbalanced component causes the occurrence of a noise current called a common mode current and causes an erroneous operation of a system. Thus, a differential transmission line has a configuration for suppressing the occurrence of an unbalanced component.
For example, a technique for suppressing undesired mode conversion in a curved region of a transmission line has been proposed. According to this technique, the differential transmission line has a board, a grounded conductive layer formed on the top side of the board, and first and second signal conductors arranged side by side on the bottom side of the board. The first signal conductor and the grounded conductive layer form a first transmission line. The second signal conductor and the grounded conductive layer form a second transmission line. The differential transmission line is formed of the first transmission line and the second transmission line. The differential transmission line includes a curved region. Both ends of the curved region are connected to straight regions. It is assumed that the width of the signal conductor in the curved region is Wb1, the width of the second signal conductor in the curved region is Wb2, the width of a gap between the first signal conductor and the second signal conductor is Gb, the width of the first signal conductor in the straight regions is Ws1, and the width of the second signal conductor in the straight regions is Ws2. In addition, it is assumed that the width of a gap between the first signal conductor and the second signal conductor is Gs, a minimum distance between the center of the curvature of the curved region and a line edge, located on the side of the center of the curvature of the first signal conductor, of the first signal conductor in the curved region is Rb1, and a distance between the center of the curvature of the curved region and a normal to a straight line extending from a line edge, located on the side of the center of the curvature of the first signal conductor, of the first signal conductor in the straight regions is Rs1. According to this technique, undesired mode conversion in the curved region of the transmission line is suppressed by setting these the values Wb1, Ws1, Wb2, Ws2, Gb, Gs, Rb1, and Rs1 so as to ensure that Wb1 is smaller than Ws1, Wb2 is smaller than Ws2, Gb is smaller than Gs, and Rb1 is larger than Rs1.
In addition, the following technique has been proposed: a technique for suppressing a reduction, caused by the unevenness of differential impedance of a differential transmission line, in the quality of transmission in a printed board in which the differential transmission line composed of a first wiring and a second wiring and an element connected to the differential transmission line are mounted in a wiring layer that is in contact with a dielectric layer. According to this technique, the width of the first wiring and the width of the second wiring are gradually reduced to a predetermined width on the side of one of ends of each of the first and second wirings, and the first and second wirings are axisymmetric in a region in which the widths of the first and second wirings are gradually reduced.
International Publication Pamphlet No. 2007/000934 and Japanese Laid-open Patent Publication No. 2005-340506 are examples of related art.
FIG. 1 is a diagram illustrating an example of a wiring pattern of a pair of signal lines that form a differential transmission line. A differential transmission line 100 includes a first signal line 101 and a second signal line 102. The first and second signal lines 101 and 102 are curved at an angle of 90° in a curved region 103. The second signal line 102 is arranged on the inner side of the curved region 103 and is a meander line curved and extending away from the first signal line 101 and the difference between the lengths of the first and second signal lines 101 and 102 is reduced. If the difference between the lengths of the first and second signal lines 101 and 102 is large, the difference between the phases of two signals transmitted in the first and second signal lines 101 and 102 may occur and cause the occurrence of an unbalanced component. It is, therefore, preferable that the difference between the lengths of the first and second signal lines 101 and 102 be small.
However, if the differential transmission line includes the meander line, the area of a region occupied by the signal lines may be large and it may be difficult to design a pattern of the differential transmission line. FIG. 2 is a diagram comparing a region (illustrated on the upper side) occupied by differential transmission lines including meander lines with a region (illustrated on the lower side) occupied by differential transmission lines without a meander line. In an example illustrated in FIG. 2, differential transmission lines 100A to 100D that include meander lines are arranged side by side, form four signal line pairs, and extend in a direction intersecting with a direction in which signal lines extend, and differential transmission lines 100E to 100H without a meander line are arranged side by side, form four signal line pairs, and extend in the direction intersecting with the direction in which the signal lines extend. The differential transmission lines 100A to 100D that form the signal line pairs have meander portions 101A to 104A included in signal lines of the signal line pairs and curved and extending away from the other signal lines of the signal line pairs. It is assumed that inter-wiring distances (wiring pitches) L between the signal lines of the differential transmission lines 100A to 100D including the meander lines and inter-wiring distances (wiring pitches) L between the signal lines of the differential transmission lines 100E to 100H without a meander line are equal to each other and that distances M between adjacent differential transmission lines are equal to each other. As illustrated in FIG. 2, a region R1 in which the differential transmission lines 100A and 100D that form the four pairs and include the meander lines are arranged is larger than a region R2 in which the differential transmission lines 100E to 100H that do not include a meander line are arranged. In addition, as illustrated in FIG. 3, if the differential transmission lines 100A and 100D that form the four pairs are curved, the area of the region occupied by the differential transmission lines 100A and 100D is further increased.
As described above, if a differential transmission line includes a meander line, the area of a region occupied by signal lines of the differential transmission line is increased. In order to suppress the increase, it is considered that the widths of curves of the meander line are reduced. In this case, however, the number of the curves is increased in order to reduce the difference between the length of the meander line and the length of another line of the differential transmission line. If a sufficient number of curves are not secured, the difference between the lengths may not be sufficiently reduced.

Printed board and wiring arrangement method


A system for monitoring a workload for a data content delivery apparatus of a communications network. The delivery apparatus delivers content to mobile users via buffered RF link over a fixed bandwidth. A last router routes the content from the delivery apparatus to RF link buffer(s) for transmission to the users. A monitor determines, from the delivery apparatus, parameters describing the content and determines, from the router, bandwidth utilization via the buffer(s), and reports, to the delivery apparatus, bandwidth available for allocation to the content based on the parameters and the bandwidth utilization. The system tracks overall data transfer rates for the network and provides information that can be used to optimize available bandwidth.

Broadband data and video services have not been widely available to users on mobile platforms such as aircraft, boats, trains, and automobiles. Network systems have traditionally been limited in bandwidth and link capacity, making it prohibitively expensive and/or unacceptably slow to distribute such services to all passengers on a mobile platform. Certain limited services are available to provide video programming to a mobile platform. For example, one service provides either TV broadcast services from available direct broadcast signals (i.e. Echostar® and DirecTV®) or provides a custom TV broadcast signal through dedicated satellite links (i.e. Airshow®).
Limited Internet access also is currently available to a user on a mobile platform. For example, a narrow-bandwidth Internet connection is available via a standard computer telephone modem between a user's computer and the air-ground or ship-shore telephony system. Another service is anticipated to provide world-wide-web content to users on a mobile platform. The web content, however, is pre-stored on a server located on the mobile platform and is updated while the platform is in an inactive mode, for example, when an aircraft is parked at an airport gate or when a ship is docked at a port.
A system described in co-pending U.S. patent application Ser. No. 09/639,912, the disclosure of which is incorporated herein in its entirety by reference, provides bi-directional data services and live television programming to mobile platforms. Data content is transferred via satellite communications link between a ground-based control segment and a mobile RF transceiver system carried on each mobile platform. Each user on each mobile platform is able, using a laptop, personal digital assistant (PDA) or other computing device, to interface with an on-board server. Each user can independently request and obtain, for example, Internet access, company intranet access and live television programming. Real-time programming is supplied, for example, by Direct Broadcast Satellite (DBS) service providers such as Echostar® and DirecTV®. The content is kept fresh by periodic updates from at least one ground-based server.
As on-board users make various requests for data content and network access, the ground segment must coordinate the requests and deliver the requested content in a timely manner to each platform from which requests have originated. As passengers make use of on-board communication services with increasing frequency, it becomes increasingly desirable to optimize usage of fixed bandwidth so that quality of data transmission to the platforms can be maintained at levels acceptable to onboard users of these services.

System and methods for monitoring a network workload


The object of the claimed hearing aid device is to improve the speech intelligibility of a speech signal transmitted by the hearing aid device. To this end provision is made to define a maximum gain of the input signal and to determine a target gain at least at a first and second frequency of an input signal. A resulting gain is set in the hearing aid device, which does not exceed the maximum gain. A reduction of the resulting gain compared with the target gain at the first frequency is compensated for according to the invention by an automatic increase in the set resulting gain compared with the target gain at the second frequency, with compensation preferably being achieved by improving the speech intelligibility of a speech signal transmitted with the aid of the hearing aid device.

With modem hearing aid devices there are a large number of possible options for adjusting the transmission function, in other words the gain of an input signal over frequency. In particular the transmission function of a modem hearing aid device can be adjusted by tailoring the hearing aid device to the individual hearing loss of a user.
A method for tailoring the transmission characteristics of a hearing aid device defined by parameters specific to the hearing aid device using a personal computer is known from DE 44 18 203 C2, a memory for base values of a hearing aid device setting in conjunction with an algorithm and a data memory supplying a transmission characteristic of the hearing aid device and displaying it on the screen of the personal computer as a graphic curve.
It is also known that the transmission response of a hearing aid device can also change during normal operation of the hearing aid device. On the one hand the user can change the transmission characteristics of the hearing aid device by manual activation of operating elements on the hearing aid or a remote control unit. It is thus possible for example to switch between different hearing programs or to vary the volume setting. Modem hearing aid devices are also frequently equipped with different automatic systems, which automatically influence the transmission function as a function of the current ambient situation or specific system states.
A method for operating a hearing aid device is known from DE 101 31 964 A1, in which a transmission characteristic of maximum gain over frequency is determined. If, due to an automatic or manual change of parameters relating to signal processing in the hearing aid device, the gain is now increased beyond the characteristic of maximum gain in one specific frequency range at least, the resulting gain in this frequency range is limited automatically to the preset maximum gain for the frequency range in question.
Hearing aid device wearers frequently encounter the problem that the speech intelligibility they experience does not correspond to the speech intelligibility of a person with normal hearing, despite the use of a hearing aid device. Different speech intelligibility models are known from the prior art, which show the frequency ranges that are particularly important for speech intelligibility. This knowledge can advantageously also be used to adjust devices that reproduce or transmit speech, such as hearing aid devices.
A method is known from U.S. Pat. No. 5,729,658, with which speech intelligibility can be quantified for a device that transmits, amplifies or reproduces acoustic speech signals. This makes it possible to compare different devices or different settings of a device in respect of their speech reproduction.

Automatic gain adjustment for a hearing aid device