The invention is a termination circuit which may be used to terminate a tester end of a transmission line between the tester and a digital device under test (DUT). The termination circuit is a clamp circuit which acts as a non-linear resistor of infinite resistance for termination voltages between zero volts (or low logic level voltage) and the power supply voltage V.sub.cc (or high logic level voltage) of the DUT, and which provides a substantially constant slope resistance set to equal the characteristic impedance (Z.sub.O) of the transmission line for voltages outside this range. Given that the output impedance of the DUT is less than the characteristic impedance Z.sub.O of a transmission line, and given the characteristics of the clamp circuit, all reflections on the transmission line as a result of unmatched impedances are totally eliminated by the clamp in twice the delay time of the transmission line. After the reflections are eliminated, the clamp acts as an open circuit. This clamp circuit may be used in virtually any application where reflections are a concern.

The dynamic operating characteristics of an integrated circuit (IC), such as switching speed characteristics and min./max. edge-to-edge timing of waveforms, are typically determined by an automatic tester. For example, the tester may be programmed to transmit a series of test waveforms to various input/output (I/O) ports of a device under test (DUT), such as an IC, and measure the resulting output levels and response times of the IC. Such testing may determine whether the IC works properly and also determine the required timing of any input signals for the proper operation of the DUT.
Since such response times of the DUT are generally on the order of a few nanoseconds (ns), the transmission lines connecting the DUT to the tester should have a minimum of delay, as will be further explained later, even though this delay is taken into account by the tester when calculating the response times. A transmission line approximately 0.5 meters in length connecting a tester to a DUT may have a delay on the order of 2.5 ns.
To avoid or limit reflections of a transmitted step voltage propagating back through the transmission line due to unmatched impedances of the DUT or tester with the transmission line, the input impedance of the DUT and the tester must ideally match the characteristic impedance (Z.sub.O) of the transmission line so that all the energy provided to the input of the DUT or tester by the transmission line is completely absorbed by the DUT or tester.
In a normal operating environment for an IC (e.g., on a circuit board), the IC ports are generally connected to other devices by transmission lines of only a few inches in length, so although reflections may exist, the reflections die out within a short period of time due to the small time delay between the ends of these short transmission lines. However, in a test setup where a DUT is connected to a tester, the transmission lines are much longer and thus the relatively long delay before any reflections die out may cause a reflected step voltage to be misinterpreted as an intentionally generated test or response signal, resulting in inaccurate test results.
Further, since many pins of an IC may be bi-directional, switching from an input mode to an output mode in only a few nanoseconds, even reflections lasting only a few round-trips of the transmission line may cause the IC, having an I/O pin which has been switched from an output mode to an input mode, to undesirably be triggered by a reflected step voltage.
This problem with reflections is especially acute as the operating frequencies of the DUT increases and the rise times of the tester and DUT waveforms fall, since reflected signals being delayed several nanoseconds due to the transmission line propagation delay will be more likely to be misinterpreted as an intentionally generated test or response signal.
Similar problems with reflections may also exist where a high speed electrical device is connected to any device, not just a tester, by a relatively long transmission line.
FIG. 1 generally illustrates a prior art connection between a DUT 10 and an automatic tester 14 via a transmission line 16. FIG. 1 shows only a single transmission line connected to a single I/O pin 18 of DUT 10 for purposes of illustrating the present problems with reflections during testing of DUT 10. In an actual test setup there would typically be one transmission line for each I/O pin of DUT 10.
It will be assumed for purposes of explaining how a reflection occurs that the output signal of DUT 10 is provided by a CMOS output buffer 20, represented by a pull-up resistor having a value R.sub.hi (actually a PMOS device) and a pull-down resistor having a resistance of R.sub.lo (actually an NMOS device). In response to a control signal by DUT 10 to CMOS buffer 20, pin 18 is switched to either power supply voltage V.sub.cc through resistor value R.sub.hi or to ground via resistor value R.sub.lo. Such switching may occur at rates up to 20 MHz or faster.
A typical transmission line 16 connecting DUT 10 to tester 14 will have a characteristic impedance (Z.sub.O) on the order of 50-100 ohms, where characteristic impedance Z.sub.O is given by the equation, EQU Z.sub.O =.sqroot.L/C (eq. 1)
where
L equals the inductance of the transmission line per unit length, and PA1 C equals the capacitance of the transmission line per unit length. PA1 V.sub.r is a reflected step equal to the voltage that the termination is driven to (V.sub.t) minus the voltage at the other end of the transmission line (V.sub.a) which gave rise to the termination voltage.
Tester 14 will be assumed for this case to incorporate a comparator 24 having an input terminal coupled to transmission line 16 for comparing the input signal from transmission line 16 to a threshold voltage V.sub.th on line 26.
The input impedance of tester 14, determined by shunt resistor 27 having a value R.sub.t, is typically set to match the Z.sub.O of the transmission line 16 so that any input signals will be completely absorbed and no reflected signals created. Since the same transmission lines are typically always used with the tester, the manufacturer of the tester may easily fix this input impedance value R.sub.1 to match the Z.sub.O of the transmission line.
Tester 14 may also include a transmitter 28 selectively coupled to transmission line 16 for supplying a test waveform to DUT 10, where pin 18 of DUT 10 would first be configured to be in an input mode instead of in an output mode as shown in FIG. 1.
The prior art also sometimes incorporates diodes, such as diodes D1 and D2 in FIG. 1, at the tester termination of transmission line 16 to prevent any termination voltages from rising significantly above a threshold voltage V.sub.x and significantly below ground voltage. However, one problem with using diodes in the configuration of FIG. 1 is that V.sub.x and V.sub.y must be carefully adjusted for each DUT 10, since each DUT 10 has different characteristics which would affect the value of V.sub.x and V.sub.y.
Although the input and output impedance of tester 14 may be preset to match the Z.sub.O of transmission line 16, DUT 10 will most likely have an input impedance well above the Z.sub.O of transmission line 16 and have an output impedance well below the Z.sub.O of transmission line 16. For example, the input impedance of MOSFET input buffers are extremely high due to the insulated gate of the MOSFET, and fast MOSFET output buffers may have output impedances as low as 5 ohms. Thus, any test signal or reflected signal being provided to a pin of DUT 10 will most likely cause another reflected signal to be sent back along transmission line 16 away from DUT 10.
If neither the total terminal impedance R.sub.t of tester 14 or the impedance of pin 18 of DUT 10 is equal to the Z.sub.O of transmission line 16, then the series of reflections back and forth across transmission line 16 will repeat until these reflections die out in an exponential manner due to the attenuation in the system. The time between the steps of these reflected waveforms returning to a same terminal is twice the delay time of transmission line 16.
For simplicity, the below discussion, providing a mathematical basis for understanding reflections on a transmission line, will ignore the effect of diodes D1 and D2 in FIG. 1 and set the R.sub.hi value of the pull-up resistor of CMOS buffer 20 in FIG. 1 to R.sub.g.
In FIG. 1, if CMOS output buffer 20 puts a positive step voltage transition on transmission line 16 by connecting transmission line 16 to V.sub.cc through resistance R.sub.g, the amplitude of the step at node A shown in FIG. 1 will be EQU V.sub.a =V.sub.cc *Z.sub.O / (Z.sub.O +R.sub.g). (eq. 2)
The step of voltage V.sub.a propagates along transmission line 16 and reaches tester 14 where it produces a voltage V.sub.t across the terminating resistor R.sub.t, where EQU V.sub.t =2*V.sub.a *R.sub.t /(Z.sub.O +R.sub.t) (eq. 3)
Since R.sub.t is typically not exactly equal to Z.sub.O, there will be a reflected step which propagates back to BUT 10 with an amplitude of EQU V.sub.r =V.sub.t -V.sub.a, (eq. 4)
where
In the condition where Z.sub.O =R.sub.t, V.sub.r is zero and the activity on the line stops with a constant voltage throughout the line until the output of DUT 10 is again switched. If Z.sub.O does not equal R.sub.t then when the reflected step V.sub.r reaches pin 18 of DUT 10 it may be completely absorbed (if R.sub.g =Z.sub.O) or a new reflection will start traveling away from DUT 10.
If neither the source or the load impedances are equal to Z.sub.O, then the series of reflections is infinite, dying out in an exponential manner, with the time between steps of these waveforms being twice the delay time of the transmission line.
To make test results most valuable to a user of the DUT, realistic loading conditions should be used when testing the DUT. For example, a single output buffer in DUT 10 may drive a number of output pins of DUT, where all of these output pins are intended to be coupled to a high impedance input of another IC, such as to an input of a CMOS device. A CMOS output device in a DUT could possibly drive a single terminated transmission line, such as transmission line 16, directly since the load provided by the single transmission line and the tester (e.g., R.sub.t) will not overload the CMOS output device. However, a CMOS output device in a DUT driving a number of outputs, and hence a number of transmission lines, generally could not be so heavily loaded and still operate as it would in a realistic environment. To ameliorate this problem, the prior art, to reduce the loading on a DUT output buffer, inserts a series resistor between the appropriate DUT pin and the transmission line leading to the tester. The tester end of the transmission line is then terminated by a shunt resistor equal to the characteristic impedance (Z.sub.O) of the transmission line, where one end of the termination resistor is coupled to a voltage about midway between ground and the power supply voltage V.sub.cc to compensate for the voltage drop across the series resistor. Thus, a number of these high impedance transmission lines may be driven by the CMOS output device without unduly loading the CMOS output device.
When the output device in the DUT now drives one or more tester inputs, the final voltage produced at the tester inputs is a good, but attenuated, representation of the DUT output voltage. In the case of a 50-ohm transmission line, the resistor placed in series with the DUT output may be 150 ohms, and the termination resistor will be 50 ohms to match the transmission line Z.sub.O. This would provide an effective 4:1 attenuation of the DUT output voltage across the termination resistor.
One disadvantage to this approach is that, when the bi-directional pin of the DUT connected to the series resistor is now controlled to be an input port, and the tester now drives this DUT pin through the series resistor, the extra impedance (150 ohms in the example given) will undesirably greatly increase the rise time of the tester drive waveform at the DUT pin due to the RC low pass filter formed by the series resistor and the input capacitance of the DUT.
Further, during a DC test of the DUT where a DC current is used to load the DUT outputs to see the effect on the output voltages and to determine the output impedance of the DUT, the range of load currents that can be applied during this test is restricted because the voltage drop across the series resistor has to be accommodated by the tester current source, and the measurement of the DUT output voltage by the tester must precisely account for this resistor voltage drop. Thus, this approach for preventing an unduly heavy load on a DUT output has numerous drawbacks which adds to the complexity of testing a device.
Still further, since each DUT type generally has output devices having a different output impedance than that found in other DUT types, the series resistor has to be adjusted to take into account these various output impedances so that the tester can take account of the precise voltage drops which occur between the tester and the DUT. This means that the interface board between the tester and the DUT must be changed for testing different IC's, even in the same basic family.
What is needed in this field is a means to terminate a transmission line coupling a DUT and a tester, wherein the same transmission line and termination means can be used for testing different IC's and wherein the termination would not unduly load any DUT output. This termination should also limit reflections from interfering with the accurate test results obtained by the tester. This termination should also not substantially increase the impedance between the tester and the DUT in a manner which would increase the rise time of any drive waveform.

Method and circuit for controlling voltage reflections on transmission lines


According to the present invention, a bidirectional buck boost DC-DC converter can be obtained, in which power can flow bidirectionally from a primary side to a secondary side and from the secondary side to the primary side, regardless of a magnitude relation between a secondary-side voltage and a primary-side voltage in a state where different DC voltage sources are connected to the primary side and the secondary side in the DC-DC converter. A direction and a magnitude of the power can be automatically controlled to a desired value continuously on instantaneous value basis.

Conventionally, a technology has been known, in which a power storage device such as a secondary battery or an electric double-layer capacitor is applied to a railway system, and kinetic energy of a vehicle is effectively used by storing surplus regenerative power generated when braking the vehicle and using the stored power when the vehicle is accelerated. In this case, a buck boost converter (hereinafter, a bidirectional buck boost DC-DC converter) capable of controlling power in bidirectional directions is used for connecting a direct-current wire and the power storage device (for example, Patent Document 1).
Patent Document 1: Japanese Patent Application Laid-open No. 2005-206111
However, the bidirectional buck boost DC-DC converter as described above cannot control current when a primary-side voltage is lower than a secondary-side voltage in the converter because of the circuit configuration. Therefore, the bidirectional buck boost DC-DC converter needs to be used under the condition that the primary-side voltage is always higher than the secondary-side voltage.
For avoiding such a problem, a DC-DC converter (hereinafter, a bidirectional buck boost DC-DC converter) is useful, which is capable of causing power to flow bidirectionally from the primary side to the secondary side and from the secondary side to the primary side regardless of a magnitude relation between the primary-side voltage and the secondary-side voltage of the bidirectional buck boost DC-DC converter. The circuit configuration thereof is disclosed, for example, in Patent Document 2.
Patent Document 2: Japanese Patent Application Laid-open No. 2001-268900

Bidirectional buck boost DC-DC converter, railway coach drive control system, and railway feeder system


A low-voltage protective switching device includes: at least one line conductor length extending from a line conductor supply connection of the low-voltage protective switching device to a line conductor load connection of the low-voltage protective switching device; a neutral conductor length extending from a neutral conductor connection of the low-voltage protective switching device to a neutral conductor load connection of the low-voltage protective switching device; a mechanical bypass switch and a first mechanical circuit breaker disposed in series in the line conductor length; a second mechanical circuit breaker disposed in the neutral conductor length; a first semiconductor switching arrangement disposed in parallel to the bypass switch; and an electronic control unit that presettably actuates the bypass switch, the first mechanical circuit breaker, the second mechanical circuit breaker, and the first semiconductor switching arrangement. The first semiconductor switching arrangement includes a snubber, which includes a first capacitor.

So-called hybrid switching devices that include mechanical switching contacts as well as semiconductor switches are known in the art. Aside from components that are required for the actual deactivation function, these switches further include mechanical circuit breakers intended to achieve galvanic isolation, when the switching device is in the deactivated state, as required in many countries and/or pursuant to pertinent regulations.
Hybrid switching devices typically include at last one capacitor that is typically arranged in a so-called snubber circuit. After such a hybrid switching device has been deactivated, said capacitor is discharged, which is known in the art, via a resistor, whereby the stored energy and/or charge is converted to heat.
When such a switching device is activated, all the mechanical circuit breakers that are used to achieve the galvanic isolation are closed first. With the first electrically conductive contact of these switching contacts of these circuit breakers, the capacitor begins charging, accordingly drawing a charging current. However, when the switching contacts of the circuit breakers are closed, switching contact bouncing ensues, which causes consecutive, brief interruptions of the electrical contact. As current is already being drawn via these switching contacts, any bouncing of the switching contacts results in a series of light arcs and associated contact erosion. This effect is intensified because, while charging, a discharged capacitor draws the highest current at the beginning. This results in wear of the circuit breaker contacts. Increased resistance of the switching devices is the consequence. As current flows continuously through circuit breakers during the normal operation of the switching device, any wear of the break contacts results in higher self heating of the switching device. The operating life of semiconductor components depends greatly on the ambient temperature, wherefore contact bouncing can reduce the operating life of the switching device. Any failure of the semiconductor switching elements in a hybrid switching device can have serious consequences.
Alternating current applications offer the possibility of mitigating the bouncing effect by providing that the circuit breaker is closed around zero-crossing of the supply voltage, whereby the charging current of the capacitor is reduced during bouncing. Although disadvantageous consequences can be reduced this way, they are not eliminated. In addition, switching and/or securing direct current networks has become increasingly important and has become more and more widespread. Because direct current networks do not have zero-crossings, direct current applications do not provide for the possibility of reducing light arcs by adjusting switching times.


There is a zero power programmable logic device with a one time programmable and fully-testable anti-fuse cell architecture. Specifically, a half-latch and fuse cell circuit allows the PLD to use "zero power" during the standby period since the sense amps are not used to maintain the programmed logic. Additionally, the PLD is capable of being tested for logic gate and logic path integrity, and anti-fuse electrical parameters without permanently programming the anti-fuse.

Historically
The introduction of programmable logic devices (PLD) was a true revolution in the hardware design world. It enabled engineers to shrink circuits requiring several devices onto a single device thus simplifying their designs while saving space and power. Traditionally, PLDs have been used in combinatorial circuits such as address decoders as well as sequential circuits such as bus arbitration schemes. During the last few years, advances and improvements in PLD architectures enabled the devices to grow more complex while addressing the never-ending quest for higher density and faster speeds. Despite these improvements, engineers still face certain problems and limitations with PLDs.
A typical programmable logic device is composed of a user-programmable AND array, a fixed OR gate, followed by an output register which includes a feedback path from the output to the programmable AND array. PLDs also have circuitry for programming the inputs to the AND and OR arrays, and for configuring the output macrocells.

One time programmable fully-testable programmable logic device with zero power and anti-fuse cell architecture


Method and apparatus for providing thermal protection for actuators used in haptic feedback interface devices. An average energy in the actuator over a predetermined period of time is determined, and the maximum allowable current level in the actuator is reduced if the average energy is determined to exceed a predetermined warning energy level. The maximum allowable current level can be reduced to a sustainable current level if the average energy reaches a maximum energy level allowed, and the maximum allowable current level in the actuator can be raised if the average energy is determined to be below the predetermined warning energy level. Preferably, the maximum allowable current level is reduced smoothly as a ramp function.

The present invention relates generally to actuators, and more particularly to actuators used in computer interface devices that allow the user to provide input to computer systems and allow computer systems to provide haptic feedback to the user.
A user can interact with a computer to perform functions and tasks on the computer, such as playing a game, experiencing a simulation or virtual reality environment, using a computer aided design system, operating a graphical user interface (GUI), navigate web pages, etc. Common human-computer interface devices used for such interaction include a mouse, joystick, trackball, gamepad, steering wheel, stylus, tablet, pressure-sensitive sphere, knob, or the like, that is connected to the computer system controlling the displayed environment. In some interface devices, kinesthetic force feedback and/or tactile feedback is also provided to the user, more generally known collectively herein as "haptic feedback." These types of interface devices can provide physical sensations which are felt by the user manipulating a user manipulandum of the interface device, such as a joystick handle, mouse, wheel, etc. One or more motors or other actuators are coupled to the manipulandum and are connected to the controlling computer system. The computer controls forces on the manipulandum and/or device housing in conjunction and coordinated with displayed events and interactions by sending control signals or commands to the actuators. The computer system can thus convey physical force sensations to the user in conjunction with other supplied feedback as the user is grasping or contacting the interface device or manipulatable object of the interface device.
A problem with many types of haptic feedback interface devices, such as haptic knobs, joysticks, and other types of devices, is protecting the actuator(s) of the device from failure due to high temperatures. For example, moving-coil DC motors in haptic feedback devices are typically stalled at high currents, and so have the potential to heat up quickly. For example, a haptic feedback device may output a barrier force or other resistive force, where the user moves a manipulandum in direct opposition to the output force. This can cause excessive heat in an actuator.
A robust haptic feedback product must protect its actuators against excessive coil and magnet temperatures. This problem can be solved by mounting a thermistor directly on the motor coil and using its information to safely regulate temperature. However, it is impossible to mount a thermistor on the moving coil of a typical brushed motor. Other ways must be employed to predict and prevent destructive coil temperatures in brushed motors. More cost effective ways to prevent such temperatures in brushed motors and other types of actuators are also needed.

Actuator thermal protection in haptic feedback devices


The present invention is related to a screening, detection and/or quantification method of one or more transcriptional factor(s) (1) possibly present in a biological sample, said method comprising the steps of:                possibly extracting and isolating said transcriptional factor (1) from said biological sample,        putting into contact the transcriptional factor (1) with a double-stranded DNA sequence (2) bound to an insoluble solid support (3), and        detecting and/or quantifying said fixed transcriptional factor (1),said double-stranded DNA sequence having a specific sequence able to be fixed by the transcriptional factor (1) and being preferably located at a distance of at least about 6.8 nm from the surface of the solid support (3), and said double-stranded DNA sequence being bound to the surface of the insoluble solid support (3) at a concentration of at least 0.01 pmole/cm2 of solid support surface (3).

Transcriptional factors are proteins that bind to specific sequences of DNA, called consensus sequences, and influence the transcription of the DNA into mRNA. Some of these factors directly participate in the transcription process by activating or inhibiting the transcription and regulate the synthesis of proteins needed by cells to function, to adapt, to respond or to differentiate. Some of these proteins have to be transcribed in a constitutive manner (essential role in cell functions) while others are only synthesised in response to specific stimuli or when the cells are for instance in pathological environment. External signals are sensed by receptors and transduced through the plasma membrane followed by cascades of enzymatic kinase reactions, resulting in a phosphorylation or dephosphorylation of the transcriptional factors which affects positively or negatively their binding to their consensus sequence.
An example of drug acting indirectly on transcriptional factor is compactin, an inhibitor of HMG CoA reductase, which leads to an up-regulation of the transcription of the LDL receptor gene, permitting the clearance of cholesterol (U.S. Pat. No. 5,563,036).

Method for the screening, the detection and/or the quantification of transcriptional factors

Abstract: The present invention is also related to the kit comprising means and media for performing said method.


A test device (1) for testing power engineering equipment comprises at least one connection socket (4) which is electrically connected to an overvoltage protection arrangement (2). The overvoltage protection arrangement (2) comprises at least one overvoltage protection element (5) and is configured such that the at least one overvoltage protection element (5) is exchangeable.

In test devices for testing operating resources in electrical high or medium voltage systems, overvoltages may often occur, which reach or are applied to the interior of the test device through the input sockets or output sockets of the test device and may damage or even destroy there components of the test device, in particular the electronics of the test device. Therefore, overvoltage protection elements such as suppressor diodes or overvoltage gas arrester are installed in conventional test devices in order to protect the test device against such overvoltages or surge voltages.
FIG. 1 schematically shows a test device 1 according to the state of the art. The test device 1 comprises a housing 9 with a plurality of sockets 4 or connection terminals 4, each socket 4 being provided for applying an input signal to be evaluated by the test device 1 or for outputting a test signal by the test device 1 via the respective socket. In the example shown in FIG. 1, for protecting the test device 1 against overvoltages, each of the sockets 4 is connected to a separate overvoltage protection element 3 that is fixed installed in the housing 9.
For example, each protection element 3 may be an overvoltage gas arrester. In the case of overvoltage gas arresters, a small arc ignites if a predetermined voltage is exceeded to discharge the overvoltage to earth. Such overvoltage gas arresters may also be equipped with short-circuit springs. In this case, a spacer melts if the arc occurs too long, and the short-circuit spring can then short-circuit the contacts of the overvoltage gas arrester. Thereby, the overvoltage is reduced to almost zero so that the electronics of the test device can be permanently protected against a malfunction or a fault.
Likewise, suppressor diodes such as TransZorb diodes may be used as protection elements, which have a voltage limiting effect but lead to an electric short-circuit if an overvoltage or overload occurs.
The conventional overvoltage protection arrangements have in common that, if an overvoltage occurs, the protection elements respectively used are destroyed similar to a fuse in order to protect the test device against the overvoltage. To restore or repair a test device in which such an overvoltage protection element has been destroyed by an overvoltage, the housing of the test device has to be opened and an extensive, time-consuming and costly repair has to be carried out.
Therefore, it is the object of the invention to provide a test device for power engineering equipment and a method for manufacturing a test device for power engineering equipment with this problem being resolved and it being possible to restore the test device in a simple and cost-effective way even after a damage or destruction of an overvoltage protection element.

Test device for power engineering equipment and method for manufacturing a test device for power engineering equipment


A handrail system comprising a top rail (50) and one or more support posts (25). The rail and post/s may be formed from a synthetic material such as a fibre reinforced plastics material.

Hand rail structures are used in a wide range of circumstances and for a variety of reasons. For example, hand rail structures may be deployed along staircases or walkways to serve as a support for people as they move. Alternatively or additionally hand rail systems can be used as barriers or "fences" to delimit an area.
There are a variety of considerations when designing a hand rail system, primarily safety aspects but also material choice, production techniques and ease of assembly which will influence the properties and performance of the resulting structure that is in turn dictated by, for example, the final application (such as offshore installations).


An enclosed drive system for use in conjunction with a lift cord extending from a headrail of an architectural cover. The enclosed system encases and engages the lift cord with a drive mechanism within the enclosure, thereby avoiding hazardous loops. A method for retro-fitting an architectural cover lift cord assembly including a lift cord associated with a cord lock and extending from a headrail of the architectural cover is also described, for modifying the architectural cover to eliminate hazardous loops therefrom. Also disclosed in this disclosure is a cord lock mechanism that pinches the cord, a handle that actuates the cord lock mechanism, and a driving mechanism having a cord guide that engages the cord and a slider that slides along the handle to actuate the cord while the cord is enclosed within an enclosure defined by the handle.

In the provision of window and architectural passage coverings, the art has long relied on cords, string or the like to extend and retract the coverings. Such coverings take many forms, including shades such as curtains, roll-up shades, Venetian blinds, vertical blinds, cellular shades, and the like. A primary problem with such coverings that rely on cords is that small children can become entangled in the cords and experience serious harm, including strangulation and death. On Aug. 26, 2009, the U.S. Consumer Product Safety Commission announced a voluntary recall of all ¼ inch Oval Roll-up Blinds and Woolrich Roman Shades, including some 4.2 million roll-up blinds and 600,000 Roman shades, (http://www.cpsc.gov/cpscpub/prerel/prhtml09/09324.html). The Commission referenced the hazard that "[s]trangulations can occur if the lifting loops slide off the side of the blind and a child's neck becomes entangled on the free-standing loop or if a child places his/her neck between the lifting loop and the roll-up blind material." Recent cited injuries include a report that "[i]n November 2007, a 1-year-old boy from Norridgewock, Me. became entangled and strangled in the lift cord loop of a roll-up blind that had fallen into his portable crib. In October 2008, a 13-month-old boy from Conway, AR was found with his head between the exposed inner cord and the cloth on the backside of a Roman shade. The cord was not looped around the boy's neck but rather ran from ear to ear and strangled the child." Numerous manufacturers and retailers have followed the recall. Additional information may be found at: (http://www.windowcoverings.org).
In addition to the internal cords attached to the shade or blinds that can be pulled out and pose a problem, the pull cords, string and beaded cords in mechanical-based blinds and shades that are pulled on to draw up the blinds or shades also pose a risk since they also create a hazardous loop of sufficient diameter (12 inches according to the Consumer Product Safety Commission) for a small child to get their head tangled inside. The retrofit devices currently available (http://www.windowcoverings.org/how_to_retrofit.html) do not eliminate the hazardous loops created by the beaded cords even if they are tied to the wall with a tie-down device such as a Rollease™ product or with separated draw strings and/or cord stops that could still become tangled together to create a hazardous loop.
U.S. Pat. No. 5,472,035 discloses a window blind lift cord operating mechanism incorporated into the twist wand that rotates to control tilting of blind slats, wherein the operating mechanism for raising and lowering the blind and locking the blind in adjusted positions includes a lift member mounted for movement along an outer side of the wand that drives an engaging member inside the wand that engages the lift cords that also extend into a lengthwise cord passage inside the wand. The disclosed operating means also includes a lock means for locking the lift cord engaging member at selected positions along the wand. One problem with this configuration is the obvious entanglement issues that would result with the lift cords internal to a wand that is rotated to control tilting of the blind slats, wherein securing the cord within the rotating wand almost guarantees entanglement. In addition, the weight and force required to lift the bottom rail along with the blind slats would create a significant burden on the rotating gears that open and close the blind slats including the entire attachment of the wand to the headrail.
In consequence, the art is in need of improvement in coverings for architectural openings that maintains the functionality and aesthetics of previously developed coverings, but avoids their deficiencies, particularly their hazardous character regarding the risk of injury or death associated with the use of cord arrangements. The art also is in need of a new structural "fix" for the lifting mechanism of shades and blinds that avoids creating a hazardous loop.

Cordless blind system and retro-fit method


A first signal conditioning circuit is formed from a first portion, a second portion and a third portion. Signal conditioning functions of each of these portions are facilitated by a predetermined type of integrated semiconductor die within which they are formed. Two different semiconductor dies are thus provided for facilitating integration of the first through third signal conditioning portions therein. Wire bonds are provided between the two different semiconductor dies in order to form circuit paths between the different first through third portions. The signal routing using between the two different semiconductor dies provides for completing of the first signal conditioning circuit having a first signal conditioning function. For example, circuits such as interstage matching circuits are disposed on a different semiconductor die than power amplifier circuits.

Typically, manufacturers in the area of wireless products wish to implement radio media interface circuits into radio terminals, such as PCMCIA cards or dongles, which typically must operate within the context of two or more radio standards but in accordance with one standard at any one time. These radio standards are for example collectively referred to as the IEEE 802 standard, which is well known to those of skill in the art. This standard is typically divisible into a number of individual radio standards including one standard at 5.8 GHz, known as 802.11a, and another two standards at 2.45 GHz, known as 802.11b and 802.11 g.
In terms of these radio standards, manufacturers are often interested in building radio terminals that will be able to operate at 802.11a, b, and g standards, with only one particular standard being active at any one time. As a result, the manufacturers are interested in acquiring a front-end module that incorporates receive and transmission elements such as the low noise amplifiers (LNA), power amplifiers (PA), impedance matching components, and RF switches for all the standards that the terminal or card must deal with. Thus providing them with flexibility in their radio terminal designs.
Unfortunately, PAs and other components such as the LNA, are highly specialized components that have specifications that generally do not overlap with other radio frequency bands. Thus, a 5.8 GHz PA is generally not suitable for use 2.4 GHz PA. As a result, distinct components such as the LNAs and PAs are incorporated into the module in order to accommodate different radio standards. Moreover, many of the high performance RF components such as PAs and LNAs have a relatively low level of ancillary circuit integration. For example, voltage regulation circuits, temperature regulation circuits, control circuits and other circuits that are used for control and optimization of the operation of the PA are often not integrated into a same die with the PA but rather disposed as discrete components, on separate semiconductor substrates, within the module surrounding the PA die. It is well understood by most module designers that adding more components to the module increases cost, reduces yield and durability while resulting in an increase in module size. This effect is compounded when additional circuitry is used for each active RF component such as an RF switch, LNA, and PA.
Recent advances in SiGe BiCMOS technology have allowed for progressively higher levels of integration of high-performance RF components. For example, a high-performance 2.45 GHz PA for the 802.11b/g standard implemented in SiGe BICMOS technology can incorporate voltage and temperature regulation circuitry along with various power optimization and control schemes manifested in control circuitry. The benefit of such high levels of integration are well understood by the IC design community and include reduced module sizes, reduced cost, reduced assembly time, and increased yield and module longevity. Moreover, for PAs in particular, the robustness of the PA in tolerating of mismatch conditions to the antenna can be improved with voltage standing wave ratio (VSWR) sensing circuitry and PA output power sensing circuitry integrated into the PA chip. In this particular example, a determination of high VSWR might lead to the generation of a control signal to reduce power output and thereby protect one or more PA gain stages from over voltage conditions. Clearly, integration of this type of ancillary circuitry into the PA has the potential to increase PA performance and robustness with a minimum increase in the module size. In respect of LNAs, the integration of bias point control circuitry is important.
However, the usage of SiGe BiCMOS technology in the industry is currently limited. For example, for 5.8 GHz PAs, only a small number of manufacturers are utilizing SiGe for whereas several end users are utilizing GaAs or group III-V based technologies. The GaAs based technologies however offer more gain per stage and lower losses in the RF signal path at 5.8 GHz. GaAs based technology, however, is often unsuitable for the integration of ancillary circuits for use with the GaAs based RF component. Voltage regulation, for example, may not be integrated into the GaAs based PA due to the lack of suitable elementary devices within the GaAs based technology. Therefore, in the context of a module, the module designer is compelled to add those additional circuits, or dies, for supporting of the GaAs based components. As mentioned previously, the addition of more components causes a detriment to the module size and cost.
A need therefore exists to for providing a compact RF module that supports a number of RF standards. It is therefore an object of the invention to provide a compact RF module that overcomes the limitations of the prior art by facilitating integration of multiple circuit components into a same module in order to support a number of RF standards.


A fiber-reinforced thermoplastic composition includes a polypropylene polymer component including a low flow grade polypropylene and a high flow grade polypropylene, and a fiber reinforcement component. The fiber-reinforced thermoplastic composition is capable of being vacuum formed. In another aspect a thermoplastic composition includes a homopolymer component including polypropylene, a co-polymer component, an impact modifier, and one or more of a flame retardant component and a fiber reinforcement component. The thermoplastic composition is capable of being vacuum formed. The fiber-reinforced thermoplastic composition may be formed into an article such as an enclosure for an electrical component, and it may be chemically resistant to a medical grade cleaner.

Glass fiber is typically added to semi-crystalline materials, such as, for example, polypropylene materials, to maintain or improve dimensional stability under extreme temperatures. Unfortunately, the addition of glass fiber also results in diminished elastic properties. Similarly, long fiber reinforcements in thermoplastic resin can improve impact properties of the product. Presence of the long fibers in the composite, however, can also result in an unwanted brittleness of the composite, which can limit its applicability due to performance concerns.
Accordingly, there remains a need for thermoplastic compositions and methods of forming article from the same that can provide improved impact strength properties and other improved properties including the ability to be sterilized for medical applications. These needs and other needs are satisfied by the compositions, articles, and methods of the present disclosure.


In one embodiment, the present invention includes an apparatus having a first amplifier stage to receive an input voltage and to provide an amplified output voltage at an output terminal, where the first amplifier stage is controlled by a first bias current. The apparatus may further include a second amplifier stage coupled to receive a control voltage and to provide an offset voltage to the output terminal, where the second amplifier stage is controlled by a second bias current. The first and second bias currents may be controlled by a single bias controller.

Amplifiers are used in many applications to amplify an incoming signal into an amplified signal. For example, amplifiers are often used in communication systems to boost the level of an incoming signal and sometimes to shape the signal in some desired way. Certain communication systems transmit data with a clock embedded in a data stream, rather than as a separate signal. When the data stream is received, a clock and data recovery circuit (CDR) recovers the embedded clock and retimes the received data to the recovered clock. Oftentimes, a CDR is implemented in an integrated circuit along with additional components, such as a limit amplifier (LA) and other such components. The LA may receive a voltage signal from a transimpedance amplifier (TIA) or other amplifier, which amplifies an incoming converted optical signal.
The function of the limit amplifier is to produce a consistent waveform from the TIA output which can be used by the CDR, regardless of incoming optical energy. In addition to amplifying the input signal, the LA may provide an adjustable slicing level to compensate for an asymmetric noise characteristic present in the incoming data. A slicing level is the threshold voltage at which an incoming signal is determined to be either a "1" bit or a "0" bit. At low levels of optical energy (e.g., corresponding to a zero bit level, for example), the noise current is low. At higher levels of optical energy (corresponding to a one bit), the noise current may be higher. An optimal slice level for an amplifier in a receive path can enhance receiver performance significantly, especially in long-haul applications. Thus an offset is typically inserted into the receive path, either at an input of an amplifier or at an output thereof.
The offset voltage, referred to as a slice voltage in certain applications, is often applied to be summed with the input of an amplifier. This offset voltage may be used to compensate for a slice level at which an amplified signal is to be sampled. Accordingly, the output of an amplifier may correspond to the sum of the input voltage and offset voltage, multiplied by the gain of the amplifier.
Referring now to FIG. 1A, shown is a block diagram of a limit amplifier 10 that receives an incoming voltage, Vin, along with a slice voltage, Vslice, and provides an amplified output signal, Vout. The output voltage of amplifier 10 may be described in accordance with the following equation:Vout=(Vin+Vslice)×GAINLA  (Eq. 1)where GAINLA is the gain of limit amplifier 10. While limit amplifier 10 is shown in FIG. 1A as a differential amplifier, a single-ended implementation is also possible. Further, while the slice voltage is shown as a single-ended input, this voltage may also be a differential signal.
Optical signals are single-ended in nature. That is, a logic one value provides light, while a logic zero signal is dark. There is asymmetry in "1" and "0" signals when they are converted into the electrical domain, creating an asymmetrical data eye pattern. FIG. 1B is an eye diagram of a typical incoming data signal at an input of a LA and an amplified version appearing at the output of the LA. As shown in FIG. 1B, a data eye 20 corresponding to the incoming data is formed by superimposing waveforms of multiple data signals.
As shown in FIG. 1B, an output data eye 30 corresponding to the signal at the output of a LA is clipped at the top and bottom via the limit amplifier. Further shown in FIG. 1B is a slice voltage, Vslice, which corresponds to a widest opening of the eye pattern. The slice voltage may be adjusted depending upon the incoming signal to maintain the slice level at a widest portion of the eye pattern.
In the real world, data signals forming a data eye have transitions with varied rise times and fall times and may also exhibit different voltage levels and shapes. Thus a slicing level may be selected or controlled to obtain an output data eye with its widest opening and a relatively symmetric margin between the positive swing voltage and the negative swing voltage. To achieve the desired output signal, an introduction of an intentional offset may be effected, to optimize noise margin and hence achieve a lower bit error rate (BER).
Typically, this offset or slice voltage is proportional to the magnitude of the input voltage. A limit amplifier is a highly non-linear device, as the purpose of a limit amplifier when used, for example, in an optical system is to produce a clipped output such that a downstream device (e.g., a CDR) can easily process the data signal. Accordingly, the gain of the limit amplifier is not constant; for a small input voltage the gain is large, while for a large input voltage the gain is small.
It is desirable to generate a slice voltage that is at a low noise level, as noise in this slice voltage is amplified in the same manner as the input voltage. Typically, slice control is implemented by adding a slice amplifier stage to a signal amplifier signal stage in the limit amplifier. Both amplifier stages are generally controlled using independent fixed bias currents. Noise present in the output signal of the amplifier may originate in various sources, including circuitry that provides the input voltage, for example, a photodiode and a transimpedance amplifier that convert incoming optical energy into electrical signals. Furthermore, noise can be generated by the components of the signal amplifier stage as well as the slice amplifier stage. Still further, circuitry that generates a control voltage that is used to generate the slice voltage can also lead to noise.
In order to reduce noise contribution from the slice amplifier stage, typically the transconductance (gm) of the devices in the slice amplifier stage are much smaller than the transconductance of the devices in the signal amplifier stage. Because the bias currents remain fixed, so too does this transconductance ratio remain fixed.
Furthermore, because the signal swing range of a slice voltage is limited by the linear range of the slice amplifier stage and the available voltage swing of the control voltage, the achievable slice range is compromised, resulting in a less than satisfactory slice control range. For example, it is common for a slice range to be limited to approximately 20% of the incoming signal strength. In actual terms, this slice level is often limited to 100 millivolts (mV) or less in an optical receiver.
A need thus exists for an improved manner of controlling an offset signal range such as providing an extended slice adjust range.

Signal dependent biasing scheme for an amplifier


A controller to programmably provide stored values of drive control data (e.g., a ramp value) to a display device. Using the stored values of drive control data, modulated signals, such as pulse width modulation waveforms may be formed to digitally drive display elements of a display device, as an example. In a display refresh period, a first count indicative of a modulation characteristic may be compared to a stored value that corresponds to the first count. This comparison may determine an update for a second count indicative of a display data characteristic based on the stored value. Because only unique stored values may be stored in a programmable storage device, such as a look-up-table, a relatively smaller number of table entries may be stored and programmed in one embodiment. This may substantially reduce the size of the look-up-table and significantly decrease programming time and effort.

The present invention relates generally to electro-optical displays, and more particularly to forming modulated signals that digitally drive display elements.
Typically, a display system includes a display device that receives drive control information for driving display elements, displaying desired content. More specifically, for digitally driving a display device a commonly shared drive control data may be sent to each display element as a reference signal in addition to appropriate per-pixel display data (e.g., a pixel value). For example, an array of display elements (e.g., pixels) in a display device may be driven using drive signals, such as modulated waveforms that may be formed based on the common drive control data and per-pixel display data. In doing so, each modulated waveform may be individually formed to drive a different pixel of the display device. However, there are many ways to generate these drive signals.
One approach to form drive signals in display systems involves using pulse width modulation (PWM). By generating pulse width modulated waveforms, pixels with available digital storage, such as in liquid crystal displays (LCDs) may be appropriately driven. In one pixel architecture, per-pixel circuitry may modulate the orientation of liquid crystal (LC) material of a pixel.
To generate a modulating signal, such as a PWM waveform, a refresh period (or modulation cycle) may be divided into "m" discrete steps. For these steps, a counter may keep a step count as a counter value. At each step, the per-pixel circuitry may elect to change the state of the pixel based on the step count and pixel value of the pixel. Typically, the per-pixel circuitry makes the state transition decision by mapping a counter value from an interval counter (e.g., an m-bit counter) into an n-bit space (where "n" is the number of bits in the per-pixel display data). For example, by asserting that the state of the PWM waveform for a pixel of value "p" is 0 if "p" is less-than the mapping of the current counter value of the interval counter onto the n-bit space, a programmable storage device, such as a look-up-table (LUT) may enable this n-bit space mapping.
Using the m-bit counter output onto a different set of numbers, i.e., a 2m×n LUT, a n-bit ramp value for use at each pixel may be provided to accomplish this mapping in one case. The n-bit value, however, should be monotonically increasing. Moreover, the fidelity with which a given non-linear relationship may be represented depends on the value of "m". Therefore, typically a large value is desired for "m," requiring a look-up-table (LUT) of a relatively much larger size than necessary to support a ramp-based technique. Even worse, programming such a large look-up-table (LUT) may be inefficient, especially when most of the entries in the LUT do not change. As a result, a large LUT may waste precious hardware real estate in some displays.
Thus, there is a continuing need for better ways to form modulated signals that drive display elements with available digital storage.

Forming modulated signals that digitally drive display elements


Embodiments facilitate prediction of anti-vascular endothelial growth (anti-VEGF) therapy response in DME or RVO patients. A first set of embodiments discussed herein relates to training of a machine learning classifier to determine a prediction for response to anti-VEGF therapy based on a vascular network organization via Hough transform (VaNgOGH) descriptor generated based on FA images of tissue demonstrating DME or RVO. A second set of embodiments discussed herein relates to determination of a prediction of response to anti-VEGF therapy for a DME or RVO patient (e.g., non-rebounder vs. rebounder, response vs. non-response) based on a VaNgOGH descriptor generated based on FA imagery of the patient.

Diabetic macular edema (DME) is one of the leading causes of vision loss in patients with diabetic mellitus. The major cause of DME-related vision loss is the disruption in the blood-retinal barrier, which leads to fluid accumulation within intra-retinal layers of the macula. When evaluating DME, fluorescein angiography (FA) provides information on vascular leakage and non-perfusion. The use of ultra-wide FA (UWFA) is becoming more common given its ability to provide near panretinal assessment of disease burden. A rise in vascular endothelial growth factor (VEGF) is linked to an increase in permeability in the blood-retinal barrier, thereby initiating a cascade of events which ultimately leads to a loss in visual acuity.
Anti-VEGF therapy has emerged as a first-line treatment for DME. Utilization of anti-VEGF therapy has improved clinical outcomes by improving visual acuity and reducing macular edema. While these outcomes do present promising results for the future, there still lies a void in the knowledge surrounding the impact of anti-VEGF treatment on the underlying pathology of retinal vasculature characteristics, such as blood-vessel arrangement, vascular leakage, and ischemia. In addition, discriminating image features that may be important biomarkers for treatment response have not been identified by existing approaches. Furthermore, existing approaches to UWFA interpretation rely on subjective physician interpretation, and quantitative higher-order assessment is not readily available in clinical situations.

Hough transform-based vascular network disorder features on baseline fluorescein angiography scans predict response to anti-VEGF therapy in diabetic macular edema


The present invention relates to a process for spraying a one-component composition by

1. Field of the Invention
The present invention relates to a process for spraying a one-component coating, sealing or adhesive composition using air-assisted, low pressure spray equipment having an improved spray nozzle.
2. Description of the Prior Art
One-component coating, sealing or adhesive compositions are known and include isocyanate-terminated and alkoxysilane-terminated resins or prepolymers that cure in the presence of atmospheric moisture. Also known are mixtures of isocyanate-terminated resins and blocked co-reactants that are activated in the presence of moisture, such as aldimines, ketimines and oxazolidines. Depending upon the particular application these one-component compositions are often mixed with solvents, pigments or other additives that may not be entirely free of moisture. Any moisture present in these additives can cause premature polymerization of the compositions reducing their storage stability.
It is also known in the prior art to employ processes for reducing the moisture content of the additives prior to blending them with the reactive component. Examples include the addition of moisture scavengers, which are often added in excess amount, based on the moisture present, to ensure complete removal of moisture. However, many of the moisture scavengers also have to removed or neutralized due to their volatility. Due to the steps involved and the amount of time necessary, these existing methods are costly.
While it is possible to mix the reactive components with the additives just prior to use, it is critical that the components are mixed in the right proportions. If the components are mixed in the wrong proportions, then the properties of the resulting products can be substantially affected. Special metering and mixing equipment is often needed to conduct this process on a commercial scale, which is also costly.
Accordingly, it is an object of the present invention to provide a process for mixing the binders for one-component compositions with additives without the need for expensive moisture removal steps. It is an additional object of the present invention to accurately mix the components.
This object may be achieved with the process according to the present invention which utilizes a low pressure, air-assisted spray system to accurately mix the components of the one-component spray according to the present invention. An important feature of the invention is the use of a disposable spray tip and static mixer to accurately mix the binders and additives of the one-component systems. Another important feature of the present invention is the use of an optionally power-assisted caulking gun to deliver the one-component composition to the spray tip.
Copending applications, U.S. Ser. Nos. 09/838,792 and 09/838,794, disclose the use of a disposable spray tip and static mixer in combination with a low pressure, two-component, air-assisted spray system. However, that system is intended for larger applications and does not disclose the use of a caulking gun to deliver the two-component composition. Copending applications, U.S. Ser. Nos. 09/917,309 and 09/917,298, describe the use of a caulking gun to deliver two-component compositions to a static mixer having an optionally removable spray tip. These applications do not disclose mixing the binder for a one-component composition with one or more additives. Copending application, describes the use of a caulking gun to mix the binder for a one-component composition with one or more additives, but that application does not describe inserting the static mixer into a shroud.
The present invention relates to a process for spraying a one-component composition by
a) activating the trigger mechanism of a caulking gun having a two or more rams and containing a two or more cartridges to incrementally advance a ram into operative engagement with each cartridge and dispense a first liquid binder component from a first cartridge and a second liquid additive component from a second cartridge into a static mixer having an optionally removable spray tip,
b) mixing the first component and the second component in the static mixer,
c) discharging the mixed liquid components from the static mixer through the optionally removable spray tip at the downstream end of the static mixer into an atomizing zone,
d) introducing air into the atomizing zone,
e) atomizing the mixed liquid components in the atomizing zone,
f) spraying the atomized liquid components onto a substrate and
g) during an interruption in the spraying process or after termination of the spraying process, discarding the static mixer and the optionally removable spray tip.

Process for spraying one-component compositions with air-assisted, low pressure equipment having an improved spray nozzle

Abstract: a) activating the trigger mechanism of a caulking gun having a two or more rams and containing a two or more cartridges to incrementally advance a ram into operative engagement with each cartridge and dispense a first liquid binder component from a first cartridge and a second liquid additive component from a second cartridge into a static mixer which is encased in a shroud and has an optionally removable spray tip,


A character shielding-preventive pointer instrument for automotive gauges includes a polarizer film having permeability or non-permeability characteristics selectively depending on whether power is supplied thereto. The polarizer film is attached on a lower surface of a front end portion of a pointer needle positioned just above characters of a character plate. Whether or not power is supplied to the polarizer film is controlled depending on the current position of the pointer needle by a micro computer such that the polarizer film is permeable to light when the pointer needle is located above a character of the character plate so that light emitted from the character plate passes through the pointer needle through the polarizer film to prevent the pointer needle from shielding the character.

1. Field of the Invention
The present invention relates to a character shielding-preventive pointer instrument for automotive gauges, and more particularly, to such a pointer instrument in which a polarizer film having permeability or non-permeability characteristics selectively depending on whether electric power is applied thereto or not is attached to a pointer needle.
2. Background of the Related Art
In general, an automotive vehicle includes various gauges or meters mounted on an instrument panel constituting the front surface of an instrument cluster. Pointer-type gauges are widely used for speedometers, RPM tachometers, temperature gauges, fuel gauges, etc.
In general, a pointer needle is rotatably mounted at a pointer shaft installed at the center of a character plate so as to rotate about the point shaft above the character plate having a scale and characters thereon. The pointer needle rotates by means of a step motor mounted below the character plate, and controlled by a micro computer.
For night driving, the pointer needle may receive light from an LED to emit light according to the manipulation of a combination switch. The character plate also typically receives light from the LED to cause the scale and the characters to emit light.
However, when the pointer needle continuously indicates a specific character, a front end portion of the pointer needle shields the character, which makes it difficult for a driver to read the character.
Due to this problem, there have been many restrictions in the thickness of the pointer needle or the character position of the gauge apparatus and so forth when designing a pointer.


A telephone answering system (100) and method (200) that permits a user to immediately generate a customized playback message in response to an incoming call without having to actually answer the call. The system (100) can include a ring detector (104), a command interface (114), a controller (110) and a telephone network interface (102). In response to an incoming call, the ring detector (104) alerts the called party and causes the controller (110) to activate the command interface (114). The command interface (114) is activated for a predetermined time while the call is still ringing. While activated, the called party can select or enter a playback message. The playback message can be a pre-recorded audio message stored within the device, or a voice message spoken by the called party during the activation period. After the playback message is selected by the called party, the telephone system (100) answers the incoming call and automatically plays the customized message to the calling party.

1. Field of the Invention
The present invention generally relates to telephone answering devices, and in particular, to an improved method and system for selectively presenting customized audio messages to callers without answering the call or directing the call to a phone mail system.
2. Description of the Related Art
A conventional phone answering machine automatically plays a pre-recorded audio message to a caller when a called party fails to answer. A pre-recorded message is typically generic in nature, informing the caller that the called party is unavailable and that the caller may leave a message if so desired. In some instances, the answering device gives the caller the option to transfer to another destination, such as a receptionist or secretary, who can provide more information as to the whereabouts of the called party.
On occasion, a called party may be aware of an incoming call, but unable to immediately answer. For instance, the called party could be engaged in a meeting. In such instances, it may be desirable to provide a customized recorded message to the caller without actually answering the call. A customized message could provide specific information, for example, a notice that the called party will return the incoming call within a few minutes.

Method and system for providing customized audio responses to incoming phone calls


An electromagnetic resonance coupler includes: a transmitting resonator provided on a transmission substrate and having an open loop shape having an opening, first wiring provided on the transmission substrate and connected to a first connection point on the transmitting resonator, a receiving resonator provided on a reception substrate, second wiring provided on the reception substrate and connected to a second connection point on the receiving resonator, and third wiring provided on the reception substrate and connected to a third connection point on the receiving resonator. When viewed in a direction perpendicular to a main surface of the transmission substrate, the transmission substrate and the reception substrate face each other so that the transmitting resonator and the receiving resonator are symmetric about a point and have matching contours.

Rat race circuits (for example, patent literature (PTL) 1), which convert one high frequency signal (single-ended signal) into two equal amplitude, anti-phase differential signals, are widely used as a structural element in, for example, microwave band frequency converters. Use of such a rat race circuit makes it possible to amplify each of the differential signals by amplifying the single-ended signal with one amplifier.

PANASONIC INTELLECTUAL PROPERTY MANAGEMENT CO., LTD.


A one-pack preparation of irrigating solution for ocular surgery of cataract, glaucoma or intraocular lens transplantation, which is excellent in the protection of ophthalmic tissues and endothelial cells during and after the operation and has a high in vivo stability. The preparation comprises an aqueous solution containing at least one compound selected from D-3-hydroxybutyric acid and water-soluble salts thereof, at least one compound selected from water-soluble bicarbonates, phosphoric acid and water-soluble phosphates, a water-soluble calcium salt, and a water-soluble magnesium salt.

This application is a 371 of PCT/JP98/04757 filed on Oct. 21, 1998.
1. Technical Field
The present invention relates to a preparation of irrigating solution for ocular surgery which may be used in the surgery of cataract, intraocular lens transplantation or glaucoma. More specifically, it relates to a preparation of irrigating solution which is suitable for protecting intraocular tissues, removing the substances left in the eye after the surgery by suction and preventing the surface of the corneal epithelium and the conjunctiva from drying in order to perform the surgery safely and effectively.
2. Background Art
Recently, development of ocular surgery methods for surgery of cataract, intraocular lens transplantation, glaucoma and the like has remarkably progressed. An irrigating solution which is used as a surgical adjuvant plays an important role in order to perform the above surgery safely and effectively. For example, when the periphery of the cornea is incised by a scalpel at the start of the surgery of cataract, the aqueous humor flows out from the anterior chamber immediately. Therefore, injection of an irrigating solution and a viscoelastic substance is indispensable for protecting intraocular tissues and cells and for maintaining the space of the anterior chamber. Further, when the irrigating solution is present in the eye at the time of breaking the opaque crystalline lens into pieces and extracting them, the pieces can be removed smoothly by suction. The irrigating solution is also used for preventing the surfaces of the cornea and the conjunctiva from drying during operation.
Some important points in the preparation for achieving such application purposes of the irrigating solution are as follows: (1) the osmotic pressure and pH of the preparation must be physiologically harmonized with the intraocular tissues and the corneal endothelial cell; 2) the essential compounds of aqueous humor components such as inorganic salts, energy sources and cell-activators must be added; 3) the preparation must be biologically safe; and 4) the preparation must be able to be preserved at room temperature for the long term.
One of preparation of irrigating solution for ocular surgery which are currently available in Japan""s market is a commercial product containing oxyglutathione as a cell-activator, and another commercial product having a bicarbonate ion-based buffer system has already been practically used. However, since these are a two-pack preparation which requires two types of solutions to be mixed prior to use or a preparation which contains no ingredients effective for protecting the corneal endothelial cell, they have not a few problems to be solved with regard to stability, simplicity at the time of use and efficacy as a preparation.
A preparation of irrigating solution for ocular surgery which is composed essentially of 3-hydroxybutyric acid as an energy source is disclosed in the specifications of U.S. Pat. Nos. 5,116,868 and 5,298,487. However, the preparations described in the specifications do not contain bicarbonate ions necessary to sustain the function of the corneal endothelial cell. The disclosed reasons why the preparation does not have to contain the bicarbonate ions in advance are that when the bicarbonate ions exist in the preparation, the pH of the preparation fluctuates due to a CO2 partial pressure, whereby the preparation becomes unstable, and that 3-hydroxybutyric acid generates CO2 through metabolism and the CO2 changes into the bicarbonate ions which are therefore supplied automatically. In addition, sodium acetate, which is generally said to be absent in human aqueous humor, is contained in the above preparation.
D-3-hydroxybutyric acid or its salts used as active ingredients in the present invention are known to be biological substances existing in humans and most of other mammals, biosynthesized through an oxidation process of fatty acids in the liver, and carried into the cornea as well as peripheral tissues out of the liver by blood to be utilized as an efficient energy source (refer to Lehninger, New Biochem., 2nd Ed., p625, 1993 and NATURE, No.4, 841, p597, 1962). It is also known that the substances are much more useful for corneal tissues as an energy source than glucose (refer to TRANSPLANTATION, 57, p1778-1785, 1994).
D-3-hydroxybutyric acid or its salts are oxidized in the TCA cycle of these tissues to produce ATP and are eventually converted into carbon dioxide and water (refer to NATURE, No.4841, p597, 1962).
As for the application of D-3-hydroxybutyric acid and its salts to drugs, it has been reported that they are mixed into an infusion solution for supplying nutrients to patients in the accelerated state as to biological protein catabolism or those having an invaded body (refer to Japanese Patent Application Laid-Open No. 191212/1990).
It is disclosed in GANKA RINSHO IHO, Vol.92, No.7 (1998), p902-905, that the influence of an intraocular irrigating solution containing xcex2-hydroxybutyrate on the retinas has been studied on an electroretinogram (ERG) using the retinas extracted from rabbits and that the intraocular irrigating solution sustains retinal functions which are equal to or more than the market product BSS PLUS (registered trademark) does. However, the D-form of xcex2-hydroxybutyrate is not disclosed in this report, and only the influence of xcex2-hydroxybutyrate on the retinas is disclosed.
In addition, the Proceeding 201 of the 36th Meeting of the Retina Vitreous Society of Japan held on Jul. 24-26, 1997, discloses that the influence of a newly formulated intraocular irrigating solution containing sodium D-xcex2-hydroxybutyrate on the retinas was studied on an ERG using the retinas extracted from rabbits and that the newly formulated intraocular irrigating solution could sustain the ERG of a retinal in vitro sample which is equal to or more than BSS PLUS does.
However, the detailed composition of the above irrigating solution is not disclosed in this report, and only its influence on the retinas is disclosed.
It is an object of the present invention to provide a one-pack preparation of irrigating solution for ocular surgery of cataract, glaucoma or intraocular lens transplantation, which is excellent in the protection of ophthalmic tissues and endothelial cells during and after the operation and has a high in vivo stability.
It is another object of the present invention is to provide an intraocular preparation of irrigating solution having formulation stability in addition to the above excellent properties by adding inorganic ions, energy sources, isotonic agents, buffers, bicarbonate ions and stabilizers.
Other objects and advantages of the present invention will become apparent from the following description.
According to the present invention, the above objects and advantages can be attained by a one solution-pack preparation of irrigating solution for ocular surgery of cataract, glaucoma or intraocular lens transplantation, which comprises an aqueous solution containing:
(1) at least 0.1 mM but less than 500 mM of at least one compound selected from the group consisting of D-3-hydroxybutyric acid and water-soluble salts thereof as a D-3-hydroxybutyrate anion;
(2) at least 0.1 mM but less than 100 mM of water-soluble bicarbonate salts as a bicarbonate ion;
(3) at least 0.1 mM but less than 50 mM of at least one compound selected from the group consisting of phosphoric acid and water-soluble phosphate salts thereof as a phosphate ion;
(4) at least 0.01 mM but less than 50 mM of water-soluble calcium salts as a calcium ion; and
(5) at least 0.01 mM but less than 50 mM of water-soluble magnesium salts as a magnesium ion.

Perfusate preparation for ophthalmic operation


An arrangement (100) and method for a high precision and low distortion digital delay line with infinite delay. The digital delay line has an oscillating ring (110) with an odd number of inverting elements that triggers a counter (120). A comparator (130) compares the counter and the MSB of a given delay word. A line of inverters (150–159), double the odd number in the ring oscillator, is connected to a MUX (160) controlled by the LSB of the delay word.

In the field of this invention it is known that typically in a digital delay line the signal to be delayed is propagated through a line of inverters and a multiplexer (MUX) to select the location (inverter) at which the signal will be output.
However, this approach has the disadvantage(s) that traditionally a digital delay line with high resolution and long delay occupies a big silicon area of an integrated circuit. In order to build a long digital delay line with small silicon area, the resolution must be decreased. In addition, the signal to be delayed is distorted as more as the delay line becomes longer.
A need therefore exists for an arrangement and method for a digital delay line with infinite delay wherein the abovementioned disadvantage(s) may be alleviated.

Arrangement and method for digital delay line

Abstract: This provides the advantages of: high resolution due to use of a small, basic component, self-delay ring oscillator; small silicon area due to use of a special decoding scheme use the rings number to produce large delays; and easy implementation as a digital block in an integrated circuit using a standard cells library to build the ring and the decoder.


A transition metal carbide-Group VIII metal powder comprising discrete particles of a transition metal carbide and Group VIII metal wherein: substantially all of the particles have a size of at most 0.4 micrometer; the transition metal carbide is selected from carbides of the group consisting of tungsten, titanium, tantalum, molybdenum, zirconium, hafnium, vanadium, niobium, chromium, mixtures and solid solutions thereof; and the Group VIII metal is selected from the group consisting of iron, cobalt, nickel, mixtures and solid solutions thereof. Said powders are produced by heating an admixture comprising a finishing source of carbon (e.g., acetylene black), a source of a group VIII metal (e.g., Co.sub.3 O.sub.4), and a particulate precursor to a temperature of about 1173 K to about 1773 K for a time sufficient to form a transition metal carbide-Group VIII metal powder, wherein at least about 25% by weight of the carbide precursor is carburized in forming the transition metal carbide of the transition metal carbide-Group VIII metal powder. The particulate precursor generally contains less than 2.5% oxygen by weight and contains compounds which undergo carburization such as a transition metal (e.g., W), lower valence transition metal carbide (W.sub.2 C) to form the transition metal carbide (e.g., WC)-Group VIII metal powder.

Metallic carbide powders are used to make densified or sintered products. For example, it is well-known that monotungsten carbide (WC) is useful in the manufacture of commercially worthwhile items such as cutting tools, tool dies, blast nozzles and drill bits. In producing said WC items, it is common for a tungsten carbide powder to be combined with a metal such as cobalt and, subsequently, densified into a WC/Co cemented carbide by heating when making said tools.
As the particle size of the metallic carbide-metal powder decreases, the densified products generally exhibit improved properties such as increased strength and improved wear resistance. However, due to their high surface energy, if the particles are too small they may cause exaggerated grain growth to occur when forming a cemented carbide part. Exaggerated grain growth adversely affects properties such as strength. Grain growth can be controlled to some extent by addition of grain growth inhibitors such as VC, Cr.sub.3 C.sub.2, or TaC or by starting with a WC having a narrow size distribution.
Densified metallic carbide-metal products having improved properties (e.g., increased strength) are also generally achieved by homogeneously blending the metallic carbide and metal powders. Homogeneously blending the powders generally results in a more uniform microstructure resulting, in less defects such as large grains due to exaggerated grain growth and pores in the densified body.
Monotungsten carbide is typically formed by the carburization of metal tungsten. Metal tungsten carburization processes typically make WC powders having a particle size of about 0.8 micrometer and larger because of the difficulty in producing W metal much smaller than this size. Tungsten metal typically cannot be made much smaller than this size due to synthesis limitations and the tungsten powder being pyrophoric.
Methods which have attempted to make more homogeneously blended and smaller WC-cobalt powder (i.e., WC-cobalt mixed powder) include the following. The article, "Production of WC Powder from WO.sub.3 with Added Co.sub.3 O.sub.4," by Ushijima, et al., published in the Japan Metal Society Journal, 42, No. 9, pages 871-875 (1978), describes a method to produce WC-cobalt powder by carbothermal reduction of WO.sub.3 and Co.sub.3 O.sub.4 in the presence of carbon in the form of carbon black and hydrogen. The WC-cobalt mixed powder formed by this method had a particle size of 0.6 micrometer or greater.
Pollizotti et al., (U.S. Pat. No. 4,851,041) disclose a WC--Co powder produced by reduction decomposition of a suitable mixed metal coordination compound such as tris(ethylenediaminecobalt) tungstate resulting in an atomically mixed high surface area reactive intermediate product, followed by carburization reduction of the intermediate product in flowing CO/CO.sub.2 gas. The WC--Co mixed powder is described as being composed of multiphase composite particles which are larger aggregates containing WC grains (particles) having a size of 10 to 20 nm in a matrix of beta-Co/W/C solid solution.
S. Takatsu in Powder Metallurgy International, Vol. 10, No. 1, pages 13-15, 1978, discloses a method to produce WC powder by reducing a mixed oxide of W and Co by reducing and carburizing with gaseous reagents using a rotary kiln. The mixed oxide is first reduced to metal in a hydrogen atmosphere, then carburized in a methane hydrogen gas mixture, and finally further treated in hydrogen or a methane-hydrogen gas mixture to remove excess carbon and convert W.sub.3 Co.sub.3 C to WC and Co. A homogeneous WC--Co mixed powder is disclosed having a mean particle size of greater than or equal to about 0.4 micrometer.
It is desirable to provide a metallic carbide-metal powder and process to manufacture said powder wherein the powder has a particle size less than about 0.4 micrometer.

Metallic-carbide-group VIII metal powder and preparation methods thereof


A phenothiazinium compound of Formula (I):

It is known that certain organic compounds ("photosensitisers") can induce cell death by absorption of light in the presence of oxygen. The cytotoxic effect involves Type I and/or Type II photooxidation. Such photosensitisers find use in the treatment of cancer and other diseases or infections with light (photodynamic therapy) and in the sterilisation (including disinfection) of surfaces and fluids by the light-induced destruction of microbes. In this context, the term sterilisation is taken to mean the reduction or elimination of microbes in a particular situation. For prevention of wound infections sterilisation means a significant reduction in bacterial load on, in or around a wound site which helps to promote efficient wound healing or which minimises the chance that wound infection will occur.
It is also known that certain coloured phenothiazinium compounds, (e.g. methylene blue) can take part in Type I and Type II photooxidation processes, but compounds of this type thus far have proved unsuitable or of low efficacy as sensitisers for photodynamic therapy, or have shown low photochemical antimicrobial activity. For application in PDT, a good sensitiser must have at least some and preferably all of the following properties. Most importantly, it should cause the destruction of target cells (for example tumour cells or bacterial cells) efficiently on exposure to light (preferably wavelengths ca. 600-800 nm). The PDT treatment using the photosensitiser should show a high degree of selectivity between target and normal tissues. The sensitiser should have relatively little dark toxicity and it should cause little or no skin photosensitivity in the patient. The sensitiser should have short drug to light intervals for patient and hospital convenience and to minimise treatment costs.
For applications in photosterilisation, a good sensitiser must show a strong phototoxic effect in a wide range of microrganisms, ideally using ambient light, and should not photobleach readily.
In oncology, several different types of photosensitiser have been used to treat both solid tumours and thin tumours of hollow organs such as the oesophagus and bladder. However, the use of these photosensitisers has been restricted partly because of lack of selectivity between tumour and healthy tissue and partly because of the prolonged skin photosensitivity which can be caused. There is a need for new photosensitisers which cause little or no skin photosensitivity and which selectively destroy tumour cells.
Although PDT has previously been used in the treatment of tumours, it has not yet been used clinically against infections caused by bacteria and other microorganisms. The use of antibiotics to treat bacterial infections is becoming challenging due to the increasing resistance of many bacterial species to commonly used antibiotics, such as tetracyclines and beta-lactams. Hospital-acquired antibiotic resistant infections such as MRSA are especially problematic. Photodynamic antibacterial treatment is a promising alternative to antibiotics for local treatment.
When developing antibacterial agents a major problem which must be overcome is the uptake of the drug into the bacterial cell. Gram negative and Gram positive bacteria differ in the composition of their outer surface and respond differently to antimicrobial agents, especially in terms of uptake. Due to the high negatively charged surface of Gram negative bacteria they are relatively impermeable to neutral or anionic drugs, including most commonly used photosensitisers. Development of antimicrobial photosensitisers which are effective against Gram negative bacteria, as well as Gram positive bacteria would be highly beneficial to replace commonly used antibiotics and drugs which are becoming increasingly ineffective due to resistance. A number of different types of photosensitiser have been investigated in bacteria. These include phenothiazinium compounds, phthalocyanines, chlorins and naturally occurring photosensitisers. For uptake into Gram negative bacteria, it is accepted that the cationic derivatives are the most effective.
Phenothiazinium compounds are blue dyes with maximum absorption at wavelengths between 600-700 nm. They have been studied for their non-photodynamic antibacterial properties but few apart from methylene blue and toluidine blue have been investigated photodynamically.
Wainwright et al (1998) investigated the effect of a series of phenothiazinium methylene blue derivatives in tumour cell lines and bacteria. New methylene blue (NMB) and di methyl methylene blue (DMMB) were effective at inactivating MRSA and were shown to be more effective photosensitisers than methylene blue when acting on pigmented melanoma cell lines. Wagner et al (1998) studied these dyes and in addition a hydrophobic derivative for the inactivation of enveloped viruses.
The precise mode of antibacterial action of methylene blue is unknown, but one hypothesis is that because of its stereochemistry it can intercalate into DNA, and that photodynamic action causes DNA damage. Methylene blue itself has been shown to be ineffective as an anti-tumour agent. In addition, methylene blue is known to be susceptible to photobleaching, which could be a serious disadvantage in some applications. Because of the recognised limitations of methylene blue, both anti-tumour PDT and antimicrobial PDT would benefit from development of new phenothiazinium-based photosensitisers.

Biologically active methylene blue derivatives

Abstract: wherein:    A and B each independently is

Abstract: in which R′ and R″ each independently is a linear, branched or cyclic hydrocarbon group, or R′ and R″ together with the N atom to which they are attached form an optionally substituted 5-, 6- or 7-membered ring;    and where XP− is a counteranion and P is 1, 2 or 3;    except for the compounds in which A and B are both either —N(CH3)2 or    —N(CH2CH3)2 for use in a treatment that requires removal, deactivation or killing of unwanted tissues or cells.