A multiple port unit includes plural peripheral communications ports and two network ports for connect the peripheral devices with at least one remote controlling computer. Multiple port unit further includes a controller which interrogates network links coupled to the network ports and alternately switching network links. The controller also interrogates computers coupled to the network links and ascertains that a computer controlling devices coupled to the communication ports is working properly.

Protective relays are commonly used to protect electrical power distribution systems. A simple protective relay can be an electro-mechanical contact relay having an energizing circuit coupled to the load on an electric power distribution line. When the load on a portion of the system exceeds certain parameters, i.e., a fault is present, the relay is energized to operate a circuit breaker or the like coupled to the power distribution line to thereby isolate a portion of the electrical distribution system having the fault. The contacts of the relay can perform various functions such as tripping a circuit breaker, generating an alarm or providing a signal to another protective relay. For the most part, such simple relays only provide the contact operation as an output. They do not provide any other indication of the conditions which produced activity in the output contacts.
For instance, the principal of operation of a distance measuring relay is that the distance of a fault can be determined by a comparison of the complex impedance of the line derived from the current and voltage at the relay to a reach characteristic. If this comparison indicates that there is a fault within the protection zone of the relay, a trip contact is actuated. Accordingly, "intelligent relays" have been developed having microprocessors capable of evaluating complex impedance or other variables to protect the electrical distribution system by isolating faults and to transmit diagnostic data and the like to computers or other devices for evaluation and display purposes. Typically, substations in an electric power distribution system have many protective relays. The intelligent relays can be programmed to perform various protection functions. For instance, digital distance relays and overcurrent relays are in use. These relays are capable of providing a great deal of information. For instance, data indicating the location of the fault, and the current and voltage at the fault are available from intelligent distance relays. Similarly, current information is available from an intelligent overcurrent relay. This information is often transmitted to a remote computer for control and report generation. Conventionally, this is accomplished over an RS-232 channel or other serial communications channel for each relay. In addition to relays, other intelligent electronic devices, i.e. control devices having microprocessors capable of executing commands and/or collecting data, have been developed.
Accordingly, multiple serial port units are utilized to couple multitudes of intelligent electronic devices to remote a computer. Such units include multiple serial ports, 8 for example, and a single Ethernet port for coupling the serial ports to a network communications link. The Ethernet port is coupled to a computer using standard cables and protocols, e.g. a twisted pair. The serial ports are each connected to an intelligent electronic device. The multiple serial port unit uses known hardware and software to map the serial ports over the Ethernet connection to appear as local serial ports to the computer. Accordingly plural intelligent protective relays can be coupled to a computer over a great distance by an Ethernet connection.
However, intelligent electronic devices and associated computer systems are applied under hazardous conditions. Particularly, electrical distribution systems are inherently in environments that include temperature changes, high EMF, and other environmental hazards. Accordingly, computers, network connections, and other components often fail intermittently or permanently in electrical distribution systems. If a computer or network connection over which an intelligent protective relay is communicating fails, the operator may not have control of devices such as circuit breakers, disconnect switches, and the like. Also, the operator might not know the status of their devices and may lose centralized control of an entire substation. Accordingly, the protective relay may not function properly and equipment damage or injury of personnel may result. Accordingly, there is a need for failure tolerance in a control system for protective relays in an electric power distribution system.
It is known to provide network failure tolerance using redundant computers i.e., servers, and to switch over to a backup computer when a primary computer fails. Also, it is known to send separate packets of data over different paths in an Ethernet connection. However, these systems and methods are not truly redundant because they rely on the computers for fault detection and a single Ethernet connection for communications.

Computer multiple communications port unit


The present invention provides a lamp adapter, including a first adapter, a second adapter and a short-circuit. These two adapters are separately coupled between two incoming ends of T5 lamp and T8 socket. The first adapter contains a circuit board, and the second adapter is used for the coupling of the other pin pitch of the lamp. The short-circuit enables functional short-circuiting of the starter of T8 socket, so that the current from the power supply is fed from both ends of T5 lamp to highlight T5 lamp through the circuit of first and second adapters. The shunt circuit is arranged between the connecting circuit (of the input inductor and T5 lamp connector terminal) and cathode loop. The T5 lamp can be mounted onto the T8 socket without changing any structure and components, thus realizing energy-saving and environmental protection with higher intensity of illumination.

1. Field of the Invention
The present invention relates generally to an adapter exclusively used for the lamp, and more particularly to an innovative adapter, which allows installation of a T5 lamp onto a T8 socket.
2. Description of Related Art Including Information Disclosed Under 37 CFR 1.97 and 37 CFR 1.98.
With ever-changing progress, the manufacturing technology and quality of lamps are improving continuously, e.g. the up-to-date T5 lamps' illumination efficiency is 30% higher than traditional T8 lamps, with the color rendition almost similar to the sunlight. So, such lamps are an ideal option for environmental protection and widely applied in many countries. Yet, some actual problems will be encountered due to different dimensions of T5 and T8 lamps, e.g. the standard T5/28 W lamp is approx. 60 mm shorter than T8/40 W lamp. Also, there are varying connecting pins at the receiving terminals, i.e. T5 lamps cannot be mounted onto T8 lamp sockets and have to be replaced along with the well-functioned sockets, leading to a serious waste of resources, especially in the shipping centers where thousands of lamps are often removed together with the operable sockets.
Thus, to overcome the aforementioned problems of the prior art, it would be an advancement in the art to provide an improved structure that can significantly improve efficacy.
Therefore, the inventor has provided the present invention of practicability after deliberate design and evaluation based on years of experience in the production, development and design of related products.


An ATM cell multiplexing apparatus includes a plurality of first cell multiplexing units and a second cell multiplexing unit. The first cell multiplexing units divide a plurality of input cell streams into a plurality of groups, thereby multiplexing the input cell streams in units of groups. The second cell multiplexing unit further multiplexes multiplexed cell streams output from the first cell multiplexing units and outputs one multiplexed cell stream.

The present invention relates to an ATM (Asynchronous Transfer Mode) cell multiplexing apparatus and, more particularly, to an ATM cell multiplexing apparatus which multiplexes a plurality of cell streams for transferring cells each having a predetermined length in an ATM communication system.
Such an ATM cell multiplexing apparatus is disclosed in, e.g., Japanese Patent Laid-Open No. 4-40718. The cell multiplexing method of this apparatus is as follows. As shown in FIG. 11, data in input signals 11-1, 11-2, . . . , 11-n each having a cell stream are written in FIFO (First-In First-Out) memories 12-1, 12-2, . . . , 12-n serving as cell generators, respectively, in units of bytes. The data are accumulated in the FIFO memories 12-1, 12-2, . . . , 12-n to constitute cells, respectively. When read access in units of cells is enabled, cell send request signals 13-1, 13-2, . . . , 13-n are output from the FIFO memories 12-1, 12-2, . . . , 12-n to a cell send arbiter 15.
The cell send arbiter 15 processes the cell send request (RDY) signals 13-1, 13-2, . . . , 13-n and issues a cell send permission signal to one FIFO memory (12-n). Accumulated cell information is read out from the FIFO memory applied with the right therefor.
With this operation, cell data from the FIFO memories 12-1, 12-2, . . . , 12-n are sent as cell send permission (OE) signals 16A to 16D. These signals are byte-multiplexed by a byte multiplexing parallel/serial converter 17 so that a serial signal 18 is sent. A timing signal generator 19 generates a transfer clock 20 and cell send start timing signals A to D.
The cell send arbiter 15 will be described below with reference to FIGS. 12 and 13. FIG. 12 shows an example of a circuit 60 constituting the cell send arbiter shown in FIG. 11. FIG. 13 shows an example of a selector shown in FIG. 12. Assume that a memory 74 of a selector 60-3 (n=3) is at high level, and an ENo signal 62-3 is at high level.
In this state, when the RDY signals 13-1, 13-2, . . . , 13-n are not input to all selectors 60-1, 60-2, . . . , 60-n, AND circuits 71 and OR circuits 72 of all the selectors except for the selector 60-3 output signals at high level, and data send right output (ENo) signals are also at high level. This state will be referred to as a cell send right transfer state.
At this time, when the RDY signal 13-8 at high level is input to one of the selectors including the selector 60-3 in the cell send right transfer state, e.g., the selector 60-8 (n=8), the AND circuit 71 and OR circuit 72 of the selector 60-8 output signals at low level, and an ENo signal 62-8 goes low. This state will be referred to as a cell send right acquisition state.
All the selectors on the downstream side of the selector 60-8 in the cell send right acquisition state are set in a waiting state. Assume that, when the selector 60-8 is in the cell send right acquisition state, one of the selectors in the cell send right transfer state between the selector 60-3 and the selector 60-8 in the cell send right issue state, e.g., the selector 60-5 (n=5) receives the RDY signal 13-5 at high level. At this time, the selector 60-5 is immediately set in the cell send right acquisition state, and all the selectors on the downstream side of the selector 60-5 are set in the waiting state.
Therefore, the selector 60-8 loses the cell send right. More specifically, selectors closer to the selector 60-3 in the cell send right issue state are applied with a higher priority.
The first problem is that, in the prior art, as shown in FIG. 11, as the number of input ports 11-n (n is an integer) increases, the number of circuits 60 in the cell send arbiter 15 for cell send arbitration increases. The reason for this is that since read control for the FIFO memories 12-n to each input port 11-n is individually performed by independent circuits, another identical control circuit is necessary for a new input port.
The second problem is as follows. The above-described cell send arbiter 15 has a daisy chain configuration (in which circuit networks are connected in series with each other to form a chain-like configuration), as shown in FIG. 12. For this reason, a data send right is always imparted to only upper input ports (ports whose n is small). If cells frequently arrive at the upper input ports, and simultaneously, at lower input ports, the FIFO memories overflow with the cells unless the capacities of the FIFO memories of these input ports are largely increased. This is because the cell send arbiter has a series-connected chain-like configuration.


An exhaust system for an internal combustion engine includes an exhaust gas-carrying component (16) with an outer wall (14), a heat conductor element (12) with a jacket (40) and with a heat conductor device (50) enclosed by the jacket (40). A pass-through device (22) provides a gastight passing of the heat conductor element (12) through the outer wall (14) of the exhaust gas-carrying component (16). The pass-through device (22) includes a pass-through opening (26) in the outer wall (14), which pass-through opening (26) is traversed by the heat conductor element (12), and a connection element (24), which is connected in a gastight manner to the heat conductor element (12), on the one hand, and to the outer wall (14), on the other hand.

To reduce the nitrogen oxide content in the exhaust gases emitted by an internal combustion engine into the environment, it is known that a reactant, for example, a urea/water solution, is injected into the exhaust gas stream and a catalytic reaction reducing the nitrogen oxide content is carried out. In order to achieve good mixing of the liquid reactant, which is generally injected as a spray mist, with the exhaust gas, a mixer, which is, for example, plate-like and is configured with wings and which generates a swirling of the exhaust gas stream, on the one hand, and provides a surface heated by the exhaust gas stream, on the other hand, on which surface the reactant impinging thereon can be evaporated, is generally arranged between an injector injecting the reactant and the SCR catalytic converter device.

Exhaust system for an internal combustion engine and process for manufacturing an exhaust system


An information processing method includes: in cases where at least one application program icon is displayed in a first display area, and an interface of a first application program is displayed in a second display area, receiving an input by a user for an icon of a second application program among the at least one application program icon; and in response to the input, performing a target operation in the second display area based on a display feature of the first application program. The at least one application program icon includes the icon of the second application program. The target operation is associated with the second application program.

With the development of a terminal device, the terminal device has increasingly more functions, greatly facilitating people's life. As people's pace of life accelerates, a convenient operation manner is an important indicator of improving user approval for the terminal device.
When a user performs some conventional operations by using an application program, for example, upgrading the application program or setting a permission of the application program, multiple operations generally need to be performed in an interface of the application program to search for a required function. Setting the permission of the application program is used as an example. When permissions of multiple application programs need to be separately set, multiple operations need to be performed on each application program one by one to enter a permission setting interface of the application program. This operation manner is tedious.

Information processing method and terminal device


A gas surface range having a downdraft ventilation system with automatic shut off during ignition. A relay is activated by current flowing to the spark coil of the electrical igniter, and has contacts connected in series with the blower motor of the downdraft system. Thus, the downdraft system is disabled during attempted ignition, and is automatically enabled at the completion of ignition.

The invention generally relates to gas cooking ranges, and more particularly relates to gas surface ranges that have electrical igniters and a down draft ventilation system.
As is well known, gas surface ranges have been built with down draft ventilation systems. One such example is described in U.S. Pat No. 4,413,610 which issued Nov. 8, 1983. In particular, the range described therein had a cooktop surface with two compartments each of which received a modular plug-in cartridge. One type of cartridge had two surface burners, and the other type included tubular burners in a broiler or grill unit. Each burner of the surface burner cartridge had side jump ports which were adjacent to respective flash tubes that extended horizontally towards a common igniter. When the control knob for either of the two surface burners was turned to the light position, the conductor of the igniter was energized by a high voltage such as 15,000 to 20,000 volts. As a result, an electrical arc jumped from the conductor to a target which was grounded to the frame. Gas from the burner ignition ports which had filled the flash tube was ignited and burned back to the jump ports that carried the flame upwards to light the burner.
The surface range further had a down draft ventilation or exhaust system located in a central region of the cooktop surface between the two compartments that received the plug-in cartridges. The down draft exhaust system included a blower connected to and communicating with a duct having an inlet or mouth defined by an aperture in the cooktop surface. In operation, the blower drew air across the cooktop surface past the cartridges and down into the duct through the aperture. In such manner, cooking effluents such as smoke were drawn from the cooking area. The blower was actuated either by manually turning a control knob, or automatically in response to a grill cartridge being operated.
The American Gas Association requires that surface gas ranges with down draft ventilation systems pass a specified ignition test. In particular, ignition must be attained within four seconds under certain operating conditions. The first condition is that the down draft be set at high speed. The second condition is that the gas pressure be reduced to 3.5 inches water column. The third condition is that a pot be placed on each of the surface burners, presumably thereby increasing the velocity of the air flow in the area of the igniter. Under the AGA test conditions described above, ignition may fail to occur within four seconds if operated with a down draft blower of relatively large capacity such as, for example 400 cubic feet per minute. More specifically, the relatively strong draft at the burner and through the igniter and flash tube region may prevent the proper gas/air mixture for ignition.

Gas range having down draft with automatic shutoff during ignition


A method for more rapidly forming a stochastic model of Gaussian or Gaussian-related type, representative of a porous heterogeneous medium such as an underground reservoir, constrained by data characteristic of the displacement of fluids and punctual observations, these observations being uncertain and characterized by a probability law. The method transforms static information, given in form of probability laws, into Gaussian punctual pseudo-data which has the advantage of being compatible with a gradual deformation method. An objective function J measuring the difference between the dynamic data (production data for example) and the corresponding responses simulated for the reservoir model considered may be minimized.

1. Field of the Invention
The present invention relates to a method for forming more rapidly a stochastic numerical model of Gaussian or Gaussian-related type, representative of the spatial distribution of a physical quantity (such as the permeability for example) in a porous heterogeneous medium (such as a hydrocarbon reservoir for example) calibrated in relation to data referred to as uncertain static and dynamic data.
2. Description of the Prior Art
Optimization in a stochastic context determines realizations of a stochastic model which meet a set of data observed in the field, referred to as static or dynamic data depending on the nature thereof. Static data correspond to observations on the studied physical quantity proper. When it is certain, the static datum is an exact value. In the opposite case, it is defined by a probability law. Dynamic data are characteristic of the displacement of fluids in the medium: they are, for example, production data (pressures obtained from well tests, flow rates, etc.).
In reservoir engineering, the realizations to be identified correspond to representations, in the reservoir field, of the distribution of carrying properties such as the permeability, the porosity or the facies distribution, each facies corresponding to a family of carrying properties. These realizations form numerical reservoir models. The available static data are, for example, punctual permeability, porosity or facies observations, and a spatial variability model determined according to punctual measurements. The punctual data can be defined by probability laws rather than exact values. For example, at a given point, a porosity value can be characterized by a normal probability law of mean 0.20 and variance 0.03. The dynamic data are directly related to the fluid flows in an underground reservoir, that is pressures, breakthrough times, flow rates, etc. The latter are often non-linearly related to the physical properties to be modeled. A randomly drawn realization is generally not in accordance with the whole of the data collected.
Static Data Integration
Coherence in relation to the static data is integrated in the model from kriging techniques
Journel, A. G., and Huijbregts, C. J., "Mining Geostatistics", Academic Press, San Diego, Calif., 1978.
The general approach generates a non-conditional realization and in correcting it so that it meets the punctual observations and the spatial structure. Within this context, the punctual observations are assumed to be exact values (for example, at a given point, the permeability is 150 mD). Let there be a Gaussian and non-conditional realization y of the stochastic model Y. The corrected realization is obtained as follows:yc(x)=ydK(x)+[y(x)−yK(x)]
yc is the corrected and therefore conditional Gaussian realization. ydK and yK are obtained by kriging from the punctual observations and from the values of y simulated at the observation points.
When the punctual observations do not correspond to exact values, but are defined by probability laws, it is possible to use either a Bayesian approach, which is extremely time-consuming in making calculations, or a kriging technique. In the latter case, on which focus occurs herein, a preliminary stage is necessary to transform the probability law into a punctual value. This transformation cannot be any transformation: the punctual values obtained must meet the spatial structure and the probability laws from which they result. Clearly, the relation between probability laws and punctual values is not a single relation. Iterative transformation methods have been proposed for facies realizations, where the probability law is a uniform law, by:
Freulon, X., and Fouquet, C. de, "Conditioning a Gaussian Model with Inequalities", in Geostatistics Troia '92, A. Soares, ed., Kluwer Academic Publishers, Dordrecht, The Netherlands, 1993,
Le Ravalec-Dupin, M., "Conditioning Truncated Gaussian Realizations to Static Data", 8th Ann. Conf. Int. As. Math. Geol., Berlin, Germany, 15-20 Sep., 2002.
These techniques tend towards the desired probability density function, but very slowly. In practice, it is not desired to completely sample this function. A single set of punctual values meeting the spatial distribution and the probability laws is merely determined and it is used to obtain the corrected realization yc. It is this single and therefore invariable set that the optimization process constantly refers to so as to form realizations constrained simultaneously by the static and the dynamic data. This point is fundamental in the optimization process.
Dynamic Data Integration
Coherence in relation to the dynamic data is integrated in the model by means of an inverse procedure:
Tarantola, A., "Inverse Problem Theory—Methods for Data Fitting and Model Parameter Estimation", Elsevier Science Publishers, 1987.
Recently, a geostatistical parameterization technique which simplifies the inverse problem has been introduced to constrain, by gradual deformation, the stochastic realizations to data on which they depend non-linearly. It forms the object of French Patents 2,780,798 and 2,795,841 filed by the assignee, and of the following publications, notably:
Hu, L. Y., 2000, Gradual Deformation and Iterative Calibration of Gaussian-Related Stochastic Models: Math. Geology, Vol. 32, No. 1,
Le Ravalec, M. et al., 2000, The FFT Moving Average (FFT-MA) Generator: An Efficient Numerical Method for Generating and Conditioning Gaussian Simulations: Math. Geology, Vol. 32, No. 6,
Hu, L. Y., Blanc, G. And Noetinger, B. (2001): Gradual Deformation and Iterative Calibration of Sequential Stochastic Simulations. Math. Geology, Vol. 33, No. 4.
This method has been successfully applied in various cases, notably from data obtained from oil development fields, as described in the following documents:
Roggero, F. et al., 1998, Gradual Deformation of continuous Geostatistical Models for History Matching, paper SPE 49004: Proc. SPE Annual Technical Conference and Exhibition, New Orleans,
Hu, L. Y. et al., 1998, Constraining a Reservoir Facies Model to Dynamic Data Using a Gradual Deformation Method, paper B-01: Proc. 6th European Conference on Mathematics of Oil Recovery (ECMOR VI), 8-11 Sep. 1998, Peebles, Scotland.
Assuming that fobs=(f1obs, f2obs, . . . , fMobs) represents all of the dynamic data collected in the field and f=(f1, f2, . . . , fM) the corresponding responses simulated for a realization yc already constrained by the static data are as explained above. In general, the responses f=(f1, f2, . . . , fM) are obtained by solving numerically the direct problem. Thus, if y0 represents a permeability field, data f can be pressure measurements. In this case, they are simulated from a flow simulator. The goal of a stochastic optimization is to produce realizations of Y which reduce the differences between the observed data and the numerically simulated corresponding responses. These differences are measured by the following objective function:
  J  =            1      2                          ∑                  m          =          1                M                                                ω            m                                          (                                          f                m                            -                              f                m                obs                                      )                          2
Coefficients ωm are weights assigned to data fmobs. fm are functions of realization y0 discretized over a large number of grid cells. In this sense, minimization of the objective function is a problem with several variables.
Let N be the number of grid cells forming realization y0. N is often very large (104˜107). It is therefore very difficult to perform an optimization directly in relation to the components of y0. Furthermore, realization y0, even modified, must remain a realization of Y. Parameterization by gradual deformation allows these difficulties to be overcome.
The gradual deformation technique allows construction of a continuous chain of realizations by combining an initial realization y0 of Y with another realization u1, referred to as complementary, of Y, u1 being independent of y0. The combination coefficients are for example cos(t) and sin(t), and the combined realization meets the relationy(t)=y0 cos t+u1 sin t where t is the deformation parameter.
Once the chain is formed, it can be explored by varying deformation parameter t and an attempt is made to identify, from among all the realizations of this chain, the realization which minimizes the objective function after integration of the static data by kriging. This minimization is performed in relation to t. Parameterization according to the gradual deformation method allows reduction of the number of dimensions of the problem from N to 1, where N is the number of values that constitute the field to be constrained. Furthermore, the sum of the combination coefficients squared being 1, the optimized realization still is a realization of Y: it follows the same spatial variability model as all the realizations of Y.
However, if the exploration of the realizations space is restricted to a single chain, the possibilities of sufficiently reducing the objective function are greatly limited. The above procedure therefore has to be repeated, but with new realization chains. These realization chains are constructed successively by combining an initial realization, which is here the optimum realization determined at the previous iteration, with a complementary realization of Y, randomly drawn each time. Thus, at iteration l, the continuous realization chain is written as follows:yl(t)=yl−1 cos t+ul sin t.
yl−1 is the optimum realization defined at iteration l−1 and the ul are independent realizations of Y.
Minimizing the objective function in relation to t allows improvement or at least preservation of calibration of the data each time a new realization chain is explored. This iterative minimum search procedure is continued as long as data calibration is not satisfactory.
To date, the punctual values integrated by kriging in the model to account for the static data remain constant throughout the optimization process, even when they correspond to uncertain values. In the latter case, such a hypothesis can significantly slow down the optimization process and prevent minimization of the objective function.

Method for more rapidly producing the representative stochastic model of a heterogeneous underground reservoir defined by uncertain static and dynamic data


A cleaning sequence usable in semiconductor manufacturing efficiently cleans semiconductor substrates while preventing chemical oxide formation thereon. The sequence includes the sequence of: 1) treating with an HF solution; 2) treating with pure H2SO4; 3) treating with an H2O2 solution; 4) a DI water rinse; and 5) treatment with an HCl solution. The pure H2SO4 solution may include an H2SO4 concentration of about ninety-eight percent (98%) or greater. After the HCl solution treatment, the cleaned surface may be a silicon surface that is free of a chemical oxide having a thickness of 5 angstroms or greater. The invention finds particular advantage in semiconductor devices that utilize multiple gate oxide thicknesses.

In the sub-micron era of today's rapidly emerging semiconductor manufacturing industry, gate oxide thicknesses are scaled down to the range of 10-20 angstroms. It is therefore critically essential to maintain gate oxides at their intended thicknesses, since any variation in thickness will be a significant one in such thickness range.
In addition to utilizing reduced gate oxide thicknesses, many semiconductor devices are designed to include two or more gate oxide thicknesses. For example, integrated circuit driver devices typically include high voltage and low voltage regions and use at least three operating voltages. The different operating voltages are used for different device types formed on the substrate and the different operating voltages are associated with gate oxide thicknesses that differ according to the operating voltage. A challenge in semiconductor manufacturing technology is to form multiple gate oxides of various thicknesses on the same substrate, then to define and form associated devices using the various gate oxides, while preserving the integrity of the gate oxides and maintaining correct gate oxide thicknesses by preventing the formation of chemical or other gate oxides during cleaning or other operations.
Wet etching procedures are typically used to remove the gate oxide from exposed areas not covered by photoresist, so that a further gate oxide having a different thickness can be subsequently formed in the exposed areas to produce the multiple gate oxide thickness effect. In some devices, this process may be repeated so that a photoresist pattern is also formed over portions of two different gate oxide thicknesses to remove the oxide from the exposed areas and subsequently form a third gate oxide. It can be appreciated that the oxides must be completely removed from the exposed areas if the subsequently formed gate oxide is to have a desired thickness in the range discussed above.
According to conventional technology for forming multiple gate oxide thicknesses, an oxide is grown, and a photoresist pattern formed over the oxide. The oxide is etched in areas not covered by the photoresist pattern using DHF (dilute HF) or BHF (buffered HF). The photoresist is then stripped using an SPM solution then a two-step, RCA clean using NH3 and H2O2 is used to clean the etched areas prior to the formation of a second, thinner oxide in the exposed areas. Using conventional technology, however, a chemical oxide forms on the silicon surface after the etching operation and during the cleaning operations. The chemical oxide is an oxide that forms on silicon surfaces during wet cleaning and rinsing operations and is highly hydrated, having a composition that differs from stoichiometric SiO2 and may be represented by SiOx, with x<2. Such chemical oxides can undesirably grow to thicknesses of 10 angstroms and greater and this compromises the ability to form gate oxides having targeted thicknesses in the 10-20 angstrom range.
One attempt to subvert the growth of the chemical oxide is to add a final HF process but the addition of an HF-final process carries with it the shortcomings of high particle counts, watermarks formed on the substrate, and organic residue. Another approach is to replace the RCA clean with the SPM cleaning solution, an H2SO4:H2O2 mixture typically in a 1:4 ratio. The use of the SPM solution, however, degrades gate oxide integrity and potentially damages the silicon surface.
As such, there is a need to provide a cleaning operation that addresses the above shortcomings and provides an efficient and fast cleaning method that strips photoresist and cleans an etched surface without the undesirable formation of a thick chemical oxide. The present invention addresses these and other needs.

Surface preparation for gate oxide formation that avoids chemical oxide formation

Taiwan Semiconductor Manufacturing Co., Ltd.


A system and method for collecting and transmitting medical and health-related data over a network are disclosed. A measuring device measures a user's physiological attribute and produces a first signal related thereto, which an integration system coupled to the measuring device receives and converts into a second signal for transmitting over the Internet. In accordance with one aspect of a preferred embodiment, the integration system is adapted to read the first signal as it is sent from the measuring device to its display. A communications system transmits the second signal over the Internet to a remote system using any of a variety of techniques known in the art. The remote system extracts the measured physiological attribute and other associated data from the second signal and populates a database. Preferably, a web-based portal provides access to the data for one or more users.

The invention relates to systems for collecting and transmitting medical and health-related data over a network.
The healthcare industry is the largest sector of this nation's economy, comprising over one trillion dollars, or roughly 13% of the gross domestic product (GDP). Because of increasing healthcare costs, it is desirable to reduce overhead, free hospitals beds, and increase compliance with treatment. Remote medical data monitoring devices are directed precisely at those goals.
Accordingly, advances in healthcare and medical devices are increasingly required to meets the needs of an aging population. For example, medical industry experts predict that the demand for medical data monitoring systems will drastically increase over the next decade. Existing monitoring systems, however, fall short of satisfying customers' needs in several ways.
Some remote monitoring systems have been designed to allow patients to transmit their medical data from their homes. An example of one such monitoring system provides a measuring device, such as a blood sugar monitor, which a patient uses to measure a physiological attribute. The patient then enters the measurements taken by the device into the monitoring system, which transmits the data over phone lines or the Internet. Obvious drawbacks of this system are reliability of data and ease of use. Due to human error, users will sometimes enter incorrect data. Because it is not connected to the measuring device, the monitoring system is incapable of detecting or correcting the error, and the database is therefore corrupted. Further, it is inconvenient, and perhaps difficult for some users, to manually enter data. Other existing devices are inadequate because they are not easily expanded, cannot work with multiple users or devices, or are encumbered by physical wire connections.

System and method for collecting and transmitting medical data


A logging last resource (LLR) system can provide a transaction log and transaction data to a LLR resource after a number of two-phase-commit resources have been prepared. The LLR resource manager can operate on the transaction log and transaction data in an atomic fashion so that the local commit can be done. The local commit can be done by the LLR manager in an atomic manner.

In many cases, transaction processing requires the use of multiple resources. Typically, each of the resources can maintain Atomic, Consistent, Isolated, and Durable (ACID) properties. A transaction manager is often used to maintain the ACID properties over multiple resources. For example, consider a single transaction involving the changing of an account balance in a database and sending of a wire transfer. It is crucial that both portions of the transaction either both occur or both do not occur. Otherwise, either the bank balance is debited without a wire transfer or the funds are transferred without debiting the bank account. Such a failure of the transaction is called a heuristic failure. If neither portions of the transaction occur, the transaction can rolled back and tried again.


A shift register includes a sampling circuit to sample an input signal in response to a start pulse and two clock signals having different duty ratios from each other, a holding circuit to hold the input signal in response to an output signal of the sampling circuit and the two clock signals, an inverter to invert the output signal of the sampling circuit or the holding circuit, and a NAND gate to receive the output signal of the sampling circuit or the holding circuit and the output signal of the inverter and perform a logical operation on the received output signals to output an output signal. The first clock signal has a duty ratio smaller than the second clock signal. The sampling circuit and the holding circuit have a three-stack structure in which three transistors are coupled with one another in series.

1. Field of the Invention
The present invention relates to a shift register and an organic light emitting display having the same, and more particularly, to a shift register that is capable of preventing malfunction caused by skew and slop between clock signals used in the shift register.
2. Discussion of the Background
Generally, a shift register shifts bits of information at least one position to the right or left. Such a shift register may include cascaded flip-flops in which an output of the first flip-flop is sequentially connected to an input of the immediately following flip-flop. All flip-flops simultaneously receive the same clock signal and inverted clock signal so that data shift simultaneously occurs in a stage-by-stage manner.
Shift registers are widely used in various fields. In particular, in display devices such as liquid crystal displays (LCDs), organic light emitting displays, plasma display panels (PDPs), and so forth, the shift register is typically used in a scan driving unit, which sequentially supplies a scan signal, or in an emission control driving unit, which controls light emission.
FIG. 1 is a circuit diagram of a conventional shift register, and FIG. 2 is a timing diagram for signals of the shift register of FIG. 1. The shift register has a plurality of flip-flops that are connected to each other in series, and FIG. 1 shows the case where the shift register has two flip-flops as a basic unit. Additionally, the shift register of FIG. 1 has a four-stack structure in which four transistors are stacked between the positive power supply voltage VDD and the negative power supply voltage VSS.
Referring to FIG. 1 and FIG. 2, a conventional shift register may include a first flip-flop FF1, which includes transistors MN1, MN2, MN3, MN4, MN5, MP1, MP2, MP3, MP4, and MP5, and a second flip flop FF2, which includes transistors MN6, MN7, MN8, MN9, MN10, MP6, MP7, MP8, MP9, and MP10. The two flip-flops FF1 and FF2 are connected to each other in series, and an output signal of the first flip-flop FF1, which receives a start pulse SP as an input signal, becomes an input signal of the second flip-flop FF2. Accordingly, the first flip flop FF1 delivers the input start pulse SP to the second flip-flop FF2 per one or half period of a clock signal CLK in synchronization with the clock signal CLK and an inverted clock signal CLKB.
Each flip-flop FF1 and FF2 repeatedly performs sampling and holding of the input signal in response to states of the clock signal CLK and the inverted clock signal CLKB of FIG. 2. That is, the first flip-flop FF1 detects the state of the input start pulse SP at a sampling time T1 and maintains that state at a holding time T2 in response to the input of the start pulse SP. The second flip-flop FF2 operates opposite to the first flip-flop FF1 such that it delivers the start pulse SP by sequentially sampling the state held by the first flip-flop FF1 and delivering it to the next flip-flop.
In the timing diagram of FIG. 2, which shows normal operation of the clock signal CLK and the inverted clock signal CLKB, a first output signal SR1 transitions to a low level just after the transition of the clock signal CLK and the inverted clock signal CLKB. Accordingly, a sampling region and a holding region of each flip-flop are correctly discriminated to generate a normal output signal.
However, as described below, the conventional shift register of FIG. 1 may malfunction when skew occurs between the clock signal CLK and the inverted clock signal CLKB or when slop increases.
FIG. 3 is a timing diagram showing an error of an output signal SR2 due to skew between the clock and inverted clock signals input to the shift register.
Referring to FIG. 3, the timing diagram shows skew in the clock signal CLK prior to the inverted clock signal CLKB. That is, referring to the skew interval, the inverted clock signal CLKB maintains a low level even after the clock signal CLK and the first output signal SR1 transition to a low level.
Accordingly, transistors MN1 and MN3 of the first flip-flop FF1 and transistors MN6 and MN8 of the second flip-flop FF2 of FIG. 1 are turned off, and transistors MP2 and MP4 of the first flip-flop FF1 and transistors MP7 and MP9 of the second flip-flop FF2 are turned on. In this case, as FIG. 3 shows, the second output signal SR2 transitions to a low level instead of maintaining the high level. Hence, an abnormal output signal may be output when the magnitude of the skew between the clock signal CLK and the inverted clock signal CLKB increases to more than a predetermined value.
FIG. 4 is a timing diagram showing an output signal error due to slop between the clock and inverted clock signals input to the conventional shift register. Here, the time from the moment an input signal is sampled by any flip-flop to the moment when the input signal is output is defined as Ts. Additionally, it is assumed that skew between the clock signals does not occur, and the clock signal CLK and the inverted clock signal CLKB are converted as shown in FIG. 4.
FIG. 4 shows the time Ton in which the clock signal CLK transitions from a threshold voltage Vthn of an N-type transistor through a threshold voltage Vthp of a P-type transistor while the inverted clock signal CLKB transitions from the threshold voltage Vthp through the threshold voltage Vthn.
Transistors MP2, MP4, MN1, MN3, MP7, MP9, MN6, and MN8 of FIG. 1 are turned on during the time Ton in which the slop occurs. Accordingly, when the slop of the clock signal CLK and the inverted clock signal CLKB increases and Ton exceeds Ts, output signals SR1, SR2, and SR3 of respective flip-flops FF1, FF2, and FF3, which must sequentially perform sampling and holding operations, operate as shown in FIG. 4. That is, each flip-flop FF1, FF2, and FF3 becomes a buffer in which two inverters are connected to each other in series. Accordingly, malfunction occurs in that the output signal SR1 becomes the next output signal SR2.
External noise or electromagnetic inference (EMI) may cause skew or slop in the clock signal CLK and the inverted clock signal CLKB, thereby causing an abnormal signal to be output from the shift register. This abnormal signal causes malfunction in a display device to which it is applied.

Shift register and organic light emitting display having the same


There is provided an operating apparatus for a medical apparatus, the operating apparatus including a ring-shaped magnet magnetically polarized in a circumferential direction or a radial direction and configured to rotate along with rotating operation by a user, and a sensor unit configured to detect a magnetic field and to output a signal depending on the detected magnetic field. The sensor unit outputs two-phase signals having different phases.

Examples of an operating apparatus for a medical apparatus include an operating apparatus using magnetism for manually controlling and adjusting a medical imaging apparatus. Such an operating apparatus using magnetism has already been developed. Examples of technology related to an operating apparatus using magnetism include those described in Patent Literatures 1 and 2 below.

Operating apparatus for medical apparatus


A control device of a vehicle which device makes a generated voltage of an alternator variable so that a state of charge SOC of a battery installed in the vehicle reaches a control target includes an idle stop permitting SOC setting unit for setting a battery state of charge SOC in which idle stop is permissible, and a battery SOC adjusting unit for reducing and resetting a control target of the battery state of charge SOC in a range beyond the idle stop permitting SOC when a predetermined operation condition holds.

A system for varying a generated voltage (charge voltage) of an alternator (generator) according to a running condition of a vehicle is being installed in the vehicle recently. The control system for varying the generated voltage in this way can improve fuel economy by actively charging a battery by increasing the generated voltage during a deceleration fuel cut and reducing the generated voltage to reduce an engine load such as during the acceleration of the vehicle.
In a system of JP2001-268708A, a target SOC during steady running and an idle stop permission determining SOC are changed according to a degree of battery deterioration.

Control device and control method of vehicle


A device including an imaging optical unit (9) imaging an object field (5) in an image field (10), a structured mask (7), arranged in the region of the object field (5) via reticle holder (8) displaceable in a reticle scanning direction (21), and a sensor apparatus (25), arranged in the region of the image field (10) via a substrate holder (13) displaceable in a substrate scanning direction (22). The mask (7) has at least one measurement structure (27; 33) to be imaged on the sensor apparatus (25), wherein the sensor apparatus (25) includes at least one line sensor (28) with a multiplicity of sensor elements (29), and affords the possibility of testing the imaging optical unit (9) during the displacement of the substrate holder (13) for exposing a substrate (12) arranged on the substrate holder.

The invention relates to an optical device and a method for testing an imaging optical unit. The invention furthermore relates to a projection exposure apparatus, a method for producing a microstructured or nanostructured component and a component produced according to this method.
Generic modules and/or methods have been disclosed in the prior art, for example in U.S. Pat. No. 7,298,498 B2, DE 101 09 929 A1 and US 2008/0130012 A1.


A frame and lens arrangement for eyeglasses in which the frame has two front recesses respectively disposed in communication with the lens mounting grooves thereof and two pairs of retaining projections respectively bilaterally disposed in the front recesses, and the lenses each have a protruded portion fitting the front recesses and two stop edges at two sides of the protruded portions for friction engagement with the retaining projections.

1. Field of the Invention
The present invention relates to eyeglasses and, more particularly, to a frame and lens arrangement for eyeglasses, which enables the user to replace the lenses conveniently.
2. Description of the Related Art
The lenses of regular eyeglasses are commonly of a monochromic design. During installation, the lenses are directly forced into position. When dismounting the lenses for a replacement, much force should be employed to the lenses against resisting force from the frame around each lens mounting opening. When employing force to the lenses against the frame, the lenses tend to be broken or, the frame tends to be deformed. Therefore, it is desirable to provide a frame and lens arrangement for eyeglasses, which enables the user to conveniently replace the lenses subject to different situations or weather conditions.
The present invention has been accomplished under the circumstances in view.
It is the main object of the present invention to provide a frame and lens mounting arrangement for eye glasses, which enables the user to mount/dismount the lenses conveniently with less effort.
It is another object of the present invention to provide a frame and lens mounting arrangement for eyeglasses, which enables the user to replace the lenses separately.
It is still another object of the present invention to provide a frame and lens arrangement for eyeglasses, which enables the user to replace the lenses easily and safely without deforming the frame.
To achieve these and other objects of the present invention, the frame of the eyeglasses comprises two front recesses respectively disposed in communication with the lens mounting grooves thereof and two pairs of retaining projections respectively bilaterally disposed in the front recesses, and the lenses each have a protruded portion fitting the front recesses and two stop edges at two sides of the protruded portions for friction engagement with the retaining projections. The front recesses can be made at the bottom side or the top side in the front of the frame. The protruded portion of each lens is provided corresponding to the position of the front recesses in the front of the frame.

Frame and lens arrangement for eyeglasses


A search apparatus and related method facilitate the final stage of a search for a buried person carrying a transmitter. When the searcher is in the close vicinity of the buried transmitter, the search enters a point-localization phase where the apparatus displays a representation of the current target distance from the apparatus to the buried transmitter as well as a representation of a previously-stored value for the target distance. By comparing the current distance to the previously-stored distance, the searcher can readily see whether the apparatus is getting closer to the buried transmitter or further away. Preferably, graphic symbols are displayed to represent the current distance and the previously-stored distance. The display can also provide a representation of whether the current distance is greater than or less than an immediately preceding distance that has been stored.

A method of finding such buried people, which has become standard in particular for locating avalanche victims, is to search according to the transmitter-receiver principle. That is, a wireless transmitter carried by the buried person sends out signals that are received by a searcher, or a group of searchers, by means of a wireless receiver. To achieve a high degree of compatibility between an arbitrary number of transmitters and receivers, a standardized signal characteristic is employed. In the case of avalanche searches, for example, a frequency of 457 kHz is used.
The wireless receivers have available one or more antennae with a pronounced directional characteristic, and can be used to take a bearing on the site of origin of the signals, and thus to locate the position of the buried person.
The manufacturers of such wireless transmitters and/or receivers are continually developing these devices in order to make it easier to find one or more such buried persons. This is particularly important because the rescuers who operate the wireless receivers are under extreme stress: every second spent in locating the target can crucially determine whether the person or persons involved will live or die. One study, for example, has shown that the probability that a person caught in an avalanche will survive that experience decreases rapidly only 15 minutes after the event. Hence, modern wireless receivers employ display devices (cf. the document DE 35 31 726 C2) that additionally display the momentary strength of a signal received from a particular direction. This information can be represented, for example, in the form of data explicitly stating the distance between transmitter and receiver.
In practice, it has been found that the so-called last meters are often the most difficult stage in the search for a buried person. In this phase of "point localization", the received information specifying a particular direction can often play only a very minor role, or can even be misleading because the searcher may well already be standing above the buried person. Distance data are also often erroneous in this stage, and exhibit only minimal differences.

Method and apparatus for locating a person who has been buried alive


In a method of controlling a direct-current drive, in particular a directrrent door drive, two state variables of the direct-current drive are determined and, on the basis of these state variables, a load or resistance moment applied to the direct-current drive is determined and compared with a predetermined load or resistance moment. Subsequently, it is established that an abnormal situation exists when the load or resistance moment determined exceeds the predetermined load or resistance moment.

1. Field of the Invention
The present invention refers to a method of controlling a direct-current drive, in particular a direct-current door drive.
2. Description of Related Art
The safety requirements which are to be met by the control of direct-current drives, used e.g. for opening and closing doors, garage doors, electric sliding roofs and the like, are very high. These safety requirements include the recognition of dangerous situations. If there is an obstacle in the path of movement of the element to be actuated, e.g. a garage door, switching off or reversing of the door must be initiated immediately. To avoid damage and injuries, the external forces acting on the door edge in the case of such switching off or reversing must not exceed specific limit values. Such limit values are prescribed by the legislator. In addition, it is endeavoured to keep the forces actually occurring as low as possible by special methods.
In the methods for controlling direct-current drives known from the prior art, the motor current applied to the direct-current drive is compared with an absolute limit value or with detected reference values.
In a first known method for controlling a direct-current drive, the motor current is compared with an absolute, predetermined, constant limit value. As soon as the instantaneous motor current exceeds a predetermined absolute value, the direct-current drive will be switched off. The disadvantage of this first known method is that the maximum driving power is strongly limited. A further problem entailed by this known method arises when the force required by a door depends strongly on the door position. In this case, positions exist at which the force at the door edge may exceed the admissible values without switching off of the direct-current drive being caused.
In order to avoid the problems described hereinbefore, a second method, which is known in the prior art, was developed; this method is known from DE 4214998 A1 and includes the step of comparing the motor current, which is applied to the direct-current drive, with a current determined by a learning trip in dependence upon the door position. In this method, which is based on reference measurements, the necessary motor current or the target speed is measured for various positions during an undisturbed trip of the door and stored as a reference value. Inadmissible deviations from the stored reference values will then result in switching off during subsequent trips. This known method is, however, problematic insofar as in cases in which a door is stopped between the end points of a trip (the point at which the door is closed or the point at which the door is open) and then started again, a high starting current will occur when the door is being re-started. For this high starting current at a position between the two end points, reference values do not exist. In order to avoid switching off or reversal of the door in this case, higher limit values for an admissible operation of the door must be provided in dependence upon the respective case of use when this method is employed. Another possibility of preventing the limit values from being exceeded is to disable the supervision during the starting period.
The above-mentioned problem arising when a door is being restarted after a stop at a position between the two end positions is clearly shown on the basis of a graph represented in FIG. 5. As can be seen from FIG. 5, the necessary motor current is there plotted against the position of a door. More precisely, the necessary motor current is plotted against the range between the door being opened and closed. Curve a) represents the motor current during a so-called normal trip. For this normal trip reference values were ascertained during the learning trip to which a predetermined tolerance value was added, whereby the limit value curve b) is obtained, which is shown in FIG. 5. Curve c) shows the problem which arises when the door was stopped at an arbitrary position between the two end positions and when it has to be re-started subsequently. In this case, the necessary motor current increases abruptly so that it would clearly exceed the limit value curve b). In order to avoid this problem, the limit value curve must be chosen such that, even if the door is re-started after having been stopped between the end positions, switching off of the direct-current drive by the high motor current occurring during re-starting can reliably be avoided. This, however, entails the problem that very high limit value curves b) must be chosen so that, in cases in which the door meets with an obstacle during its trip, switching off or reversing of the door will only be initiated after a comparatively long time. In one case, this may have the effect that the direct-current drive is damaged due to an excessive load applied thereon. In another, much more critical case, in which the above-mentioned obstacle is a human being, the switching off, which has been effected too late due to the higher limit values, may cause substantial injuries of the human body.

Method for controlling a direct current drive

Fraunhofer-Gesellschaft zur Foderung der Angewandten Forschung e.V.


A keyboard with a wobble prevention structure, which is substantially a substrate having at least one press key arranged thereon while enabling each press key to be driven to move in a reciprocating manner following a specific direction, and having a plurality of position limit devices disposed on the substrate and beneath the periphery of a corresponding press key. In a preferred aspect, each position device is integrally formed with the substrate, or can be formed on the substrate by stamp forming technique, that each is used to confine the corresponding press key to move following only the specific direction, such that the wobbling of the press keys is prevented.

A device such as a computer, a cell phone or a personal digital assistant (PDA) usually comes with a keyboard, and a press key structure of a computer keyboard as shown in FIG. 1 is a press key 10 with an elastic scissors-like mechanism. Compared with a traditional press key, the scissors-like press key 10 is advantageous in its long traveling path, evenly distributed acting force, and low noise, so that such press key is used extensively in thin-type keyboards, particularly the keyboards of notebook computers in recent years. The press key 10, disposed on a substrate 20 is composed of: a U-shaped first support arm 11, being pivotally coupled to a pivotal connecting shaft 13, and a second support arm 12 mounted on the first support arm 11. In addition, two position arm 111 are respectively arranged at the two sides of the first support arm 11 in a manner that each of which pieces through a position plate 21 mounted on the substrate 20 at positions corresponding to the two position arm 111. Since a vast majority of substrates 20 are made of metal, the position plate 21 can be formed by stamp forming, as those shown in FIGS. 2A and 2B. Each position plate 21 has a hole 211 for the position arm 111 to pass therethrough, so that the press key 10 can be pressed to move reciprocally along a direction F that is perpendicular to the extending of the substrate 20. When the press key 10 is not subjected to a pressing force, the first support arm 11 and the second support arm 12 can be forced to tilt upward from the substrate 20 by an elastic member (not shown in the figure) in a form of a scissor-like structure, as indicated by the dotted line in FIG. 2B. If the press key 10 is pressed, the first support arm 11 and the second support arm 12 are pressed flatly onto the substrate 20. To assure a smooth movement of the press key 10, the hole 211 and the position arm 111 are engaged loosely with a predetermined gap D. In addition, factors such as the tolerance of the size of the position plate 21, the distance between two position plates 21, and the size of the first support arm 11, and the existence of the aforementioned gap D may cause the press key 10 to shift and wobble, and thus affecting the overall stability of the press key when it is pressed, or even causing a malfunction of the press key when the pressing position is not aligned precisely.

Keyboard with wobble prevention structure


This disclosure relates to methods, non-transitory computer readable media, and systems that generate and visualize bias scores within segment-generation-user interfaces prior to executing proposed actions with regard to target segments. For example, the disclosed systems can generate a bias score indicating a measure of bias for a characteristic within a segment of users selected for a proposed action and visualize the bias score and corresponding characteristic in a segment-generation-user interface. In some implementations, the disclosed systems can further integrate detecting and visualizing bias as a bias score with selectable options for a segmentation-bias system to generate and modify segments of users to reduce detected bias.

Software developers and engineers have devised existing segmentation systems that analyze and select groups of client devices and/or users from digital databases to form target segments. For example, some segmentation systems generate target segments for distributing digital content across client devices via computer networks. To facilitate forming such target segments, some existing segmentation systems include graphical user interfaces (and underlying classification models) with options to select characteristics and build target segments on the fly. Such combinations can be complex, form multidimensional datasets, and include multifaceted characteristics or events. But existing segmentation systems have computing limitations that isolate functions of segmentation into separate graphical user interfaces and exacerbate selection biases with options for segment characteristics.
For example, some existing segmentation systems include selectable options to create rule-based segments. Such segmentation systems can quickly generate a segment from multidimensional datasets based on selections by an analyst. But the generated segments can include inherent biases, such as prejudices in favor of particular digital distribution channels or prejudices against a particular gender. As existing segmentation systems provide options for increasingly complex combinations of characteristics or events, such systems can compound and exacerbate selection biases in multidimensional user datasets.
When existing segmentation systems employ classification models to suggest target segments, the systems may still yet rely on datasets reflecting historical biases entrenched within the data. While such systems can identify segments with conventional classification models, the resulting segments often reflect past patterns of bias within the dataset itself. In short, even sophisticated segmentation systems often cannot avoid datasets with embedded historical biases.
In addition to exacerbating biased selections, in some cases, existing segmentation systems use isolated user interfaces siloed off from (and sometimes incompatible with) other software applications. Such conventional user interfaces often require analysts to utilize one or both of multiple user interfaces and different software applications to evaluate the distribution of characteristics within a target segment. Accordingly, conventional systems often require significant time and user interactions to evaluate characteristics within a target segment. To further complicate analysis of a target segment, in some cases, existing segmentation systems generate segments in formats incompatible with distribution-analysis applications. Such incompatibility can further increase the time and user interactions needed to detect and analyze distributions of various characteristics.

Generating and visualizing bias scores representing bias in digital segments within segment-generation-user interfaces


A vehicle tire deflation system includes a number of spike carrying members operably interconnected to an equal number of base members to form an accordion style vehicle tire deflation system. The vehicle tire deflation system includes an arrangement for ensuring the that the vehicle tire deflation system may be effectively utilized whether deployed right side up or upside down and a mechanism for ensuring that the vehicle tire deflation system remains in its extended configuration upon deployment in use.

Accordion style vehicle stop sticks are generally known in the relevant arts to exhibit various advantages over linear style stop sticks. Unfortunately, however, in order to ensure effective operation against a target vehicle the known accordion style stop sticks must be carefully deployed in order to ensure that the stop stick is right side up. Because in at least some circumstances, the press of time or other environmental and/or officer safety issues result in such a stop stick being inadvertently deployed upside down, generally resulting in a missed opportunity to stop the offending vehicle. Additionally, the known accordion style stop sticks are also generally prone to snapping back upon deployment, causing the expanded stop stick to contract and, as a consequence, reducing the available length of stop stick and also often resulting in missed opportunity to stop the offending vehicle.
Still further, when either of these situations occurs, a deploying officer may attempt to perform post deployment adjustment of the incorrectly deployed stop stick. Unfortunately, such behavior causes the officer to be exposed to traffic and, in many cases, has resulted in serious injury and even fatality. As a result, it is an overriding object of the present invention to improve over the prior art by teaching an accordion style vehicle tire deflation system that is particularly adapted for effective operation regardless of whether the stop stick is deployed right side up or upside down and that is also generally impervious to inadvertent post deployment collapses.


A brushless motor control device includes a brushless motor including a rotor magnet and a stator coil; rotor position detection means for detecting positions of a plurality of magnetic poles of the rotor magnet; vibration detection means for detecting an unnecessary vibration of the brushless motor when the brushless motor is rotating; lead angle setting means for setting a magnitude of a lead angle such that a first output from the vibration detection means does not exceed a prescribed tolerable value; and lead angle correction means for providing the lead angle to a third output, from the rotor position detection means, in accordance with a second output from the lead angle setting means, so as to generate a translocation timing of a driving current to the stator coil.

Conventionally, a plurality of types of information discs of different recording formats are handled by one type of disc apparatus for recording information thereto and reproducing information therefrom. In the case of optical discs, for example, a disc apparatus for handling discs such as DVD-ROM discs, DVD-RAM discs, and CD-ROM discs has been put into practice.
This type of disc apparatus is often designed to provide each of elements such as a head, a disc motor, a signal processing LSI and the like with all the functions required for recording and reproduction of various types of discs. Therefore, a condition which is set for one type of disc may disturb a condition for another type of disc, which prevents improvements in performance.
For example, when designing a disc motor, the motor's characteristics are of ten determined in accordance with the rotation conditions of the disc which is to be rotated at the highest rate among all the types of discs used with the disc motor. In this case, in order to reduce the inverse electromotive force of the motor, the number of turns of the coil, for example, is decreased so as to reduce the number of linkage magnetic fluxes between the rotor magnet and the stator coil, thus reducing the generated torque per unit current (torque constant). As a result, inconveniences occur such that, for example, the generation torque of the motor is reduced, and the time required to change the rotation rate of the motor to the target rotation rate is extended.
For example, in the case of a disc apparatus handling discs such as DVD-ROM discs, DVD-RAM discs and CD-ROM discs, the rotation rate required of a spindle motor for recording information to and reproducing information from a DVD-RAM disc is about 3250 rpm at the maximum. In order to increase the speed of a seek operation for the purpose of performing ZCLV (Zoned Constant Linear Velocity) control, a high torque is required for speeds in the range of 1350 rpm (which is a relatively low rate) to 3250 rpm. For recording information to or reproducing information from CD-ROM discs and DVD-ROM discs, there is a strong demand for high speed reproduction. Information on CD-ROMs is often required to be reproduced at a speed of x40 or higher. In order to realize this, a maximum rotation rate of about 9000 rpm is required. Since such a high rotation rate is required only for reproduction, it is not necessary to change the rotation rate during a seek operation owing to a circuit having, for example, a jitter-free structure. Therefore, a very high torque is not needed for a seek operation.
As described above, when the motor coil is designed to provide a high rotation rate and a low torque so as to realize a high reproduction speed which is demanded for CD-ROM discs and DVD-ROM discs, the high torque required for the high speed seek operation for the DVD-RAM discs is not obtained. By contrast, when the motor coil is designed with a larger number of turns to provide a low rotation rate and a high torque for DVD-RAM discs, the rotation rate required for the high speed reproduction for the CD-ROM discs and DVD-ROM discs is not obtained. In this case, these two requirements cannot be provided by one motor.
Japanese Laid-Open Publication No. 10-127086 discloses a technology for making the torque constant of a motor variable by offsetting the translocation timing, for the electric current flowing to the stator coil of the motor, from the regular timing. This technology will be described with reference to FIG. 9.
FIG. 9 shows a structure of a conventional control device 400 for a brushless motor. The control device 400 includes an AC power supply 111, a rectifying and smoothing circuit 112, a switching power supply 113 for outputting a DC voltage VM, a driving control circuit 114 for receiving the DC voltage VM, a pulse width modulation circuit 115, rotor position detectors 108U, 108V and 108W, and a DC motor 123.
The driving control circuit 114 includes a differential amplifier 116 for removing a noise component from three-phase output signals HU′, HV′ and HW′ from the rotor position detectors 108U, 108V and 108W, comparators 117U, 117V and 117W for comparing the three-phase output signals HU′, HV′ and HW′, amplifiers 120U, 120V and 120W for amplifying one of two output signals of the three-phase output signals HU′, HV′ and HW′ which are respectively input to the comparators 117U, 117V and 117W, a logic circuit 118, a current switching circuit 119, a frequency/voltage converter (F/V converter) 121, and amplification ratio varying devices 122U, 122V and 122W.
Here, the amplification ratio of each of the amplifiers 120U, 120V and 120W is K. The comparator 117U compares a multiplication signal HU1 obtained by multiplying the U-phase output signal HU′ from the differential amplifier 116 by amplification ratio K, with the V-phase output signal HV′, and outputs a comparison signal HU2. The comparator 117V compares a multiplication signal HV1 obtained by multiplying the V-phase output signal HV′ from the differential amplifier 116 by amplification ratio K, with the W-phase output signal HW′, and outputs a comparison signal HV2. The comparator 117W compares a multiplication signal HW1 obtained by multiplying the W-phase output signal HW′ from the differential amplifier 116 by amplification ratio K, with the U-phase output signal HU′, and outputs a comparison signal HW2.
The comparison signals HU2, HV2 and HW2 are input to the logical circuit 118. The logical circuit 118 outputs U-, V- and W-phase positive (N-pole) output signals HUU, HVU and HWU to the current switching circuit 119. Simultaneously, the logical circuit 118 outputs U-, V- and W-phase negative (S-pole) output signals HUL, HVL and HWL to the current switching circuit 119.
The current switching circuit 119 turns ON switching power elements TRU1, TRV1, and TRW1 through the U-, V- and W-phase positive poles, and turns ON switching power elements TRU2, TRV2, and TRW2 through the U-, V- and W-phase negative poles. Thus, the current switching circuit 119 sequentially provides a DC voltage VM to the 3-phases 107U, 107V and 107W of the DC motor 123.
The F/V converter 121 converts the output from the differential amplifier 116 into a voltage signal. The amplification ratio varying devices 122U, 122V and 122W vary the amplification ratio K of the amplifiers 120U, 120V and 120W in accordance with the output from the F/V converter 121.
Owing to the above-described structure, when one of the two signals input to each of the comparators 117U, 117V and 117W is respectively amplified by the amplifiers 120U, 120V and 120W at the amplification K where K>1, a lead angle Δθ is given to the three phases 107U, 107V and 107W of the DC motor 123. The lead angle Δθ is set to an optimum value in accordance with the rotation rate of a rotator assembly by the function of the F/V converter 121.
The above-described control device 400 for a brushless motor has the following problems.
When a large lead angle is given to the brushless motor (for example, the DC motor 123), the torque ripple of the brushless motor is increased, and thus an unnecessary vibration of the control device 400 is increased. This makes it difficult to apply the control device 400 to a precision device which is vulnerable to vibrations. The magnitude of vibration is determined by a composite of factors including variance in a vibration adding force occurring due to individual variances among brushless motors and variance in vibration transfer characteristics of the entirety of the control device 400 which is associated with the variance in vibration adding force. In order to restrict the magnitude of the unnecessary vibration to a prescribed value or less with an allowance for all the variance factors, it is necessary that the adjustable range of the lead angle be restricted to be narrow. Thus, the motor's characteristics cannot be significantly changed. When a large lead angle is given to the brushless motor, there occurs another problem that the reliability of the control device 400 for restricting the vibration level to a prescribed level or less is not sufficient.
The level at which the disc apparatus using a brushless motor is allowed to vibrate varies depending on whether an information disc having a high recording density such as a DVD disc is used or an information disc having a low recording density such as a CD-ROM disc is used. As a result, the range of lead angle which can be set for the brushless motor varies. The level at which the disc apparatus using a brushless motor is allowed to vibrate also varies depending on whether a reproduction-only DVD-ROM disc is used or a recordable and reproduceable DVD-RAM disc is used. The range of lead angle which can be set for the brushless motor varies. Such a change in the allowed level of vibration was not conventionally considered.
The above-described disc apparatus complicates the control of variable lead angles, which makes it difficult to simplify the motor control structure. The reason is that the lead angle is set in accordance with the rotation rate. Such a system requires elements including the F/V converter and also requires that the rotation rate be monitored constantly so as to update the lead angle. As a result, a circuit dedicated to setting the lead angle is required, or use of interrupts is often required in order to update the lead angle in the case where a CPU, a DSP or the like is used.
In the case where the target rotation rate is frequently changed and it is necessary to control the actual rotation rate to follow the target rotation rate, the driving current amplitude needs to be controlled while changing the lead angle. Since two parameters are changed simultaneously, the control operation is complicated.
The setting precision of the lead angle is deteriorated due to the variance in the amplitude among the outputs from the three rotor position detectors 108U, 108V and 108W and also due to the waveform distortion of the outputs. When the outputs from the rotor position detectors 108U, 108V and 108W have ideal sine wave signals having equal amplitudes to each other, an accurate lead angle can be set for the following reason. By amplifying one of the two outputs by a constant value and synthesizing the amplified output with the other output, a sine wave signal having a phase which is shifted by a desired amount can be formed. In actuality, however, the outputs from the three rotor position detectors 108U, 108V and 108W have different amplitudes due to, for example, the individual variance among rotor position detectors (for example, hall elements) or changes in characteristics of the rotor position detectors which occur due to temperature. When such signals having different amplitudes are used, the lead angle is different among the U-, V-, and W-phases. This generates an error in the lead angle among the phases. In addition, the outputs from the rotor position detectors 108U, 108V and 108W themselves do not have pure sine waveforms. Due to, for example, the variance in magnetization characteristics of the rotor magnet, the waveforms of the outputs may sometimes be distorted with a high harmonic component superimposed on the output being large. In such a state, the relationship between the amplification ratio K and the lead angle significantly changes from the relationship when a pure sine wave signal is obtained. This deteriorates the setting precision of the lead angle.
It is not necessary that the lead angle can be arbitrary controlled. It is possible to preset the lead angle as one factor with respect to the rotation rate of the motor. This factor generally increases in accordance with the increase in the rotation rate of the motor (∝hall output frequency) in a simple manner. Such a factor is very easily realized by, for example, using a differentiation circuit. Japanese Laid-Open Utility Model Publication No. 62-48198 discloses a technology for setting a lead angle in accordance with the rotation rate of the two-phase pulse motor using the differentiation circuit. Such a technology will be described with reference to FIG. 10.
FIG. 10 shows a structure of a conventional pulse motor driving circuit 500. The pulse motor driving circuit 500 includes a two-phase exciting pulse motor 131, a high resolution encoder 132 connected to the pulse motor 131 for generating an output signal Sf in accordance with a rotation angle θ of the pulse motor 131, an angle calculation circuit 133 for calculating a rotation angle θm of the pulse motor 131 with respect to the magnetic pole based on the output Sf of the encoder 132, a factor generation circuit 134 for generating sine wave signals Ss and Sc having a phase difference of 90 degrees with each other in accordance with the rotation angle θm, multipliers 135 and 136 for varying the amplitudes of the sine wave signals Ss and Sc in accordance with the amplitude of a control signal Si, phase leading circuits 139 and 140, and power amplifiers 137 and 138. Outputs IA and IB of the power amplifiers 137 and 138 are respectively provided to armature coils (not shown) of the pulse motor 131.
FIG. 11 shows an exemplary structure of the phase leading circuits 139 and 140. The phase leading circuits 139 and 140 shown in FIG. 11 each include an amplifier 141, resistors 142 and 143, and a capacitor 144. A phase leading amount of the phase leading circuits 139 and 140 is selected so as to compensate for a phase delay of the magnetic flux with respect to the frequency change in the exciting current.
The position of the rotor (not shown) in the pulse motor 131 is detected by the encoder 132 and the angle calculation circuit 133. The exciting currents IA and IB corresponding to the position are respectively provided to the armature coils.
The amplitudes of the outputs Ss and Sc from the factor generation circuit 134 are represented by expression (1).Ss=sin(θm+π/2)Sc=cos(θm+π/2)  (1).
Where the amplitude of the control signal Si is Io, the magnitudes of the exciting currents IA and IB supplied to the armature coils of the pulse motor 131 are represented by expression (2).IA=Io*sin(θm+π/2)IB=Io*cos(θm+π/2)  (2).
As is clear from expression (2), the exciting currents IA and IB supplied to the respective armature coils have a phase difference of 90 degrees, and the sum thereof (vector synthesis) is constant. Therefore, the rotor generates a constant torque without non-uniformity. The magnitude of the torque is in proportion to the amplitude Io of the control signal Si. Therefore, when the load is zero, the pulse motor 131 is paused if Io is zero. When Io increases, the pulse motor 131 rotates at the rate in accordance with Io.
The electric angle in the synthesis current of the exciting currents IA and IB always has a phase difference of 90 degrees with respect the mechanical angle (rotation angle θ) of the rotator of the pulse motor 131. Therefore, the maximum torque can be generated.
However, when the pulse motor 131 goes into a high rate operation area and thus the frequency of the exciting currents IA and IB increases, the phase of the magnetic flux generated with respect to the driving current is delayed due to the iron loss in the magnetic path or the like. As a result, the maximum torque cannot be generated.
In order to avoid this, the phase leading circuits 139 and 140 are provided in the exciting circuit. When the pulse motor 131 goes into the high rate operation area and thus the frequency of the exciting currents IA and IB increases, the phases of the exciting currents IA and IB are led by the phase leading circuits 139 and 140. Accordingly, the phase delay of the magnetic flux caused by the iron loss in the magnetic path can be compensated for by the leading phase of the exciting currents IA and IB. Thus, it is possible to maintain the phase difference between the mechanical angle and the magnetic flux of the rotor so as to prevent a reduction in the generated torque.
The pulse motor driving circuit 500 has the following problems.
It is assumed that the pulse motor driving circuit 500 is applied to a disc apparatus, and the translocation timing for the electric current flowing to the stator coil of the motor is offset from the regular timing so as to make the torque constant of the motor variable. When it is attempted to realize a high maximum rotation rate required for the high speed reproduction of the CD-ROM discs and the DVD-ROM discs in this state, the phase is excessively led even when the DVD-RAM discs are rotated at a low rate for a high speed seek operation, resulting in a reduction in the torque.
This will be described in detail with reference to FIG. 12. FIG. 12 shows the relationship between the rotation rate and the phase lead angle which is obtained by the phase leading circuit. Characteristic 28 shown in FIG. 12 shows the relationship between the rotation rate and the phase lead angle when the constant of the phase lead circuit is set so as to be appropriate to the high speed reproduction of the CD-ROM discs. Characteristic 28 is obtained when, for example, value R1 of the resistor 143 is set to a relatively small value, the value of the capacitor 144 is set to 0.01 μF, and value R2 of the resistor 142 is set to 21 kΩ in the phase leading circuits 139 and 140.
This setting has main purposes of making the lead angle larger than the lead angle which is necessary to compensate for the current delay caused by the inductance component of the coil, reducing the torque constant of the motor by the effect of the weak field, and restricting generation of an inverse electromotive force so as to improve the maximum rotation rate of the motor. In this manner, the rotation rate of 9000 rpm which is required for x42 reproduction of a CD-ROM disc can be obtained using a disc motor having a no-load rotation rate of 6300 rpm, a starting torque of 190 gcm and a torque constant of 0.17 gcm/mA.
However, characteristic 28 results in a phase lead angle as large as about 10 to 23 degrees with respect to the rotation range of the DVD-RAM discs of 1370 to 3250 rpm. Since the torque constant is reduced by the effect of the weak field, the seek time is undesirably delayed in a DVD-RAM disc which requires the rotation rate to be changed during the seek operation for performing the ZCLV control.
Characteristic 27 shown in FIG. 12 shows the relationship between the rotation rate and the phase lead angle which is appropriate for recording information to or reproducing information from DVD-RAM discs. Characteristic 27 is obtained when R2 is set to a relatively small value, the value of the capacitor 144 is set to 0.01 μF and R1 is set to 6 kΩ. This setting has main purposes of making the lead angle larger so as to be sufficient to compensate for the current delay caused by the inductance component of the coil and maximizing the torque constant of the motor.
Thus, the time of the seek operation of a DVD-RAM disc performed by the same disc motor can be shortened. However, characteristic 27 results in a maximum rotation rate as low as about 5700 rpm, which is not sufficient for the high speed reproduction of information on CD-ROM discs.
As described above, the conditions for the high speed reproduction and the conditions for reduction in the seek time conflict with each other with a single circuit constant setting. It is ideal to realize, for example, characteristic 29 shown in FIG. 12 by which the lead angle rapidly increases when the rotation rate of the motor reaches a prescribed level. However, it is difficult to realize characteristic 29 with the phase leading circuits 139 and 140 shown in FIG. 11.
The present invention for solving the above-described problems has an objective of providing a control device for a brushless motor which is highly reliable against vibrations, is capable of performing easy motor control, and provides a high setting precision of a lead angle; and a disc apparatus using the same.
The present invention also has an objective of providing a disc apparatus for realizing, with one motor and a simple structure, both a high speed seek operation for ZCLV control when recording information to or reproducing information from a DVD-RAM disc and a high speed reproduction operation of a CD-ROM disc and a DVD-ROM disc.

Brushless motor control device and disc apparatus using the same

Matsushita Electric Industrial Co., Ltd.


Apparatus for and method of rapid three dimensional scanning and digitizing of an entire microscope sample, or a substantially large portion of a microscope sample, using a tilted sensor synchronized with a positioning stage. The system also provides a method for interpolating tilted image layers into a orthogonal tree dimensional array or into its two dimensional projection as well as a method for composing the volume strips obtained from successive scans of the sample into a single continuous digital image or volume.

1. Field of the Invention
The invention relates generally to the field of optical microscopy, and in particular to an automatic microscope scanner enabling rapid three dimensional image acquisition.
2. Related Art
Automated microscope scanners such as disclosed in U.S. Pat. No. 6,711,283, which is incorporated herein in its entirety, enable rapid digitizing of an entire glass slide with a biological sample. These microscope scanners are particularly efficient when the sample thickness, i.e. the depth of the specimen on the glass is smaller or close to the depth of field of the microscope lens. The depth of field is the distance in front of and behind the theoretical focal plane where the specimen appears to be in focus.
A problem commonly arises when the specimen has a thick volumetric structure. On one hand, smaller depth of field provides better spatial resolution along the third dimension of the volumetric specimen and reduces image fusion from adjacent depth layers. On the other hand, it becomes increasingly difficult to ensure focus in microscope scanners with small depth of field as the thick specimen may have a significant depth variance within the field of view. The microscopist may need to observe the same region of the specimen at multiple focal planes. Consequently, such volumetric specimens cannot be digitized efficiently with two-dimensional scanners.
Conventional scanners are designed to ensure a tradeoff between the focus quality and the magnification at which the sample can be viewed. While higher magnification microscope objective lenses normally have higher numerical apertures (NA) and provide the microscopist with higher resolution images, the depth of field decreases. For example, at low magnification such as 10 times (10×) and small NA such as 0.25, a microscope system may have the depth of field of 8.5 um. At higher magnification such as 40× and larger NA such as 0.65, the depth of field is reduced to 1.0 um. At high numerical aperture lenses, depth of field is determined primarily by wave optics, while at lower numerical apertures, the geometrical optical circle of confusion dominates the phenomenon.
One can approach a solution to the depth of field problem by improving the focus accuracy of the microscope scanner. Existing automatic focus methods include such techniques as pre-focusing in points obtained from the macro focus image and generating a three-dimensional data set corresponding to an optimal specimen distance as disclosed in U.S. Pat. No. 6,816,606. Provided the scanner follows precisely this three dimensional profile, it captures an image with increased contrast. Other autofocus methods include tilt designs of either the glass sample or the sensor detecting the focus position. For example, some methods for high speed autofocus by means of tilted designs are described in U.S. Pat. No. 6,677,656 and US Patent Publication Nos. 2005/0089208, 2004/0129858.
The focus accuracy is important at high magnifications to the extent of the specimen thickness. After an accuracy level is achieved matching the thickness of the specimen, no further advance can be made to improve the focus quality of the digital image. In particular, a thick specimen with a three dimensional structure or volume texture cannot be fully represented by its two dimensional image. A linear array sensor typically used in scanning microscopes cannot capture optical images from different focal planes within its field of view at the same time. If the depth of specimen structure varies to a large extent, no uniform focus can be attained within the field of view.
The above focus problem can be addressed by capturing a series of digital images from different focal planes. This series is known as an image stack or an image volume and provides an extended depth of field and preserves the three dimensional structure of the specimen. Image volumes can be further transformed into a three dimensional model or fused into a two dimensional image with enhanced focus. A number of microscope designs are available to acquire image stacks, for example, described in US Patent Publication No. 2004/0264765.
A conventional approach to image stack acquisition is repeated scans with a linear or area scan camera. A drawback of this approach is a substantial increase of the scanning time and memory usage to store digital images. For example, in order to capture a stack of 20 images, a conventional scanner will need to perform 20 runs followed by alignment and stitching procedures. An area scan microscope working in an image stack tiling mode is likely to be inadequately slow and may introduce stitching artifacts to the output volume image. This performance drawback may be critical for express diagnostic applications in a clinical environment and real-time surface inspection applications in an industrial environment.
Therefore, what is needed is a system and method that overcomes these significant problems found in the conventional systems as described above.

Rapid microscope scanner for volume image acquisition


A pointer for a gauge or an instrument cluster assembly is provided. The pointer is formed of a light conducting material. In one form, indicia are disposed about the axis of rotation and/or on a surface, the plurality of indicia configured to be selectively illuminated by the pointer. A second end of the pointer may be configured to be selectively rotated adjacent to each indicium of the plurality of indicia and to illuminate the indicia when the light guide pointer is disposed adjacent to the indicia. The second end may be wider than a first end of the pointer. In some variations, the pointer may have a fan shape, and the indicia may be configured as tick marks defining a bar graph. In some forms, opaque material may be disposed on the pointer, the opaque material defining a plurality of indicia on the pointer.

The background description provided herein is for the purpose of generally presenting a context of this disclosure. Work of the presently named inventors, to the extent it is described in this background section, as well as aspects of the description that may not otherwise qualify as prior art at the time of filing, are neither expressly nor impliedly admitted as prior art against the present disclosure.
Vehicles include instrument panels, typically having several gauges and dials that communicate vehicle conditions such as speed, engine RPM, temperature, oil pressure along with many other operational parameters.
Each vehicle gauge typically includes a pointer that rotates about an axis to point to a specific graphic on the gauge dial to indicate a current vehicle operating parameter. Pointer assemblies can be illuminated. In some variations, a light housing forms a plurality of pockets containing light sources, which is covered by a gauge surface. A plurality of tick marks or indicia, or a translucent or transparent surface may be formed by the gauge surface over the pockets. The light sources in the pockets may be selectively illuminated as the pointer travels over them, by way of example, to form a bar graph display.
Typically, a wall is disposed between each pocket to prevent light leakage from one pocket to another, in order to display an appearance of a discrete value. Each wall must necessarily have a certain thickness separating each pocket. Every pocket has its own light source, and therefore, a number of LEDs or other light sources, along with associated electronics, are required.
It is desirable to provide and develop gauge assemblies that provide substantially uniform illumination, but with ample lighting and minimal electronics. Accordingly, it is desirable to design and develop a pointer assembly and gauge that meets such criteria.

Pointer for illuminating bar graph gauges