The battery tester of the present invention includes a heating element for generating heat in response to current supplied from a battery, and an indicator provided in proximity to the heating element for providing a visual indication of the remaining capacity of the battery in response to the heat generated by the heating element. The heating element has a display portion and first and second connecting portions on either side of the display portion that are selectively coupled to opposite terminals of the battery. The connecting portions of the heating elements have a lower resistivity than the display portion thereby reducing the heat generated at the switch contacts that are pressed by the user to activate the tester.

The present invention generally pertains to battery testers, and more particularly, relates to on-label thermochromic battery testers.
Batteries are often stored before being used. Batteries are typically stored by retailers before being sold. After purchase by a consumer, such batteries are again typically stored for some period of time prior to use. If the period of storage is significant, batteries may self-discharge. Therefore, it is desirable to utilize a battery tester to determine if a battery has sufficient charge to operate a desired device.
It is also desirable, on frequent occasions, to determine the remaining life of batteries which are in use. Many "good" batteries are discarded simply because the user cannot recall how long they have been used in a particular device, i.e., a camera, tape deck, etc. For similar reasons, batteries often reach a useless or near useless state of discharge when no replacements are readily available. Separate or stand-alone battery testers are known which indicate remaining battery power. However, such testers are easily misplaced and cumbersome to use.
Battery testers have been described that are included in a label secured to a battery. One type of on-label battery tester is known as a "thermochromic battery tester." Thermochromic battery testers typically include a conductive element that is selectively connected between opposite terminals of the battery. The conductive element includes a switch pad at one or both ends that is pressed by the user to connect the conductive element across the terminals of the battery. When the conductive element is connected between the battery terminals, it generates heat as a function of its resistivity and the current flowing from the battery. The level of current produced by the battery is one indicator of remaining battery capacity. Thermochromic testers further include a thermochromic layer, which changes its color or visual appearance as a function of the heat generated by the conductive element. By changing the visual appearance of the thermochromic layer, a thermochromic on-label battery tester may provide an indication of the discharge level of the battery. For example, a thermochromic material that changes between opaque and transparent states may be utilized to expose indicia underlying the thermochromic layer indicating that the battery is still "good" when a sufficient level of current is output from the battery.
To produce such thermochromic battery testers in the simplest manner and at the lowest cost, the conductive heating element is printed at a single printing station using a single conductive ink material. A suitable material that may be readily printed on a substrate and that exhibits suitable heat-generating properties in response to the current from the battery, is silver ink. The silver ink is typically printed so that the resistivity of the ink film is the same in all portions of the circuit. Although the thermal flux can be focused by making the circuit narrower and the resistance higher where a high flux is required, the entire circuit acts as a heater. As a result, a low resistance circuit which draws high current is required to produce sufficient thermal flux in the display section. Because silver ink is relatively expensive, the conductive heating element thus constitutes a significant portion of the total cost of providing a battery tester on a battery label.
Another problem associated with conventional thermochromic on-label battery testers is that the contact switches that a user is required to press to activate the tester may become relatively hot due to the high current levels flowing through the conductive element. Although the heat generated at the switch contacts is not hot enough to burn the user's fingers, this heat nevertheless may create an unpleasant sensation for the user.

Battery tester having sections of different resistivity


A goods supply system that retrieves parts for making up a product from goods storage locations in a supply area and supplies them to an assembly line, which comprises: a storage means that registers key information on the product and parts information including information on types and storage locations of the parts in advance; a first in-process card issuing machine that writes the key information on the product into a first in-process card; and a retrieving unit having a means that reads out the key information written in the first in-process card, collates the key information with the key information and the parts information registered in the storage means, and retrieves the parts corresponding to the key information from the goods storage locations.

The present invention relates to a goods supply system. The goods supply system may, for example, supply goods to a predetermined place in a production site of a product.
A goods supply system that supplies goods may use the operation instruction control system disclosed in Japanese Patent Application Publication No. 2005-190, for example. In the operation instruction control system disclosed in this document, first, a production control CPU delivers operation instruction information by processes. Next, an ID tag writing device receives the operation instruction information by processes and writes the information into ID tags. Then, the ID tag with the operation instruction information by processes written is applied to the goods to be operated, and the goods to be operated are conveyed to operation areas by processes.
However, supplying parts by using the above conventional technique will require writing a massive amount of operational instruction information, such as types of products, types and quantities of parts, and the like, into an ID tag. Therefore, if there is a limitation on the storage capacity for the ID tag, information other than the operation instruction information (e.g., control information or the like) cannot be written into the ID tag, which leads to a problem such that the other processes using the ID tag concerned cannot be performed.
The present invention is directed to a goods supply system capable of supplying necessary goods to a predetermined place with a minimum quantity of information written in an information recording medium.


A bushing for a hydraulic valve has a bushing wall having openings allowing passage of a hydraulic medium to and from an interior of the bushing. The openings have an opening wall that at least across a portion of a circumference of the opening wall is formed as a molded bevel. The molded bevel is positioned at an acute angle to a radial plane of the bushing wall. The bushing wall has outer annular channels and the openings open into the outer annular channels, respectively.

1. Field of the Invention
The invention relates to a bushing for a hydraulic valve comprising openings in the bushing wall for allowing passage of hydraulic medium.
2. Description of the Related Art
Such bushings are used, for example, for cartridge valves in camshaft adjusting devices. Through the openings in the bushing the hydraulic medium is supplied to supply bores which are located in a cylinder head, an engine block, or a valve receiving block. The bushings are produced by turning from rod material of steel or light metal or are produced as cast light metal parts. The openings are mechanically produced or at least mechanically post-machined. Accordingly, the bushings are expensive with regard to their manufacture.


This invention discloses a photonic system to beamform the electric field yield by a phased array antenna. The system function relies on a photonic tunable delay line, which consists on an optical Mach-Zehnder interferometer with a predefined time delay difference between arms. The time delay is tuned by adjusting the coupling ratio between the power applied to each one of the interferometer's delay lines. Three embodiments are proposed, wherein one of them just uses a single delay line and a single monochromatic light source, independently of the quantity of the array elementary antennas.

A PAA comprises N antennas disposed along the three spatial dimensions. The antennas which form the PAA are known as elementary antennas. A PAA allows the optimization and the beamforming of the radiated electrical field through the adjustment of the amplitude and phase of the radio frequency (RF) signals sent to each elementary antenna. This is an exclusive feature for the PAA's, since in an individual antenna the optimization of the radiated electrical field depends on the antenna's design. In addition, the beamforming of the radiated electrical field depends on the spatial orientation of the antenna.
As previously said, the beamforming of the electrical field radiated by the PAA can be controlled through the phase of the RF signals applied to each elementary antenna. More precisely, the PAA can be fed by a single RF signal, which is split to all elementary antennas including a tunable phase shift. Although tunable, the phase shift is constant. This means the induced phase shift value is correct only for a specific RF frequency. In a PAA, this implies that the emitted frequency should be constant. Otherwise, different RF frequencies get different phase shifts, and so the beamforming of the electric field becomes dependent on the emitted frequency. In the case of data transmission over one RF carrier frequency, this implies that the data signal bandwidth should be as low as possible. Since there are many applications with high bandwidth (e.g., RADAR signals, Gb/s wireless networks, radio astronomy, etc.), the beamforming of the radiated electric field cannot be efficiently performed with such a technique.
This problem can be solved using phase shifts that depend on RF frequency. In practice, a phase shift depending on frequency consists in a time delay line. Therefore, instead of a phase shift, each elementary antenna should include a tunable time delay. The electrical implementation of a tunable time delay is particularly challenging at high frequencies, since increasing time delays implies increasing the length of the delay line, which in turn leads to greater insertion losses and a reduction in bandwidth. Such disadvantages are overcome using photonic implementations of tunable delay lines. The advantages of photonic systems consist on low losses, broad bandwidth, lighter weights, smaller dimensions and immunity to electromagnetic interference. Generally, a PAA with tunable photonic delay lines is characterized in that it has an electro-optical modulator, which converts the RF signal to the optical domain, followed by an optical processing system which delays and distributes the modulated optical signal according to what the needs of the different antennas are. The optical signals are converted to the electrical domain using photodetectors.
The patents summarized below describe different implementations of photonic TODL's, which can be applied to PAA.
U.S. Pat. No. 5,428,218 discloses a photonic TODL based on spatial multiplexing. In such free-space implementation, the optical signal is directed into a given optical fiber through the adjustment of mirrors. As different optical fibers have different lengths, one can get a discrete tuning of the time delay added to the optical signal. This implementation also includes the possibility of having a multi-beam system, e.g., the system can be simultaneously used by more than one optical signal.
U.S. Pat. No. 5,978,125 discloses a photonic TODL based on polarization multiplexing. In a birefringent medium, an optical signal with a specific state-of-polarization (SOP) has a higher time delay than the orthogonal SOP. By selecting one of the two SOP's, the added time delay can then be controlled. This method is described in a cascaded configuration, in which serial birefringent media are intercalated by polarization controllers (PC's). As a result, a discrete delay tuning is obtained.
U.S. Pat. No. 5,461,687 discloses a photonic TODL based on dispersive means. By tuning the wavelength of the input optical signal the path by which the signal propagates changes, resulting in a tunable time delay. In this patent, the dispersive mean is implemented in a free space using a diffraction grating. Another possible option is to use fiber Bragg gratings (FBG's) located in different points of an optical fiber.
U.S. Pat. No. 5,751,466 discloses a photonic TODL which uses the frequency response of a photonic bandgap device. An example of such a device is a FBG. This device consists of a dielectric structure in which the refractive index varies longitudinally. The control of the refractive index's variation along the structure results in changing the frequency response of the device, therefore affecting the time delay added to the photonic signal.
U.S. Pat. No. 7,558,450 B2 discloses a photonic TODL composed by three resonant elements coupled to a waveguide. This implementation is limited to single sideband (SSB) optical signals. The symmetric displacement in the frequency of two resonant elements enables the adjustment of time delay induced to the RF carrier. The third resonant element adjusts the phase of the optical carrier (OC) in order to avoid involuntary phase shifting of RF signal. Of greater importance than the tuning method, is the fact that this patent is clearly appropriate to RF signals without any spectral content between the optical and the RF carriers. As a result, the TODL's frequency response is irrelevant at frequencies located between the RF carrier and the OC.

Photonic system and method for tunable beamforming of the electric field radiated by a phased array antenna


A new method for transmitter-receiver design that enhances the desired signal output from the receiver by whitening the total interference and noise input to the receiver and maximizing the output Signal to Interference plus Noise power Ratio (SINR) is presented. As a result of the whitening process, the receiver “sees” a desired signal in white noise, and the receiver structure is then optimized to maximize the receiver output at the desired decision making instant. Furthermore the new design scheme proposed here can be used for transmit signal energy and bandwidth tradeoff. As a result, transmit signal energy can be used to tradeoff for “premium” signal bandwidth without sacrificing the system performance level in terms of the output Signal to Interference plus Noise power Ratio (SINR).

Consider a desired target that is buried in both interference and noise. A transmit signal excites both the desired target and the interference simultaneously. The interference and/or interferences can be foliage returns in the form of clutter for radar, scattered returns of the transmit signal from the sea-bottom and different ocean-layers in the case of sonar, or multipath returns in a communication scene. The interference returns can also include jamming signals. In all these cases, like the target return, the interference returns are also transmit signal dependent, and hence it puts conflicting demands on the receiver. In general, the receiver input is comprised of target returns, interferences and the ever present noise. The goal of the receiver is to enhance the target returns and simultaneously suppress both the interference and noise signals. In a detection environment, a decision regarding the presence or absence of a target is made at some specified instant t=to using output data from a receiver, and hence to maximize detection, the Signal power to average Interference plus Noise Ratio (SINR) at the receiver output can be used as an optimization goal. This scheme is illustrated in FIG. 1.
The transmitter output bandwidth can be controlled using a known transmitter output filter having a transfer function P1(ω) (see FIG. 2B). A similar filter with transform characteristics P2(ω) can be used at a receiver input 22a shown in FIG. 1, to control the receiver processing bandwidth as well.
The transmit waveform set f(t) at an output 10a of FIG. 1, can have spatial and temporal components to it, each designated for a specific goal. A simple situation is that shown in FIG. 2A where a finite duration waveform f(t) of energy E is to be designed. Thus the total energy can be expressed in the time domain or frequency domain as
                                          ∫            0                          T              o                                                                                                                  f                                                        (                    t                    )                                                                              2                                                  ⅆ              t                                      =                                            1                              2                                π                                                                                ∫                                  -                  ∞                                                  +                  ∞                                                                                                                          F                                                                    (                        ω                        )                                                                                                  2                                                                  ⅆ                  ω                                                              =                      E            .                                                              Here                                              (        1        )                                          F                                (            ω            )                          =                              ∫                          -              ∞                                      +              ∞                                                                    f                                            (                t                )                                                                ⅇ                                                -                  jω                                                                                t                                                                ⅆ              t                                                          (        2        )            refers to the Fourier transform of the transmit waveform f(t).
Usually, transmitter output filter 12 characteristics P1(ω), such as shown in FIG. 2B, are known and for design purposes, it can be incorporated into the target transform and clutter spectral characteristics. Similarly, the receiver input filter if any (which may be at the input to the receiver 22) can be incorporated into the target transform as well as the clutter and noise spectra. Here onwards we will assume such to be the case.
Let q(t)⇄Q(ω) represent the target impulse response and its transform. In general q(t) can be any arbitrary waveform. Thus the modified target that accounts for the transmitter output filter has transform P1(ω)Q(ω). Here onwards, we shall refer to this modified form as the "target transform", and the associated inverse transform as the "target" response signal and represent them simply by Q(ω) and q(t) respectively. In a linear domain setup, the transmit signal f(t) interacts with the target q(t), or target 14 shown in FIG. 1, to generate the output below (referred to in S. U. Pillai, H. S. Oh, D. C. Youla, and J. R. Guerci, "Optimum Transmit-Receiver Design in the Presence of Signal-Dependent Interference and Channel Noise", IEEE Transactions on Information Theory, Vol. 46, No. 2, pp. 577-584, March 2000 and S. M. Kay, J. H. Thanos, "Optimal Transmit Signal Design for Active Sonar/Radar", Proceedings of IEEE International Conference on Acoustics, Speech, and Signal Processing, 2002 (ICASSP 02), Vol. 2, pp. 1513-1516, 2002):
                              s                                (            t            )                          =                                            f                                            (                t                )                                      *                          q                                            (                t                )                                              =                                    ∫              0                              T                o                                                                                f                                                  (                  τ                  )                                                                          q                                                  (                                      t                    -                    τ                                    )                                                                          ⅆ                τ                                                                        (        3        )            that represents the desired signal.
The interference returns are usually due to the random scattered returns of the transmit signal from the environment, and hence can be modeled as a stochastic signal wc(t) that is excited by the transmit signal f(t). If the environment returns are stationary, then the interference can be represented by the interference power spectrum Gc(ω). Once again, if a transmit output filter is present then |P1(ω)|2Gc(ω) represents the modified interference spectrum. Here onwards, the interference power spectrum so modified will be referred simply by Gc(ω). This gives the average interference power at the receiver input to be Gc(ω)|F(ω)|2 . Finally let n(t) represent the receiver 22 input noise with power spectral density Gn(ω). Thus the receiver input signal at input 22a equalsr(t)=s(t)+wc(t)*f(t)+n(t),   (4)and the receiver input interference plus noise power spectrum equalsGI(ω)=Gc(ω)|F(ω)|2+Gn(ω).   (5)The received signal is presented to the receiver 22 at input 22a with impulse response h(t). The general receiver is of the noncausal type.
With no restrictions on the receiver 22 of FIG. 1 such as causal or noncausal, its output signal component and interference/noise components at output 22b in FIG. 1 are given by
                                                        y              s                                                  (              t              )                                =                                                    s                                                  (                  t                  )                                            *                              h                                                  (                  t                  )                                                      =                                          1                                  2                                    π                                                                                ∫                                      -                    ∞                                                        +                    ∞                                                                                S                                                              (                      ω                      )                                                                                H                                                              (                      ω                      )                                                                                ⅇ                                          jω                                                                                t                                                                                ⅆ                    ω                                                                                and                            (        6        )                                                      y            n                                          (            t            )                          =                              {                                                                                w                    c                                                                          (                    t                    )                                                  *                                  f                                                        (                    t                    )                                                              +                              n                                                  (                  t                  )                                                      }                    *                                    h                                            (                t                )                                      .                                              (        7        )            The output yn(t) represents a second order stationary stochastic process with power spectrum below (referred to in the previous publications and in Athanasios Papoulis, S. Unnikrishna Pillai, Probability, Random Variables and Stochastic Processes, McGraw-Hill Higher Education, New York 2002):Go(ω)=(Gc(ω)|F(ω)|2+Gn(ω)|H(ω)|2   (8)and hence the total output interference plus noise power is given by
                                                                        σ                                  I                  +                  N                                2                            =                                                1                                      2                                        π                                                                                ∫                                          -                      ∞                                                              +                      ∞                                                                                G                        o                                                                                (                        ω                        )                                                                                ⅆ                      ω                                                                                =                                                1                                      2                                        π                                                                                ∫                                          -                      ∞                                                              +                      ∞                                                                                (                                                                                G                              c                                                                                (                              ω                              )                                                                                                                                              F                                                                                (                                  ω                                  )                                                                                                                                        2                                                                          +                                                                              G                            n                                                                                (                            ω                            )                                                                                )                                                                                                                                  H                                                                                (                            ω                            )                                                                                                                      2                                                                                ⅆ                        ω                                            .                                                                                (        9        )            Referring back to FIG. 1, the signal component ys(t) in equation (6) at the receiver output 22b needs to be maximized at the decision instant to in presence of the above interference and noise. Hence the instantaneous output signal power at t=to is given by the formula below shown in S. U. Pillai, H. S. Oh, D. C. Youla, and J. R. Guerci, "Optimum Transmit-Receiver Design in the Presence of Signal-Dependent Interference and Channel Noise", IEEE Transactions on Information Theory, Vol. 46, No. 2, pp. 577-584, March 2000, which is incorporated by reference herein:
                              P          o                =                                                                                            y                  s                                                                  (                                      t                    o                                    )                                                                    2                    =                                                                                                          1                                          2                                            π                                                                                ∫                                              -                        ∞                                                                    +                        ∞                                                                                S                                                                          (                          ω                          )                                                                                H                                                                          (                          ω                          )                                                                                ⅇ                                                  jω                                                                                t                            o                                                                                ⅆ                        ω                                                                                                            2                        .                                              (        10        )            This gives the receiver output SINR at t=to to be the following as specified in Pillai et. al., "Optimum Transmit-Receiver Design in the Presence of Signal-Dependent Interference and Channel Noise", incorporated herein by reference:
                    SINR        =                                            P              o                                      σ                              1                +                N                            2                                =                                                                                                                                  1                                              2                                                π                                                                                ∫                                                  -                          ∞                                                                          +                          ∞                                                                                S                                                                                (                            ω                            )                                                                                H                                                                                (                            ω                            )                                                                                ⅇ                                                      jω                                                                                t                              o                                                                                ⅆ                          ω                                                                                                                2                                                              1                                      2                                        π                                                                                ∫                                          -                      ∞                                                              +                      ∞                                                                                G                        I                                                                                (                        ω                        )                                                                                                                                  H                                                                                (                            ω                            )                                                                                                                      2                                                                                ⅆ                      ω                                                                                .                                              (        11        )            We can apply Cauchy-Schwarz inequality in equation (11) to eliminate H(ω). This gives
                              SINR          ≤                                    1                              2                                π                                                                                ∫                                  -                  ∞                                                  +                  ∞                                                                                                                              S                                                                          (                          ω                          )                                                                                                            2                                                                              G                      I                                                                                (                      ω                      )                                                                                ⅆ                  ω                                                                    =                                            1                              2                                π                                                                                ∫                                  -                  ∞                                                  +                  ∞                                                                                                                                  Q                                                                                (                            ω                            )                                                                                                                      2                                                                                                                                  F                                                                                (                            ω                            )                                                                                                                      2                                                                                G                          c                                                                                (                          ω                          )                                                                                                                                      F                                                                                (                              ω                              )                                                                                                                                2                                                              +                                                                  G                        n                                                                                (                        ω                        )                                                                                ⅆ                  ω                                                              =                                    SINR              max                        .                                              (        12        )            Thus the maximum obtainable SINR is given by the right side of equation (12), and this SINR is realized by the receiver design if and only if the following receiver transform referred to in previous prior art publications, is true:
                                                                                H                  opt                                                                  (                  ω                  )                                            =                                                                                S                      *                                                                                (                      ω                      )                                                                                G                          c                                                                                (                          ω                          )                                                                                                                                      F                                                                                (                              ω                              )                                                                                                                                2                                                              +                                                                  G                        n                                                                                (                        ω                        )                                                                                ⅇ                                                            -                      jω                                                                                t                      o                                                                                =                                                                                Q                        *                                                                                (                        ω                        )                                                                                F                        *                                                                                (                        ω                        )                                                                                G                          c                                                                                (                          ω                          )                                                                                                                                      F                                                                                (                              ω                              )                                                                                                                                2                                                              +                                                                  G                        n                                                                                (                        ω                        )                                                                                ⅇ                                                                  -                        jω                                                                                t                        o                                                                              .                                                                                (        13        )            In equation (13), the phase shift e−jωto can be retained to approximate causality for the receiver waveform. Interestingly even with a point target (Q(ω)≡1), flat noise (Gn(ω)=σn2), and flat clutter (Gc(ω)=σc2), the optimum receiver is not conjugate-matched to the transmit signal transform F(ω) as in the classical matched filter receiver.Prior Art Transmitter Waveform Design
When the receiver design satisfies equation (13), the output SINR is given by the right side of the equation (12), where the free parameter |F(ω)|2 can be chosen to further maximize the output SINR, subject to the transmit energy constraint in equation (1). Thus the transmit signal design reduces to the following optimization problem: Maximize
                                          SINR            max                    =                                    1                              2                                π                                                                                ∫                                  -                  ∞                                                  +                  ∞                                                                                                                                  Q                                                                                (                            ω                            )                                                                                                                      2                                                                                                                                  F                                                                                (                            ω                            )                                                                                                                      2                                                                                G                          c                                                                                (                          ω                          )                                                                                                                                      F                                                                                (                              ω                              )                                                                                                                                2                                                              +                                                                  G                        n                                                                                (                        ω                        )                                                                                ⅆ                  ω                                                                    ,                            (        14        )            subject to the energy constraint
                                          ∫            0                          T              o                                                                                                                  f                                                        (                    t                    )                                                                              2                                                  ⅆ              t                                      =                                            1                              2                                π                                                                                ∫                                  -                  ∞                                                  +                  ∞                                                                                                                          F                                                                    (                        ω                        )                                                                                                  2                                                                  ⅆ                  ω                                                              =                      E            .                                              (        15        )            To solve this new constrained optimization problem, combine equations (14)-(15) to define the modified Lagrange optimization function (referred to in T. Kooij, "Optimum Signal in Noise and Reverberation", Proceeding of the NATO Advanced Study Institute on Signal Processing with Emphasis on Underwater Acoustics, Vol. I, Enschede, The Netherlands, 1968.)
                              Λ          =                                    ∫                              -                ∞                                            +                ∞                                                                                {                                                                                                                                      Q                                                                                (                              ω                              )                                                                                                                                2                                                                                y                          2                                                                                (                          ω                          )                                                                                G                            c                                                                                (                            ω                            )                                                                                y                            2                                                                                (                            ω                            )                                                                                +                                                                        G                          n                                                                                (                          ω                          )                                                                                -                                                            1                                              λ                        2                                                                                y                        2                                                                                (                        ω                        )                                                                                }                                                          ⅆ                ω                                                                                where                            (        16        )                                          y                                (            ω            )                          =                                        F                                      (              ω              )                                                                    (        17        )            is the free design parameter. From equations (16)-(17),
            ∂      Λ              ∂      y        =  0gives (details omitted)
                                          ∂                          Λ                                            (                ω                )                                                          ∂            y                          =                              2                                      y                                            (                ω                )                                                                {                                                                                G                        n                                                                                (                        ω                        )                                                                                                                                  Q                                                                                (                            ω                            )                                                                                                                      2                                                                                {                                                                                G                              c                                                                                (                              ω                              )                                                                                y                              2                                                                                (                              ω                              )                                                                                +                                                                              G                            n                                                                                (                            ω                            )                                                                                }                                        2                                                  -                                  1                                      λ                    2                                                              }                                =          0.                                    (        18        )            where Λ(ω) represents the quantity within the integral in equation (16). From equation (18), either
                                          y                                      (              ω              )                                =          0                                                          or                            (        19        )                                                                                G                    n                                                                          (                    ω                    )                                                                                                                          Q                                                                    (                        ω                        )                                                                                                  2                                                                              {                                                                                G                        c                                                                                (                        ω                        )                                                                                y                          2                                                                                (                          ω                          )                                                                                +                                                                  G                        n                                                                                (                        ω                        )                                                                              }                                2                                      -                          1                              λ                2                                              =          0                ,                                                    which                                                              gives                                    (        20        )                                                      y            2                                          (            ω            )                          =                                                                          F                                                  (                  ω                  )                                                                    2                    =                                                                                G                    n                                                                          (                    ω                    )                                                                                (                                                      λ                                                                                                            Q                                                                          (                          ω                          )                                                                                                                            -                                                                                G                        n                                                                                (                        ω                        )                                                                                )                                                                    G                c                                                          (                ω                )                                                                        (        21        )            provided y2(ω)>0. See T. Kooij cited above incorporated by reference herein.
However, this particular method is not relevant to the current invention, since as disclosed in the next section, the current invention focuses on compressing and stretching out the total interference plus noise spectrum to be white (flat) over the desired frequency band of interest by redesigning the transmit signal transform accordingly.

This patent is subject to a terminal disclaimer.

Energy—bandwidth tradeoff and transmit waveform design using interference and noise whitening method


A molded generally planar U-shaped plastic member has a pair of lateral projections on one leg and a single lateral projection at a distal end of the other leg, which projections are received in recesses in mutually facing surfaces of a raised escutcheon rib surrounding a handle opening to locate the base of the U-shaped member in the path of the handle, blocking movement of the handle. A notch in the distal end of the leg having the single lateral projection receives a flat-bladed tool which is twistable against the escutcheon rib surface to deflect the leg inward and projection free of the respective recess to release the handle block. The recesses are symmetrically arranged to permit the handle block to be installed to block the handle ON or OFF as desired.

This invention pertains to handle blocks for electrical switching devices having an operating handle for manually moving the switch mechanism between ON and OFF conditions. More particularly, the invention pertains to handle blocks for electrical circuit breakers having pivotally operable handles projecting through an opening in the circuit breaker housing.
In certain applications for circuit breakers it is desirable to provide a blocking member for the handle to prevent the handle from being moved from an ON position to an OFF position or vice versa. The blocking member is not to be a lock for the handle, but merely to be a block; i.e. the blocking member may be intentionally removed to permit movement of the handle and operation of the circuit breaker. In prior art devices, the blocking member relies upon engagement thereof within the handle opening in the case for installation to the case. When the handle opening of the circuit breaker case is made particularly small and close fitting to the operating handle for purposes of sealing the housing against the ingress of foreign material, insufficient space is provided to attach a handle block within the handle opening in the case. One prior art handle block is made of sheet metal formed to a three-dimensional collar overlying the handle wherein it is both costly to manufacture and bulky to store when not in use. Still another prior art handle block comprises a multiple piece assembly which is spring biased into notches in sides of the handle opening, which is also costly to manufacture.

Handle block for electrical switching device


An electronic device, an information processing method and a method for determining display region are described and they include obtaining location relationship information of each slave electronic device with respect to the master electronic device, when connecting with at least one slave electronic device; obtaining a first size of the first display screen of the master electronic device, and a second size of the second display screen of each slave electronic device; determining a display region consisting of the first display screen and the second display screen, based on the location relationship information, the first size and the second size; and determining a first effective display region of the first display screen and a second effective display region of the second display screen which form an effective display region, based on a predetermined condition.

The present disclosure relates to the field of information processing, and particularly to an electronic device and an information processing method thereof.
The current electronic devices such as the mobile terminal, the tablet, etc. usually operate in a stand-alone mode. Therefore, usually, the electronic device performs operations such as unlocking, locking, etc., only based on corresponding input, such as gesture operations by user, received by the electronic device itself.
Recently, with the development of the technology of splicing multiple electronic devices to form a large display system, the electronic device may operate in two work modes of the stand-alone mode and a link mode. It becomes a problem about how to perform the operation corresponding to the work mode based on the received input in two different work modes.
For example, in the link mode, different from the situation where the individual electronic device is unlocked/locked by a gesture operation on the single electronic device, it is often desirable to unlock/lock the display system by a gesture operation in the operation region of the display system consisted of multiple electronic devices from the user's perspective. Therefore, it becomes a problem about how to perform corresponding unlock/lock operation in response to the user input in different work modes by the electronic device.
Moreover, currently, the big screen display system is consisted of multiple display units and image controllers in the current multi-screen splicing technology, and is generally used for an ultra screen display for one picture, and for multi-window display for multiple pictures.
It has drawbacks in that the splicing of the screens is fixed and cannot change with time; all the input signals needs to be processed by the image controller to be allocated to output to each screen display unit, and additional image controllers are needed.
Therefore, this kind of big screen splicing technology is not suitable for the screen splicing of Hybrid system consisted of separate devices, such as a hybrid system formed of multiple mobile phones.
In addition, in the prior art, for the hybrid system formed of separate devices, once the separate devices are spliced, their display mode is correspondingly fixed. Usually there is only one display mode, which is not suitable for display in different modes according to different properties of the display content.

Electronic device and information processing method thereof


A keyboard device includes a keyboard module and an illumination module. The keyboard module includes plural first keys and at least one second key. The illumination module includes a light guide plate and a circuit board. The light guide plate includes plural first mapping zones and a second mapping zone. The first mapping zones are located under the corresponding first keys. The second mapping zone is located under the second key. Moreover, at least one side-view light-emitting element and at least one top-view light-emitting element are installed on the circuit board. The side-view light-emitting element emits a first light beam. The top-view light-emitting element emits a second light beam. The first light beam is extracted through the corresponding first mapping zone and transferred to the corresponding first key. The second light beam is transferred to the second key.

Conventionally, a luminous keyboard device is equipped with a whole-piece light guide plate. The cooperation of the light guide plate and a side-view light-emitting element (e.g., a side-view LED) provides light beams to the keys. Since this backlight mechanism is unable to produce a color cycling effect, a wave spectrum effect, a breathing effect or a dynamic lighting effect, the function and commercial value of the keyboard device are not satisfied.
For meeting the requirement of the luminous keyboard board in the market, the luminous keyboard board needs to produce the multi-zone lighting effect. Moreover, it is necessary for some special keys to be individually illuminated.

Keyboard device capable of producing multi-zone lighting effect and illumination module thereof


A multi-component frame includes a first component made from a rigid structural material and a second component connected to at least an end portion the first component. The first component is constructed from a metal or metal alloy, and the second component is constructed from a material different from the first component. The first and second components form at least part of a length of the multi-component frame.

Orthopedic devices or braces comprise a broad range of structures and devices used for supporting or stabilizing a joint when worn on the body of a user. Orthopedic braces may serve in either preventive or remedial roles. In the preventive role, the orthopedic brace can provide additional support, stability, and protection to a healthy joint to prevent or minimize injury to the joint due to undue stress. In the remedial role, the orthopedic brace can support and strengthen a joint weakened due to injury or infirmity, and reinforce the vulnerable joint to prevent further injury, to correct or assist the infirmity, or to facilitate healing of the joint.
A predominant orthopedic brace is a knee brace, which is used to stabilize the knee by preventing excessive movement of the knee or facilitate the motion of the knee. Many knee braces comprise a frame and have hinges on at least one of the lateral and medial sides of the knee joint. Straps are used to secure the brace to the leg or knee. An injured knee can be fit with an "off-the-shelf" brace or with a "custom-fit" brace, with the selection of the brace depending on the size and shape of an individual's leg. A clinician may further form either type of braces by providing the frame with malleable materials to customize the frame to the user.
As shown in FIG. 1, an exemplary knee brace 10 typically includes a frame that comprises at least one support member 12, 14. When there are multiple support members 12, 14, the knee brace 10 may include rotational hinges 16 that assist and control the movement of the limb. Suitable straps 20 depend from strap attachments 22 and may maintain the knee brace 10 on the limb, and other features such as pads 18 may relieve the pressure of the knee brace 10 on the limb and surrounding areas.
Many knee braces reduce knee instability following an injury, counteract fatigue, and treat the impairment of the knee, particularly if the knee has damaged ligaments. Braces may be recommended for walking, skiing, running, twisting, pivoting, or jumping activities. Besides providing increased stability to the knee, knee braces may also decrease the risk of injuring the knee or leg or may assist the knee. One way of protecting the knee is by including attachments such as a patella-protector assembly which may be secured onto the knee brace and configured to operate to protect the patella from impact during physical activities.
To maximize its supportive, protective, and comfort-related aspects, it is desirable that a knee brace securely and precisely fit the leg of the user. While custom-fit braces are made to intimately conform to the precise geometry and dimensions of a leg of a user, it is typical for the geometry and dimensions of the leg to change over time due to weight change, muscle change, inflammation, medical conditions, or other factors, requiring even a custom-fit brace to accommodate many geometries of the leg. As for off-the-shelf braces, these braces must be configurable to generally suit many leg geometries despite the geometry of a particular leg. There is a need for braces that accommodate a user's dynamic dimensions.
Existing braces further fail to account for the geometrical and dimensional variations between different parts of a leg, e.g., the difference in shape between the calf and the shin. Certain areas of the leg require more accommodation from the brace than others, but most braces have only flat frame components and thus fail to address this need.
In recognizing the need for effective knee braces, various knee braces have been introduced into the marketplace. Such knee braces, however, have generally comprised relatively heavy, bulky apparatuses that fail to provide ventilation and to evenly distribute pressure from the brace on the leg of the user. Many contemporary braces are deficient because the braces are constructed in a manner that lacks or does not consistently provide adjustment features for forming a firm, comfortable, and secure interface between the unique and dynamic dimensions of the leg and knee of the user and the brace. Because of these drawbacks, many knee braces detract from the user's endeavor.
For example, some strap supports may be deficient because they add to the brace's bulk by jutting out from the frame with a rigid strap support structure. These features may cause discomfort for a user, increasing the size, profile, and weight of the brace, increasing the cost to a user and making the brace cumbersome to use because of the brace's larger size. Such straps may further increase the risk of damage to the brace and discomfort for a user if, for example, the outwardly jutting straps catch on objects or clothing.
Braces may need to incorporate auxiliary structures such as sensors, padding, structural support, or aesthetic features into the frame. Existing braces, which utilize flat metal structures, do not have a convenient disposition for such auxiliary structures and thus the auxiliary structures must attach or append to the brace, often in uncomfortable, unsightly, and maintenance-intensive ways. This further increases the bulk of the brace.
The features of the present disclosure are provided in recognition of the need for orthopedic braces and components in both custom-fit and off-the-shelf braces to achieve superior functional performance characteristics while being comfortable to the user when worn and adapting to the user's dynamic dimensions. This recognition is realized with the embodiments described in the disclosure.

Multi-component frame for use in an orthopedic device


A sample analyzer capable of operating in a first measuring mode for measuring a sample and a second measuring mode for measuring a sample, comprising: a sample provider for providing a sample; a common reagent provider for providing a common reagent used in the first measuring mode and the second measuring mode; a special reagent provider for providing a special reagent used in the second measuring mode; a mode selector for selecting one of the first measuring mode and the second measuring mode; a measuring section for measuring the sample; and wherein in the first measuring mode, the sample provider and the common reagent provider operate so as to make a first mode sample comprising the sample and the common reagent, and the measuring section operates so as to measure the first mode sample, and in the second measuring mode, the sample provider, the common reagent provider and the special reagent provider operate so as to make a second mode sample comprising the sample, the common reagent and the special reagent, and the measuring section operates so as to measure the second mode sample, is disclosed. A sample analyzing method is also disclosed.

Red blood cells, platelets, and white blood cells are suspended in the plasma of peripheral blood. Specimens are frequently examined since a great deal of clinical information can be obtained by blood analyses that examine these cells.
Basic items in blood examinations include measurement of the number of red blood cells, number of platelets, number of white blood cells, and hemoglobin concentration in the blood, and a hematocrit value is determined from these measurement results. The measurement of these values is generally referred to as CBC (complete blood count), and hemocytometers are widely used to determine CBC.
Hemocytometers allocate a blood sample into a plurality of aliquots. For example, a first aliquot may be diluted with a dilution liquid and used to measure the red blood cell count and platelet count. A second aliquot may be added with a hemolytic agent to hemolyze the red blood cells and used to measure white blood cells. A third aliquot may be used to measure hemoglobin concentration by adding a hemolytic agent to release the hemoglobin in the red blood cells. A hemocytometer performs these measurements and determines the hematocrit value.
The measurement of a white blood cell count is added to a white blood cell classification examination in order to provide clinical information more sophisticated than CBC, and the white blood cell classification examinations are widely performed to classify white blood cells as lymphocytes, monocytes, neutrophils, eosinophils, and basophils.
White blood cell classification methods classify white blood cells based on optical signals or electrical signals of scattered light, fluorescent light and so on, or combinations thereof, using stains to stain particles and hemolytic agents capable of preserving the cellular morphology of the white blood cell.
An example of a hemocytometer capable of white blood cell classification is the model XE-2100 manufactured by Sysmex Corporation.
The XE-2100 allocates a blood sample into a blood for measurement of a red blood cell count and platelet count, blood for measurement of hemoglobin concentration, and blood for measurement of white blood cell. The XE-2100 further allocates the blood for measurement of white blood cell into two aliquots; a WBC count reagent is added to one aliquot and the number of white blood cells and number of basophils are counted, and a WBC classifying reagent is added to the other aliquot and the white blood cells are classified into four classification types, and both of these measurement results are used as the basis for the white blood cell count and the white blood cell classifications.
The XE-2100 is configured so as to be capable of operating in a first mode that measures the white blood cell count, but does not classify the white blood cells, and a second mode that measure the white blood cell count and classifies the white blood cells. The XE-2100 requires two aliquots to measure the white blood cell count and perform the white blood cell classification in the second mode. Furthermore, since white blood cell classification is generally performed less frequently than measurement of the white blood cell count, the special reagent required for white blood cell classification in conventional hemocytometers is wasted when the white blood cell classification reagent use period expires.
U.S. Pat. No. 5,656,499 also discloses another hemocytometer. This hemocytometer has a plurality of mixing chambers for preparing mixed preparations corresponding to a plurality of aliquots. A first aliquot is subjected to hemolytic processing and thereafter scattered light from the cells is detected at multiple angles using an optical flow cell/transducer to measure the number of white blood cells and perform white blood cell classification. A second aliquot is subjected to dilution processing and thereafter the change in impedance when the cells pass through an orifice is detected by an impedance transducer to measure the red blood cell count and platelet count. A third aliquot is subjected to hemolytic processing and thereafter the light optical density of the hemolytic sample is detected by an HGB (hemoglobin) transducer to measure the HGB concentration.

Sample analyzer and sample analyzing method


To provide a system capable of evaluating a deficiency and/or a lowered function of extrinsic coagulation factors or intrinsic coagulation factors with high sensitivity by adding new procedures and apparatuses to a blood coagulation system analysis procedure, an apparatus, or the like.

Thrombus formation (coagulation) and dissolution (fibrinolysis) in vivo proceed in a complex cascade reaction. The reaction is associated with both of a number of molecular components including coagulation factors, fibrinogen, fibrin, and the like and cell components such as vascular endothelial cells, platelets, and the like.
In treatment or prevention of coagulation- and fibrinolysis-related disease and injury, a variety of tests are performed to determine a blood coagulation ability and a fibrinolysis ability of a patient. The coagulation and fibrinolysis tests can be roughly classified into a quantitative test that measures amounts of specific molecules involved in a coagulation and fibrinolysis reaction system such as a variety of coagulation factors, fibrinogen, and D-dimers, and a functional test that evaluates a functional level of an entire reaction system or a part thereof.
The coagulation reaction system is separated into a mechanism (extrinsic system) that starts with complex formation of a tissue factor and an activated coagulation VII factor and a mechanism (intrinsic system) that starts with activation of a XII factor owing to a contact with a foreign matter or the like. The both merge at a stage of activation of an X factor.
Note that, in accordance with practices of a thrombus hemostasis field, the coagulation factor is expressed by adding "F" to the top of the Roman number of the factor number and, if the factor is activated, by adding "a" to the end. For example, a XII factor and an activated VII factor are expressed as FXII and FVIIa, respectively.
The generated FXa activates prothrombin (FII) and converts it into thrombin (FIIa). By an action of thrombin, fibrinogen is converted into fibrin. The generated fibrin is polymerized each other and forms a three-dimensional network structure called insoluble stable fibrin by a further action of FXIIIa. A thrombus (blood clot) is a structure formed of the network structure into which red blood cells are mainly entangled. Also, platelets contribute to the structure formation. Once the thrombus is formed, a fibrinolysis reaction system begins to work in order to prevent solidification from excessively accelerating. The thrombus finished to serve as hemostasis is dissolved eventually.
As function tests of an extrinsic coagulation ability and an intrinsic coagulation ability, a prothrombin time (PT) and an activated partial thromboplastin time (APTT) are widely used. In these tests, substances (e.g., a tissue factor and ellagic acid) that elicit extrinsic and intrinsic coagulation reactions are extra-excessively added, so that test results are obtained in a short time. Normal values of a prothrombin time and an activated partial thromboplastin time are each approximately 10 seconds and 30-40 seconds. Accordingly, these tests are suitable to evaluate a significant decrease of a coagulation ability, i.e. a bleeding tendency, but are unsuitable to evaluate a significant increase of the coagulation ability, i.e., a thrombus tendency or a subtle change of the coagulation ability. In addition, the test is performed by using plasma obtained by centrifuging blood samples. Because cell components such as platelets and red blood cells that play important roles in the coagulation reaction in vivo are removed by centrifugation, the test result is often inconsistent with an actual clinical condition.
As another function tests, there are thromboelastography and thromboelastograph cytometry. Specifically, a TEG 5000 (registered trademark, Hemonetics Corporation) and a ROTEM delta (registered trademark, Tim Innovations) are practically used.
In the TEG 5000, whole blood samples are injected into a measurement container, a cup, eliciting substances to serve the test purpose are added, a rod-like pin hanging by wire from a top of a container is immersed, and a steady reciprocating angular motion (typically back and forth motion in a 4.45 degrees range for 10 seconds) is applied to the container. As the coagulation reaction proceeds, viscoelasticity of the samples is increased, the relative motion of the cup and the pin is decreased, and a rotational displacement of the pin is thus increased. The rotational displacement is recorded over time by using an optical system of an apparatus. As a result, the waveform called thromboelastogram is obtained. Although there is a difference that the reciprocating angular motion is given not to the cup but to the pin, the ROTEM delta is also basically based on the same principle. Whereas the prothrombin time and the activated partial thromboplastin time are coagulation end point detection methods, the thromboelastography or the thromboelastography cytometry can advantageously monitor over time a series of processes from solidification starting to thrombus formation and subsequent fibrinolysis by one apparatus.
It can be said that the thromboelastography or the thromboelastography cytometry comprehensively tests work of the entire reaction system until fibrin generation by focusing on the fibrin generation that is the final stage of the coagulation cascade reaction and by monitoring the processes of the network formation (coagulation) and the dissolution (fibrinolysis) through the viscoelasticity of the samples.
However, the thromboelastography or the thromboelastometry has problems in that they are insufficiently popular mainly because: (1) measurement is not automated and the test result depends on the technique of a measuring person, (2) it is sensitive to vibration, (3) a quality control (QC) procedure is complicated and a QC reagent is expensive, (4) interpreting an output signal (thromboelastogram) needs skills, and the like. Furthermore, since they do not show very high sensitivity to a deficiency of extrinsic or intrinsic coagulation factors, it may not satisfy the medical field's needs.
On the other hand, in recent years, as a method capable of evaluating blood coagulation measurement easily and accurately, a method for performing dielectric measurement of a blood coagulation process has been devised (Patent Documents 1 and 2). The method is to fill blood into a capacitor-like sampling unit including a pair of electrodes and the like, apply an alternating electric field thereto, and measure a change in a dielectric constant caused by the coagulation process of blood. By using the method, it is shown that coagulation and fibrinolysis reaction processes can be easily monitored (Non-Patent Literature 1).

Blood coagulation system analysis system, blood coagulation system analysis method, and blood coagulation system analysis program

Abstract: A blood coagulation system analysis system includes a blood coagulation system measurement apparatus that performs blood coagulation system measurement of a blood sample; and a blood coagulation system analysis apparatus including a coagulation parameter extraction unit that extracts a coagulation parameter from a measurement result by the blood coagulation system measurement apparatus, and a blood coagulation evaluation unit that evaluates a level of blood coagulation of the blood sample on the basis of the coagulation parameter, the measurement by the blood coagulation system measurement apparatus being performed under an extrinsic system acceleration condition and an intrinsic system acceleration condition.