An apparatus and a method for monitoring and/or analysis of electrical machines during operation, wherein the electrical machine has at least one generator with a shaft and drive means for driving this shaft, wherein the shaft is grounded at the first end of the generator, and wherein a measurement unit for measurement of shaft voltage and/or shaft current as a function of time is provided on the shaft at the second end of the generator. An apparatus such as this allows the combined and simultaneous measurement of various fault states by supplying signals for the shaft voltage and/or the shaft current to an analysis unit, wherein the analysis unit allows combined and simultaneous analysis of at least two potential fault states of the electrical machine. Simultaneous cross-relationships between the individual measurement results of individual fault states may be provided so as to allow a clearer and more reliable diagnosis of critical states, not possible when individual phenomena are considered separately.

Electrical machines, in particular large electrical machines such as those used in power station installations, should be monitored continuously and/or should be analyzed from time to time in order to ensure smooth operation, in order to identify fault states in good time, and in order to avoid uncontrolled failures.
There are various methods and apparatuses for this purpose for a large number of possible fault states, and these will be described briefly.
For example, U.S. Pat. No. 5,006,769 describes an apparatus for detection of turns shorts in the rotor winding of generators. In this case, the shaft voltage is measured via a specific grounding module, and is analyzed in a specific manner by means of Fourier transformation.
For its part, EP 0271678 proposes an apparatus which allows statements to be made about the suitability for use and the functional reliability of the shaft grounding and the insulation of the shaft. The apparatus proposed in this case, which is actually intended to reduce shaft voltages, allows statements to be made about the overall grounding conditions in the electrical machine.
DE 19742622 describes an apparatus which allows the identification of spark erosion on the shaft, (particularly in the bearings), as can occur when high voltages are present and which is generally associated with damaging effects, when measuring the shaft current and shaft voltage on the shaft.
A large number of documents describe apparatuses which are used for detection of brush sparking on the sliprings. These include, for example, U.S. Pat. No. 3,653,019, U.S. Pat. No. 4,058,804, U.S. Pat. No. 4,163,227 and U.S. Pat. No. 4,451,786. In this case, a measurement apparatus which must be provided specifically for this purpose is connected directly to the brushes and, and this is the major aspect of these documents, data processing is then carried out which makes it possible to distinguish between interference signals and useful signals. This is done primarily using the gating method in which interference signals are identified and the detection process is interrupted during the interference signals (blanking). Another method for detection of brush sparking is proposed in U.S. Pat. No. 4,577,151, in which a characteristic signal is detected via an antenna which must be provided specifically for this purpose, and is then supplied to an analysis unit. For this purpose, the antenna must be arranged in the vicinity of the sliprings in order to receive the corresponding radio-frequency signals. The signals are then amplified and demodulated in a specific analysis unit, and are then supplied to a detector.
One method for identification of a further fault state is described in U.S. Pat. No. 4,814,699. This relates to the detection of partial discharges in the stator, rotor and in the excitation apparatus. In this case, the shaft is used as an antenna and the radio-frequency pulses are output via one of the (insulated) shaft bearings or via a coupling coil which must be provided specifically for this purpose. The shaft bearings must for this purpose be electrically insulated from ground and must also be designed so as to make it possible to distinguish between interference signals in this specific signal and useful signals.
A further serious fault state which must likewise be monitored is oscillations in the shaft run of the machine, in particular in a turbogenerator run. These oscillations may be of a different nature. They may be bending oscillations or transverse vibration occurring in the direction at right angles to the shaft. Furthermore, so-called hunting may occur, that is to say quasi-periodically-damped changes in the rotation frequency of the shaft above the mains frequency of normally 50 Hz (or 60 Hz) and which are produced by, for example, sudden disturbances in the mains. The actual torsional oscillations which can be produced, for example, by sudden load increases on the mains are recognized as a third type of shaft oscillation. In this case, torsional oscillations are oscillations which manifest themselves in a non-standard rotational frequency along the shaft (phase shifts or frequency shifts), that is to say they produce torsion on the shaft.
Torsional oscillations are very small oscillations, normally in the region of 0.01 degrees phase amplitude, but which nevertheless can lead to a very major load on the shaft and, in particular, coincidence between the natural frequency of such a torsional oscillation and the stimulus exciting it can lead to dangerous resonant increases in such torsional oscillations, which can even result in the shaft fracturing. Torsional oscillations may in this case be at frequencies from a few Hz up to 200 Hz, with the frequency naturally depending on the material characteristic and thickness of the shaft, the masses which are connected to the shaft and the size of the installation. These torsional oscillations can become extremely critical, particularly in large installations with long shafts.
Owing to the importance of this problem, a large number of patent specifications have also already dealt with oscillations such as these. For example, U.S. Pat. No. 3,934,459 describes test equipment and a method for measurement of the torsional oscillations of the entire shaft run of a turbine/generator system. The torsional oscillations are recorded at one or more points on the shaft for this purpose by means of one or more sensors which are not specified in any more detail but must be provided specifically for this purpose. The further processing of the torsional signals is the main subject of this document. The further processing is carried out by filtering using bandpass filters and by means of multiplication operations in order, at the end, to determine the maximum torsional torques.
U.S. Pat. No. 3,885,420, U.S. Pat. No. 4,148,222, U.S. Pat. No. 4,137,780 and U.S. Pat. No. 4,317,371 should also be cited with reference to oscillations, all of which describe test equipment and/or methods for measurement of torsional oscillations in electrical installations such as these. Toothed wheels which are connected to the shaft and must be provided specifically for this purpose are used as signal transmitters for detection of the torsional oscillations, and produce electrical signals by means of sensors. The signals are processed further by means of bandpass filters and multiples, etc. U.S. Pat. No. 4,317,371 describes one specific demodulation method for measurement of phase shifts. The method comprises the production of relatively low intermediate frequencies followed by frequency demodulation, as is known per se from radio engineering. Another method (U.S. Pat. No. 3,885,420) uses a PPL (phase locked loop) for demodulation. U.S. Pat. No. 4,444,064 is also cited, which describes a method in which, first of all, a magnetic pattern must be additionally applied to the shaft, and is then used as a pulse transmitter. Another concept for measurement of torsional oscillations is based on using the voltage at the phase winding terminals of the generator (which uses permanent magnet excitation and is coupled to the shaft) in order to determine such oscillations. The torsional oscillations are deduced by evaluation of the voltages that are produced and are tapped off by means of appropriate terminals. The evaluation process is once again carried out by means of frequency demodulation (PPL technique). This arrangement has the advantage that its costs are lower than those of the toothed wheel solution.
Further fault states which may possibly occur and which should also be mentioned include, for example, defective insulation on the rotor winding as well as rotationally synchronous shattering marks and/or witness marks which should likewise be detected in order to prevent failures.

Apparatus and method for monitoring and/or analysis of electrical machines during operation


A liquid crystal display device includes a liquid crystal panel; a backlight unit to provide a light to the liquid crystal panel, the backlight unit includes an optical sheet and a light guide plate; and a main support to receive the liquid crystal panel and the backlight unit together, the main support having first and second movement preventing members to prevent shifting of the optical sheet and the light guide plate of the backlight unit in a direction on a plane, and a third movement preventing member to prevent shifting of the light guide plate of the backlight unit in a direction normal to the plane.

1. Field of the Invention
The present invention relates to a liquid crystal display device, and more particularly, to a liquid crystal display device and method of assembling the same that enhances the device assembly process and decreases the manufacturing costs by forming an integral main support.
2. Discussion of the Related Art
A cathode ray tube (CRT) has been widely accepted as an information display device and includes advantages, such as a good display performance and a low unit price. However, the CRT also has disadvantages, such as poor portability due to its bulky size and heavy weight. Accordingly, various types of liquid crystal display (LCD) devices were developed in recent years. The LCD devices include features that can overcome the disadvantages of the CRT, for example, increased portability due to light weight and slim size, and low power consumption. These features are implemented in most LCD devices and are replacing the CRT rapidly.
FIG. 1 is a perspective view of a related art LCD device, and FIG. 2 is a partial sectional view of the related art LCD device. As shown in FIGS. 1 and 2, the related art LCD device includes a liquid crystal panel 3 displaying an image, a backlight unit 20 illuminating a plane light onto the liquid crystal panel 3, a lower cover 9 receiving the backlight unit 20, a panel guide 5 securing the liquid crystal panel 3 in place, and a top case 1 coupled to the lower cover 9.
As shown in FIG. 2, the liquid crystal panel 3 includes a thin film transistor (TFT) substrate 3b on which a pixel electrode and a TFT are formed, and a color filter substrate 3a on which a color filter layer is formed. The TFT substrate 3b and the color filter substrate 3a are attached with a liquid crystal layer (not shown) interposed therebetween. An upper polarizing plate 11a and a lower polarizing plate 11b are respectively attached on outer surfaces of the liquid crystal panel 3.
The backlight unit 20 includes a light guide plate 15, a lamp 13, optical sheets 21 and a reflection sheet 18 provided inside the lower cover 9. In the related art LCD device having the above described structure, a folded edge of the reflection sheet 18 secures the lamp 13 in place. The lamp 13 can be disposed around all four sides of the liquid crystal panel 3 or only at two sides of the panel. Light generated from the lamp 13 is incident on a sidewall of the light guide plate 15. The incident light is converted into a plane light source, and then supplied to the liquid crystal panel 3.
After the liquid crystal panel 3 is assembled with the backlight unit 20, a top case 1 is coupled to cover the liquid crystal panel 3. In FIG. 2, reference numeral 17 indicates a support pad supporting the top case 1. However, the related art LCD device is required to use an independently manufactured panel guide 5 in order to assemble the liquid crystal panel 3 after the backlight unit 20 is sequentially received inside the lower cover 9. Accordingly, the assembly processes become complicated. In addition, the panel guide 5 contributes to achieving the slim size of the LCD device, thus the panel guide 5 needs to be manufactured as an independent component. Hence, the manufacturing cost of the LCD device increases.

Liquid crystal display device having members for preventing shifting of the light guide plate and method of assembling the same


A connector mounted on a board having a plurality of board signal lines for transmitting a signal and a board ground line grounded. Each of the plurality of board signal lines includes a plurality of signal terminals formed in correspondence to each of the signal lines. Each of the signal terminals comprises: a signal core line formed of conductor by extension in the shape of a line; a shield for core line formed of conductor insulated from the signal core line electrically so as to extend in an axis direction of the signal core line and enclose the signal core line; a signal electrode formed by extension from the signal core line for connecting the signal core line with the board signal line corresponding to the signal terminal; and a plurality of ground electrodes extended from the shield for core line and opposed to each other by intervention of the signal electrode for connecting the shield for core line with the board ground line respectively.

The present application claims priority from a Japanese Patent Application No. 2003-151536 filed on May 28, 2003, the contents of which is incorporated herein by reference.
1. Field of the Invention
The present invention relates to a connector holding a plurality of signal terminals and ground terminals.
2. Description of the Related Art
When an electronic device under test is tested in semiconductor testing apparatus etc., a signal is exchanged, for example by way of test heads that intervene between tester control units generating the signal which is necessary for a test and the electronic device.
With high performance of an electronic device of recent years, a test of an electronic device has been advanced. For this reason, in a transmission line relaying a signal, deterioration of a signal or mixture of a noise from circumferences may impede a test of the electronic device.


A method for operating a power factor correction circuit is provided which may include the steps of providing a plurality of N switched-mode converter circuits each comprising an nth inductor, where N is at least 2, starting a switching pulse for the nth switched-mode converter circuit when the following conditions are fulfilled: the nth inductor of the nth switched-mode converter circuit has a predefined magnetization state; and a predefined time period has elapsed since the start of a switching pulse for an mth switched-mode converter circuit, where m=n−1 in case n>1 and m=N in case n=1. The predefined time period is a predefined fraction of the time period from the start of a previous switching pulse for the nth switched-mode converter circuit to a time when the nth inductor of the nth switched-mode converter circuit has the predefined magnetization state.

Circuits for power factor correction (hereinafter PFC) nowadays play an important role in current and/or voltage converters. For small to middle power ranges, e.g. 25 W to 150 W, power factor correctors working with currents of triangular shape are commonly used, wherein in each switching cycle a magnetic energy stored in an inductor is completely released and a new switching cycle is initiated immediately after the magnetic energy is completely released which can be detected via an auxiliary coil of the inductor. The advantage of power factor correctors relying on triangular currents is a relatively slow rate of current change in a rectifier which makes it possible to use inexpensive rectifying diodes. However, the drawbacks involved are the variable operation frequency and a high ripple of the input current. The latter issue can be resolved by using a power factor corrector working with currents of trapezoidal shape which is mostly used for power ranges between 150 W and 500 W. The operating frequency is usually fixed and is set by a clock generator. A major disadvantage of the use of a power factor corrector working with currents of trapezoidal shape is the need to use a relatively expensive fast rectifying diode.
To achieve even higher power ranges, multiphase power factor correctors working with currents of trapezoidal shape are used, where a multiphase clock generator provides the separate power factor correction stages with phase shifted clock signals which are phase shifted by 360°/N with respect to one another, wherein N denotes the number of power factor correction stages which is also equivalent to the number of different phases.
Over the past, multiphase power factor correctors working with currents of triangular shape have become increasingly attractive and partly replace single phase power factor correctors working with currents of trapezoidal shape in some applications in the range starting from 150 W. The multiphase power factor correctors working with currents of triangular shape offer several advantages over single phase power factor correctors working with currents of trapezoidal shape. The switching losses are considerably lower, which for example allows for a higher operating frequency and in turn may result in smaller magnetic components or a higher efficiency. As the magnetic components may have a decreased height, the overall circuitry can be constructed in a more compact fashion and hence their integration into flat screens, for example, may be simplified.
In case of an interleaved PFC circuit which includes more than one PFC stage working with currents of triangular shape, the synchronisation of PFC stages with respect to one another is a non-trivial task to be solved, since each PFC stage is a self-oscillating system which operates independent of a cycle generator.
In a conventional method to synchronise multiphase power factor correctors working with currents of triangular shape, two power factor correctors working with currents of triangular shape are operated independent of one another. Signals for setting the duration of the on-time of each power factor corrector stage are modulated depending on an averaged phase shift between the signals, such that by means of a phase control the power factor corrector stages reach a state of running out of phase. In another approach, a signal of a zero crossing detector of one of the two power factor corrector stages is delayed depending on an averaged phase difference between the two power factor corrector stages.

This patent is subject to a terminal disclaimer.

Method for operating a power factor correction circuit


A method for manufacturing a carbon nanotube assembly including the steps of: forming metallic fine particles, having a predetermined particle diameter, on a substrate; heating the metallic fine particles to a predetermined temperature of 300° C. to 400° C. in a reducing atmosphere to cause reduction at surfaces thereof; heating the metallic fine particles to a predetermined reaction temperature in a reactor; and introducing an organic compound vapor into the reactor to grow carbon nanotubes on the metallic fine particles in such a way that a time during which the temperature of the metallic fine particles exceeds 450° C. is 600 seconds or fewer for the period of time before the growth of the carbon nanotubes is started after the heating of the metallic fine particles is started.

A carbon nanotube is a kind of fibrous carbon having a structure where graphene sheets are layered in an annual growth ring shape, and is a nanocarbon fiber having an extremely high aspect ratio where its diameter is 0.43 nm to several tens of nanometers, while its length reaches normally 100 nm to several hundreds of micrometers. The graphene sheet mentioned here indicates a layer where a carbon atom having an sp2 hybridized orbital, which forms a crystal of graphite, is located at the apex of each hexagon.
A carbon nanotube formed of one graphene sheet is called a single-walled carbon nanotube (hereinafter abbreviated as SWCNT). A carbon nanotube formed of two graphene sheets is called a double-walled carbon nanotube (hereinafter abbreviated as DWCNT). A carbon nanotube formed of three graphene sheets is called a triple-walled carbon nanotube (hereinafter abbreviated as 3WCNT). A carbon nanotube formed of four graphene sheets is called a quad-walled carbon nanotube (hereinafter abbreviated as 4WCNT). A carbon nanotube formed of five graphene sheets is called quint-walled carbon nanotube (hereinafter abbreviated as 5WCNT). A carbon nanotube formed of six or more graphene sheets is often called, in sum, multi-walled carbon nanotube (hereinafter abbreviated as MWCNT). Hereinafter, for indicating the plural number of the carbon nanotube, it is expressed by adding "s" meaning the plural number as in SWCNTs.
On a cylindrical surface of the graphene sheet, a formation is shown in which a hexagonal mesh that is formed by carbon atoms is rolled up in a spiral form and the spiral state is called chirality. It is known that various kinds of physical properties of the carbon nanotube differ in response to the number of graphene sheet layers, diameter of tube, and chirality.
A carbon nanotube manufacturing method uses a CVD method using organic compound vapor as a raw material, an arc discharge method using a graphite electrode, a laser evaporation method, a liquid phase synthesis method, etc.
For example, in Nikolaev P and other six writers, "Gas-phase catalytic growth of single-walled carbon nanotubes from carbon monoxide," Chemical Physics Letters, vol. 313, pp. 91-97, 1999 (Document 1), there is described a method for manufacturing SWCNTs by disproportionation of carbon monoxide under a high pressure using iron particles as a catalyst, and only SWCNTs can be selectively manufactured according to this method.
Furthermore, in S. Maruyama and other six writers, "Growth of vertically aligned single-walled carbon nanotube films on quartz substrates and their optical anisotropy," Chemical Physics Letters, vol. 385, pp. 298-303, 2004 (Document 2), there is disclosed method for selectively forming only SWCNTs on a substrate by a CVD method using ethanol as a raw material.
On the other hand, as a method for manufacturing DWCNTs, in Hisanori Shinohara and other six writers, "Synthesis of high purity double wall carbon nanotubes by the CCVD method using zeolites," Conference Abstract Book of 26th Fullerene Nanotubes General Symposium, Fullerene and Nanotubes Research Society, p. 100, Jan. 7, 2004 (Document 3), there is disclosed a method for manufacturing a carbon nanotube mixture containing 50% to 60% DWCNTs by a CVD method using metallic fine particles as a catalyst carried in zeolites and using an alcohol as a raw material.
Additionally, as means for checking the number of graphene sheet layers of the carbon nanotubes which those skilled in the art normally use, there is generally used a method in which individual carbon nanotubes are observed by a transmission electron microscope to count, on observation images, the number of images of graphene sheet layers which appear on a wall surface of the carbon nanotube. Means for estimating a proportion of a carbon nanotube having a predetermined number of layers to an assembly of numerous carbon nanotubes is as follows. Specifically, the assembly is observed by the transmission electron microscope. Then, the number of layers of each of the numerous carbon nanotubes extracted at random is determined. The proportion is estimated as the number of carbon nanotubes having a predetermined number of layers with respect to the total number of carbon nanotubes thus extracted.

Carbon nanotube assembly and manufacturing method thereof


Methods for diagnosing glaucoma and for screening therapeutic agents for their usefulness in treating glaucoma are disclosed.

1. Field of the Invention
The present invention relates to the field of glaucoma diagnosis and treatment. More specifically, the present invention provides methods for diagnosis of glaucoma by measuring the amount of GRβ present in the trabecular meshwork of a patient's eye.
2. Description of the Related Art
Glaucoma is usually diagnosed by monitoring a patient's visual field loss, changes in the appearance of their optic disc, and their intraocular pressure. Glaucoma is currently treated using one or more of three strategies to lower the elevated intraocular pressure associated with the disease: with pharmaceuticals (such as beta-blockers, carbonic anhydrase inhibitors, miotics or prostaglandins), with laser trabeculoplasty, and/or with glaucoma filtration surgery. All of these therapies indirectly lower intraocular pressure but do not address the underlying disease process occurring in the trabecular meshwork. It would be advantageous to be able to diagnose glaucoma before a patient begins experiencing a loss in their visual field and deterioration of their optic disc.
There is a large body of evidence suggesting that glucocorticoids are involved in the generation of ocular hypertension and glaucoma (Clark 1995). The human glucocorticoid receptor (hGR) and its isoforms, hGRα (SEQ ID NO:3) and hGRβ (SEQ ID NO:1), are described in Encio and Detera-Wadleigh (1991) (See also FIG. 1). Several investigators have shown that the human trabecular meshwork (TM) contains the classical glucocorticoid receptor (hGRα) (Weinreb et al. 1981; Hernandez et al. 1983). Recently, the expression of an alternatively spliced form of the human glucocorticoid receptor (hGRβ) was discovered in non-ocular tissues and cells (Bamberger et al. 1995; Oakley et al. 1996). This alternatively spliced form of hGR is expressed as a protein (SEQ ID NO:2) which no longer binds glucocorticoids, but is able to interfere with the activated form of the normal glucocorticoid receptor and block or alter physiological functions of the glucocorticoid receptor.

Methods for diagnosing glaucoma and discovering anti-glaucoma drugs

University of North Texas Health Science Center


An ink jet printing apparatus for industrial use, which is provided with a comparatively large number of nozzles arranged for high duty recording, particularly an ink jet textile printing apparatus, and an ink jet printing apparatus suitably used for printing on a large-sized medium, are provided together with a method for controlling the temperature of the printing head of such high duty printing apparatuses, and various other types of printing apparatuses reliably. To the large number of heaters used for recording in a printing step, driving signals are applied to cause them to discharge ink for recording and, to the discharge heaters that are not to perform recording, secondary driving signals that do not allow ink to discharge are applied. These secondary driving signals cause the heaters not used in recording to generate heat, so as to reduce unevenness in the intensities of heat generation among the many discharge heaters of the printing head. At the same time, cooling water is supplied by a cooling device to a cooling liquid path arranged for the printing head in order to cool it.

1. Field of the Invention
The present invention relates to a printing apparatus to form images in accordance with image signals or image information obtainable from images on source documents. Specifically, the invention relates to a printing apparatus to which an ink jet recording method, thermal transfer method, or other recording methods are applicable. More particularly, it relates to a printing apparatus using an ink jet recording method capable of recording in high recording duties with the provision of many numbers of discharge nozzles.
Printing apparatuses of the present invention are those applicable as a textile printing apparatus to print on fabrics, a printing apparatus adapted for industrial use, or the like.
2. Related Background Art
There has been known an ink jet recording method whereby to record by discharging ink from discharge ports onto a recording medium and cause it to adhere to the medium. This ink jet recording method is widely used for comparatively small print output apparatuses for personal use. In a printing apparatus using such ink jet recording method, the temperature of printing head changes depending on the history of printing operations and recording duties. Then, as the temperature changes, its recording density is caused to vary, leading to unevenness created in recorded images. Particularly when the printing operation is carried out continuously or a high duty recording is performed, the temperature rise of the recording head becomes intense, making it difficult even to discharge ink in some cases. Also, in a printing apparatus capable of recording in colors with the provision of printing heads arranged respectively for each of plural colors, unevenness is created in each color used for recording, hence causing the ratio of color mixture to be varied when forming an image by mixing plural colors. It is inevitable that the color appearance varies in an image thus printed.
On the other hand, in a printing apparatus having a smaller number of nozzles to discharge ink, which prints at a comparatively slow speed, the heat generation of the printing head is also comparatively small. For such printing apparatus, the following proposals have been made in anticipation of solving the problems related to the temperature rise of printing head:
1) In U.S. Pat. No. 4,910,528, a technique is disclosed to suppress the excessive rise of temperature by detecting the temperature of printing head, thus controlling its printing speed accordingly so that the temperature of the printing head is adjusted.
2) In Japanese Patent Publication No. 3-4394, a technique is disclosed to suspend printing operation when the temperature of printing head exceeds a given temperature, and then, to resume the printing operation after waiting for the temperature to drop.
3) In Japanese Patent Publication No. 61-17670 and Japanese Patent Publication No. 62-41114, a technique is disclosed to control printing speeds by grasping printing duties in advance in accordance with recording data so that the temperature of the printing head is kept at a constant level.
4) In Japanese Patent Laid-Open Application Nos. 1-127361, 3-43254, and 4-47948, a technique is disclosed to stabilize the temperature of printing head in such a manner that while applying printing signals in an intensity good enough to generate thermal energy to the heaters of ink discharge nozzles that discharge ink, signals are applied to the nozzles that do not discharge ink in an intensity just to generate thermal energy but not strong enough to cause ink to be discharged, and that the resultant heat generation is made constant for the printing head: here, the arrangement of such means is well balanced with the arrangement of natural cooling.
5) In U.S. Pat. No. 4,929,963, a technique is disclosed to implement the cooling of a printing head by circulating ink itself in the interior of the printing head.
6) In EP Patent No. 573,062, a technique is disclosed to provide a mechanism to cause cooling water to pass a thermal transfer printing head, thus forcibly cooling such head by use of the cooling water.
In each of the proposals described above, however, the following problems are encountered:
In the paragraphs 1) to 3) described above, the temperature of the printing head is prevented from rising by the utilization of natural radiation. Thus the temperature of the printing head is not controlled, to be exact. As a result, if the recording duty is high, the printing speed is reduced, and also, there is a fear that the recording densities vary. Should a technique of the kind be applied to an ink jet textile printer or an ink jet printer for industrial use, the temperature rises immediately because such printers are provided with a large number of nozzles, and the recording duty is high, resulting in an enormous amount of heat generation. Therefore, such printer tends to suspends its operation frequently in order to allow its printing head to be cooled. Also, in this case, even if the printing speed is reduced, it is impossible to avoid the temperature rise of the printing head because of an enormous number of nozzles to be used. In any case, a printer of the kind makes it difficult to effectuate a continuous operation. Also, it is difficult to suppress the variation of recording densities due to the frequent changes of temperature while executing the printing operation.
In the technique described in the above paragraph 4), it is arranged that in addition to the energy for discharging ink, energy for generating heat is given even when no ink is discharged in order to make the heat generation of the printing head constant, and then, on the assumption that the natural radiation is constant, an arrangement is made to make the heat generation of the printing head well balanced with the natural radiation. In this way, the temperature of the printing head is stabilized at a constant level.
With this arrangement, however, the total amount of heat generation of the printing head becomes enormous, resulting in a more intensive rise of temperature than that of the examples referred to in the above paragraphs 1) to 3). Thus, the continuous operation becomes more difficult. In order to perform the operation continuously, the nozzle numbers should be smaller, and also, the printing speed is made slower. In addition, the heat generation of the printing head should be smaller so as to be able to anticipate a sufficient natural radiation. Even under such conditions, the balancing point with the natural radiation varies as the inner temperature of the apparatus rises in operation. Further, the balancing point of the head temperature varies eventually as the outside temperature changes.
In the method described in the above paragraph 5), ink is circulated between the printing head and ink tank to cool the printing head. However, the method referred to in that paragraph does not provide any mechanism to adjust the temperature of ink. Therefore, the temperature of circulating ink rises without any control as a printing operation is carried on continuously, leading to the creation of a gradual variation of recording densities after all. Further, before this problem arises, if this method is adapted for a printing head provided with many numbers of nozzles for use of high duty recording, that is, if it is used for cooling a printing head that may generate an enormous heat generation, there is a need for executing the circulation of ink in an amount sufficient enough to effectuate the intended cooling. Then, due to the pressure exerted by such circulating ink, the menisci of ink in the nozzles are broken to allow ink to leak from the nozzles or air to enter the nozzles to mix with ink. In such a case, there is a fear that the printing function itself is even liable to malfunction.
The methods described in the above paragraphs 1) to 5) are all applicable to printing apparatuses having a smaller number of nozzles for the execution of low duty recording, that is, those of a small type for office use, for which it suffices to utilize the natural radiation appropriately, and the variation of recording densities and unevenness in recorded images do not present such a serious problem as in the case of industrial use. For printing apparatuses for industrial use that require high recording duties, demands are so strict with respect to the variation of recording densities and unevenness in recorded images that any one of the methods described above is not adoptable.
Also, the method described in the above paragraph 6) discloses a mechanism using cooling water to cool a specific printing head of a thermal transfer type, but there is no consideration given to any application at all to printing apparatuses of various types including those for industrial use.
As described above, even with the adoption of any one of the conventional methods, it is impossible to materialize an ink jet recording apparatus for industrial use, which is capable of printing in high recording duties with a good color reproducibility of prints without any variation of recording densities and unevenness in the recorded images.
Now, the ink jet technologies have reached the stage almost equal to the technical level of the offset printing in such areas as the image processing technique using error diffusion methods or the like, the graduation expression technique obtainable by the combination of such image processing technique and multiple composition printing; and in the image expression capability obtainable by the application of ink jet recording technique, which uses the wide color reproducibility by means of multicolor printing in six to ten color process beyond the conventional four prime color process.
Also, with such advanced technologies, a serial printing method is now adoptable for printing a screen of wider and longer size, and it is anticipated that the range of application of this method is expandable to the industrial fields such as ink jet textile printing, printing of large image screens, fabrication of color filters for use of display, and some others. However, there are problems yet to be solved as described above in this respect.
The ink jet technologies provide readiness as an output means for the computer publishing that uses a computer as its host device. Also, when applying the technologies, there is no need for the provision of steps to prepare impressions. It is not required to mix ink to obtain colors as desired, either, among other significant advantages. However, due to the problems described above, the application of these technologies has not been sufficiently developed as yet with respect to its use in the industrial fields.

Printing apparatus and method for controlling the temperature of a printing head with heating and cooling devices


A method for dynamically controlling the transmit power of transmission streams transmitted via multiple antennas is disclosed. A transmit power level for multiple streams is determined based on a first reference channel. The difference of signal to interface ratios (SIRs) between two reference channels may represent a power offset. The power offset may be used to determine gain factors used to transmit data channels on the secondary stream with reference to the gain factor of the first reference channel. The power offset may be used to determine other parameters, such a serving grant or transport block sizes of channels carried on the secondary stream. The power offset may allow transmission parameters of channels on the secondary stream to be determined based on the transmit power level of the primary stream and a gain factor for a reference channel transmitted via the primary stream.

Multiple antenna technologies are used in cellular communication systems to improve the robustness of downlink data transmission and to achieve higher data throughput. For example, in 3rd Generation Partnership Project (3GPP), the closed loop transmit diversity was introduced into downlink transmission in Universal Mobile Telecommunications System (UMTS) and, more recently, the Dual Stream Transmit Antenna Array (D-TxAA) multiple-input and multiple-output (MIMO) technology was adopted to downlink High Speed Downlink Packet Access (HSDPA) over higher speed data channels. The enhancements brought by the multiple antenna technologies, however, are only implemented in the downlink direction in UMTS Wideband Code Division Multiple Access (WCDMA) systems. Moreover, there is no mechanism for power reference in transmit diversity and MIMO implementation in uplink transmission. Proposed open-loop transmit diversity techniques, such as switched antenna and beamforming, may be suboptimal solutions because they may not support direct dynamic feedback.

Power control for closed loop transmit diversity and MIMO in uplink


An audio detector circuit forms L+R and L-R audio signals from an intermediate frequency compatible quadrature amplitude modulated signal in the form (1+L+R)cos(fct+.phi.) where .phi. contains phase modulated L+R and L-R signals. An envelope detector generates an L+R audio signal and in-phase and quadrature phase detectors produce L+R and L-R audio signals, respectively. The difference between L+R outputs of the envelope and in-phase detectors are amplified to generate a cosine correction signal. Each detector includes a differential operational amplifier having an field effect feedback transistor coupled between each amplifier output and the corresponding input and an field effect transistor coupling the compatible quadrature amplitude modulated signal to the operational amplifier inputs. The impedances presented by the feedback transistor are varied by the cosine correction signal to remove the cosine component of the compatible quadrature amplitude modulated signal while frequency multiplication at the IF frequency rate provides the correct phase audio signal for matrix and noise processing.

Modern AM broadcast stations transmit Compatible Quadrature Amplitude Modulation (C-QUAM) signals to permit reception by both standard monophonic receivers using envelope detectors and by stereo AM receivers employing stereo detectors.
As is well known in the art, a stereo signal contains a left audio component L and a right audio component R. The carrier of a C-QUAM broadcast signal is amplitude modulated by a monophonic signal, 1+L+R and is phase modulated by the stereo information in the form of (L+R) and (L-R) signals. In producing the C-QUAM broadcast signal, the carrier is first phase modulated in quadrature with the (L-R) and (L+R) audio signals. The phase modulated signal is modified by multiplying the in-phase and quadrature phase components by a factor cos .theta. where .theta. is the arc tan {(L-R)/ (1+L+R) } and is then limited to remove any amplitude variations therein. The amplitude limited output of the phase modulator is amplitude modulated by a standard 1+L+R signal in high level transmitter stages. The C-QUAM broadcast signal resulting from the foregoing operations is of the form (1+L+R)cos(2.pi.fct+.phi.) where fc is the carrier frequency, t is time and .phi. represents the phase modulation signals L+R and L-R signals with the cosine .theta. term.
A variety of stereo receivers have been implemented to accommodate C-QUAM broadcast signals. Examples of representative receivers may be found in the article entitled Quadrature System for AM Stereo by Parker, Hilbert & Sakaie published in the IEEE Transactions on Consumer Electronics, Vol. CE-23. No. 4, November 1977 at pages 456-459 and in U.S. Pat. No. 4,192,968.
The detector for a C-QUAM stereo receiver includes an envelope detector for the amplitude modulation information in the received signal, a synchronous "I" in-phase detector for the phase modulation L+R information in the received signal, a circuit for comparing the outputs of the envelope and in-phase detectors to provide a cosine correction signal, a synchronous "Q" quadrature-phase detector for the quadrature-phase modulation L-R information, a cosine correction circuit to remove the cosine information from the in-phase and quadrature-phase signals and a stereo detection circuit to detect the presence or absence of stereo signals. The standard L+R signal and L-R stereo signals obtained from the envelope and quadrature phase detectors are processed to develop left and right channel signals. In the absence of a stereo signal of acceptable strength, the stereo receiver reverts to monophonic reception and its envelope detector produces the monophonic signal L+R.
Both bipolar and CMOS type circuits have been used in C-QUAM detectors. The finite transconductance of bipolar circuits, however, introduces distortion while the multipliers used in the bipolar circuits exhibit speed and switching deficiencies and require an output level shifter and impedance buffer. CMOS type circuits eliminate the distortion and switching problems associated with the bipolar circuits but lack gain control. As a result, an additional gain control stage is needed in CMOS detectors to provide the cosine correction.

Compatible quadrature amplitude modulation detector system


An apparatus for cutting a food product is disclosed which utilizes a cutting wheel having a plurality of knives extending between a hub and a rim in conjunction with other cutting knives to produce a multi-dimensional cut of the food product. The use of the additional cutting knives enables the apparatus to dice a thin layered or leafy food product (cut it into small pieces) as opposed to merely slicing the food product in a single dimensional cut. The additional cutting knives may include one or more julienne knives attached to each of the knives of the cutting wheel so as to extend approximately at right angles to the cutting plane defined by the cutting wheel knives. A circular knife may be located upstream of the cutting plane defined by the cutting wheel such that the rotary knife longitudinally cuts the food product before it passes through the cutting plane. The apparatus according to the invention also utilizes separate drive motors for the feed conveyor and for the cutting wheel. In order to prevent deflection or deformation of the larger cutting wheel, a rim stabilizer engages the cutting wheel rim to prevent any deflection of the rim which, may cause deflection of the cutting knives, as the cutting wheel rotates.

The present invention relates to an apparatus for cutting a food product, more particularly, such an apparatus utilizing a rotatable cutting wheel having a plurality of generally radial slicing knives which define a cutting plane.
Known devices for slicing a food product typically comprise a rotatable slicing wheel having a plurality of knives extending between a hub and a rim so as to define a cutting plane and a conveying device for conveying the food product through the cutting plane. The speed of the feed device and the rotating speed of the cutting wheel are synchronized such that the food product is sliced into substantially uniform thickness slices. While generally successful, these known slicing machines have been heretofore limited to cutting the food product into slices and have been somewhat limited in the overall size of the food product which may be accommodated. The known food slicing devices also utilize a single motor to drive both the food product feed conveyor and the rotating cutting wheel. While the use of a single motor promotes accurate synchronization of the feed means and the cutting wheel speed, it results in a complicated drive arrangement requiring numerous lubrication points and increased maintenance.
The known slicing machines have been found inadequate for slicing food products such as Iceberg and Romaine lettuce. It has been necessary to precut the lettuce heads into halves or quarters before feeding them into the known slicing machines which are capable of making only a single dimension slicing cut. Thus, the known slicing machines have been utilized only to make shredded lettuce. The lettuce food products may be diced on a known dicing type of dicing apparatus, however, the size of the food product is, again, limited and the known devices are capable of producing only approximately 4,000 lbs. of food product per hour of operation. In order to properly dice a food product, such as lettuce, it is necessary for the apparatus to provide more than a one dimensional cut. This requirement has heretofore rendered the known slicing devices to be inappropriate for dicing food products.

Rotary apparatus for cutting a food product


Described herein are apparatus and associated methods for the generation of at least one user adjustable, accurate, real-time, virtual surgical reference indicium. The apparatus includes one or more real-time, multidimensional visualization modules, one or more processors configured to produce real-time, virtual surgical reference indicia, and at least one user control input for adjusting the at least one real-time virtual surgical reference indicium. The associated methods generally involve the steps of providing one or more real-time multidimensional visualizations of a target surgical field, identifying at least one visual feature in a pre-operative dataset, aligning the visual features with the multidimensional visualization, and incorporating one or more real-time, virtual surgical reference indicium into the real-time visualization. In exemplary embodiments, the apparatus and methods are described in relation to ocular surgery, more specifically capsulorrhexis.

Medical surgery, whether reconstructive, cosmetic, palliative, or otherwise, is highly patient specific. Even though most surgery patients have the same basic physical architecture, every body has its own set of specific features and dimensions with respect to its individual organs, tissues, and structures that in certain cases may be significantly different from those of expected norms. As a result, surgeons must rely upon their individual experience and skills to adapt whatever surgical techniques they are practicing to the individual requirements as determined by each patient's unique structural features and dimensions.
To date, this individualized surgical adaptation has been accomplished essentially through freehand techniques based upon a pre-surgery examination and evaluation of the individual patient's target surgical site. This examination may include preliminary measurements as well as the surgeon making reference markings directly on the patient's tissues with a pen or other form of dye or ink marking. Then, after the patient has been prepared and placed in position for surgery, typically in a supine or prone position as opposed to the often vertical positioning of the patient during the pre-surgery examinations, the surgeon adapts the placement and configuration of the initial surgical incisions to the actual physical dimensions and circumstances found in the patient as the surgical procedure progresses. As a result, many initial measurements or reference markings on the patient's skin are at best a general guide as to where to begin the procedure and have limited accuracy and influence on subsequent aspects of the procedure or on the overall outcome of the surgery.
Further complicating matters, there are numerous areas of the body which are not conducive to pre-surgery reference markings or measurements. This is particularly true of structures and tissues that have wet surfaces, such as the eye or mucous membranes, and of internal physical structures that cannot be accessed for direct measurement or marking prior to surgery, and of micro-surgical processes directed at tiny structures and tissues that cannot be effectively marked with known reference marking techniques.
Additionally, pre-surgical washing and sterilization processes may dissolve, alter or even remove reference markings from the patient's skin or other external tissues prior to the initiation of surgery. Similarly, subsequent wiping and contact with fluids, including the patient's body fluids, may remove or distort any remaining reference markings. As a result, even the most accurate surgical reference markings may lose any practical effectiveness beyond the initial stages of the surgical process.
Accordingly, in spite of the ongoing development and the growing sophistication of contemporary medical surgery, there is a continuing need in the art for the provision of effective surgical reference indicia.

Real-time surgical reference indicium apparatus and methods for surgical applications


A system and a method are disclosed for suppressing load transients in radio frequency power amplifier switching power supplies. A power supply control circuit is provided that includes a switcher circuit and a low drop out circuit. Load transients are suppressed by generating a preload control signal that activates an active current source either in the switcher circuit or in the low drop out circuit. The active current source counteracts a decrease in the switcher operating voltage when a load transient is present. Load transients are also suppressed by generating a step control signal that activates a transistor in a feedback resistor divider network in the switcher circuit to increase the switcher operating voltage during a load transient. The preload and step control signals are reset when the load transient has ended.

The telecommunications industry continually attempts to improve the transmitter circuitry in wireless communication systems. Power amplifier (PA) circuitry is a major component of a transmitter of a wireless communication device. Power amplifier (PA) circuitry provides the power for transmitting a signal (including data modulated and carried by the signal) so that a base station or a receiver can receive the signal.
Power amplifier (PA) circuitry uses a large amount of power. The power amplifier (PA) module is one of the most power consuming components of a wireless communication device. Therefore it is very desirable to provide power amplifier (PA) circuitry that is power efficient.
One method for improving power amplifier (PA) efficiency is to use a drain/collector modulation technique. In the drain/collector modulation technique a non-linear high efficiency power amplifier can be used (e.g., a class C power amplifier) instead of a linear low efficiency power amplifier (e.g., a class A amplifier). The power control of the power amplifier (PA) circuitry is achieved by adjusting the power amplifier (PA) power supply VCC. A high efficiency power supply combined with a high efficiency power amplifier (PA) (with constant bias) would be ideal.
In prior art power amplifier (PA) modules in GSM (Global System for Mobile Communications) telecommunication devices such as RF3110 (manufactured by RFMD) and TQM7M4014 (manufactured by Triquint), the power amplifier (PA) power supply VCC is from a linear regulator or "low drop out" (LDO) circuit. An LDO circuit can have a high efficiency when the value of its output voltage (VCC) is near the value of its input voltage (VBATT). But an LDO circuit will have a very low efficiency when its output voltage (VCC) is very low compared with its input voltage (VBATT).
The maximum efficiency for an LDO circuit is the ratio of the output voltage VCC to the input voltage VBATT. That is, the maximum efficiency is given by the ratio VCC/VBATT. For example, the maximum efficiency for an LDO in a typical GSM handset with an output voltage of nine tenths volts (VCC=0.9 volts) and an input voltage of three and six tenths volts (VBATT=3.6 volts) is twenty five percent (25%).
FIG. 1 illustrates a schematic diagram of a first prior art power supply control circuit 100. Power supply control circuit 100 comprises a low drop out (LDO) circuit 110. Low drop out (LDO) circuit 110 comprises an operational amplifier 120 that receives a VRAMP signal on its inverting input. A feedback voltage signal VFB is provided to the non-inverting input of operational amplifier 120. The operating voltage for low drop out (LDO) circuit 110 is provided by a voltage source VBATT.
The output of operational amplifier 120 is provided to a gate of a PMOS transistor 140. The source of PMOS transistor 140 is coupled to the operating voltage VBATT. The drain of PMOS transistor 140 is coupled to a first end of a first resistor 150. The second end of first resistor 150 is coupled to a first end of a second resistor 160. The second end of second resistor 160 is coupled to ground. The feedback voltage signal VFB is obtained from a node between the first resistor 150 and the second resistor 160.
The output of low drop out (LDO) circuit 110 is the power supply voltage VCC. A capacitor 170 is coupled between the output of the low drop out (LDO) circuit and ground. The power supply voltage VCC is provided to radio frequency (RF) power amplifier (PA) 130. Radio frequency (RF) power amplifier (PA) 130 amplifies an RF input signal (RFIN) to generate an amplified RF output signal (RFOUT).
One method for increasing the efficiency of the power amplifier (PA) power supply VCC is to use a switching regulator. A switching regulator is able to adjust the value of the operating voltage (designated VSWITCHER) that is provided to a low drop out circuit. FIG. 2 illustrates a schematic diagram of a second prior art power supply control circuit 200 that comprises a switching regulator 210 (designated "switcher 210"). Switcher 210 has a first input that receives a peak value of voltage (designated VPEAK) and a second input that receives an enable signal (designated ENSWITCHER).
The low drop out circuit 110 in FIG. 2 has the same structure as the low drop out circuit 110 shown in FIG. 1. However, the operation of the low drop out circuit 110 in FIG. 2 no longer has a single value of operating voltage VBATT. Instead, switcher 210 provides a wide dynamic range of operating voltages VSWITCHER to the low drop out circuit 110. For example, the value of the operating voltage VSWITCHER may be chosen in a range from about four hundred millivolts (400 mV) to about four and eight tenths volts (4.8 V).
FIG. 3 illustrates a schematic diagram of a third prior art power supply control circuit 300. Power supply control circuit 300 comprises a switching regulator 304 (designated "switcher 304") and a low drop out (LDO) circuit 306. As shown in FIG. 3, switcher 304 low drop out (LDO) circuit 306 both receive the VRAMP voltage. Both switcher 304 and low drop out (LDO) circuit 306 also receive a VBATT voltage. In addition, the low drop out (LDO) circuit 306 receives a transmit enable signal (designated "TX_EN"). When the transmit enable signal TX_EN is high, the low drop out (LDO) circuit 306 sends the power supply VCC to the power amplifier 302.
In the power supply control circuit 300 of FIG. 3 the output of the switcher 304 (designated "VSWITCHER") is set to a direct current (DC) level that represents the peak level of VCC by the control signal VPEAK. A typical value for the VSWITCHER voltage for a GSM full power condition may be four and nine tenths volts (4.9 V). A typical value for the VPEAK voltage for a GSM full power condition may be one and six tenths volts (1.6 V) for a steady state operation. The wide bandwidth low drop out (LDO) circuit 306 is used for polar modulation envelope tracking and for providing a fast response to the reference control signal VRAMP.
FIG. 4 illustrates the timing waveforms 400 that would be expected for a low drop out (LDO) circuit 306 in a GSM (Global System for Mobile Communications) telecommunication device in which there are no load transient effects. FIG. 5 illustrates the timing waveforms 500 that occur when load transient effects are present.
As shown in FIG. 4 and in FIG. 5, the switcher enable signal ENSWITCHER is turned on in advance of the transmit enable signal TX_EN so that the value of the VSWITCHER signal has settled at its high value before the transmit enable signal TX_EN causes the low drop out (LDO) circuit 306 to send the power supply VCC to the power amplifier 302. The value of the VRAMP signal usually ramps up very quickly. For example, it may increase from a zero value to a maximum value in approximately five microseconds (5 μsec). This will cause the switcher load to go from a no load condition of zero milliamperes (0 mA) to a maximum load condition of approximately two amperes (2 A).
As shown in FIG. 5, this will cause a significant load transient in the VSWITCHER signal. The value of the VSWITCHER signal may temporarily decrease or "dip" as much as two hundred millivolts (200 mV). The time of the decrease is designated in FIG. 5 as TTRAN. The TTRAN value represents the time duration of the load transient. Because of the load transient the VCC signal will not be able to follow the VRAMP signal until the VSWITCHER value settles again after the end of the load transient. This is because the VCC signal is not able to follow the scaled VRAMP signal during the load transient because the VSWITCHER signal is less than the desired peak level scaled VPEAK during the load transient.
There is also an overshoot on the VSWITCHER value when the power amplifier 302 turns off. This is of no concern, however, because the low drop out (LDO) circuit 306 will force VCC to follow VRAMP as long as VSWITCHER has enough headroom.
Therefore, there is a need in the art for a system and method that is capable of providing a remedy for these prior art deficiencies. In particular, there is a need in the art for a system and method that is capable of providing an improved architecture for a power supply control circuit and a low drop out (LDO) circuit that suppresses load transients that are created by a radio frequency (RF) power amplifier (PA) turning on from an off state.

System and method for suppressing load transients in radio frequency power amplifier switching power supplies


A logic circuit for outputting signals corresponding to an input signal depending on a clock signal sent from an external source includes at least one synchronous flip-flop being synchronized with the clock signal, so that the flip-flop latches the input signal, and a unit for controlling an input of the clock signal to the flip-flop based on a difference between logic levels of an output signal of the flip-flop and an input signal newly latched by the flip-flop.

1. Field of the Invention
The present invention relates to a logic circuit which includes at least one synchronous flip-flop.
2. Description of the Related Art
A four-bit shift register is known as one example of a CMOS (Complementary Metal-Oxide Semiconductor) logic circuit including synchronous flip-flops which are synchronized with clock signals. This four-bit shift register is arranged to have four synchronous D-type flip-flops F1, F2, F3 and F4. The flip-flops F1, F2, F3 and F4 are sequentially connected to each other. That is, the flip-flop F1 is serially connected to the flip-flop F2. The flip-flop F2 is connected serially to the flip-flop F3. The flip-flop F3 is serially connected to the flip-flop F4. Each of the four synchronous D-type flip-flops is connected to an inverter. The inverters supply a clock signal to each flip-flop. In an initial state that each of the flip-flops outputs a low-level signal, when a data signal which is input to the flip-flop F1 rises to a high level, at first, the flip-flop F1 latches the high-level data signal at the leading edge of the clock signal and outputs a high-level output signal H1. The flip-flop F2 latches the high-level signal H1 sent by the flip-flop F1 at the next leading edge of the clock signal and outputs a high-level output signal H2. Likewise, the remaining flip-flops F3 and F4 serve to output their high-level output signals H3 and H4 in the same process as above.
Conversely, when the data signal lowers to a low level, those flip-flops F1 to F4 serve to sequentially output the low-level signals L1 to L4 as being synchronized with the clock signals. That is to say, the data signal input to the flip-flop F1 is shifted to the next flip-flops as being synchronized with each leading edge of the clock signals so that the flip-flops F1 to F4 serve to output parallel signals in sequence.
The aforementioned shift register is arranged to inevitably receive a clock signal even when the data signal input to each flip-flop has the same logic level as the output signal of each flip-flop, therefore, in the case that no flip-flops are required to change their states. The clock signals input to the flip-flops result in charge and discharge currents flowing in internal circuits of the flip-flops, which thereby consumes power. As such, the logic circuit is arranged so that a clock signal is input to the flip-flops of the logic circuit if not necessary, which results in the idle current flowing in the logic circuit.
The shift register needs an inverter arranged to have a CMOS transistor of a large driving capacity, for supplying clock signals to the flip-flops F1 to F4 of the shift register. Such a CMOS transistor having a large driving capacity entails flow of a large through current in internal circuits of the flip-flops when the clock signal is reversed. It is another disadvantageous factor of increasing the idle current, that is, of increasing the power consumption.


The present invention relates to a novel method for producing metabolites from omeprazole using bacterial cytochrome P450, and a composition therefor, and more specifically, to a composition and a kit for producing a 5′-hydroxyl product from omeprazole, containing bacterial cytochrome P450 BM3 (CYP102A1) or mutants thereof, and to a method for producing the same. The composition, the kit, and the method are capable of economically and highly efficiently mass-producing the 5′-hydroxyl product from the omeprazole, and thus will significantly contribute to development of a novel drug using metabolites from the omeprazole.

Omeprazole, which is a proton pump inhibitor, is known as a therapeutic agent of indigestion, stomach ulcer, gastroesophageal reflux disease and laryngopharyngeal reflux disease. The omeprazole, which is a racemate, contains S and R enantiomers at a ratio of 50:50. Both enantiomers in the above acidic condition are converted into an achiral compound and reacted with a cysteine group of H+/K+ATPase to inhibit stomach acid production in a parietal cell of the stomach. The omeprazole and enantiomers are metabolized by CYP2C19 and CYP3A4 which are cytochrome P450 present in a human liver, and main metabolites thereof include 5′-O-desmethyl omeprazole, 5′- and 3′-hydroxyomeprazole and omeprazole sulfone (see Renberg et al., Drug Metab Dispos 17:69-76, 1989; Andersson et al., Clin Pharmacokinet 40:411-426, 2001, Li et al., J Pharmacol Exp Ther 315:777-787, 2005). It has been reported that the R enantiomer is generally metabolized to be 5′-O-desmethyl omeprazole, 5′-hydroxyomeprazole by CYP2C19 and the S enantiomer is generally metabolized to be omeprazole sulfone, 3′-hydroxyomeprazole by CYP3A4.
Cytochrome P450 (P450 or CYP) enzyme is a large family consisting of enzymes serving as catalysts of significantly various oxidation reactions throughout the nature ranging from archaea to bacteria, fungi, plants, animals and human. Due to variety of catalytic function, and a wide range of substrates thereof, P450s are largely useful as a biological catalyst in production of fine chemicals including medical supplies, and the like (see Guengerich, Nat Rev Drug Discov 1:359-366, 2002; Urlacher et al., Trends Biotechnol 24:324-330, 2006; Yun C H et al., Trends Biotechnol 25:289-298, 2007; Lamb et al., Curr Opin Biotechnol 18:504-512, 2007). However, despite of potential usability of the cytochrome P450 enzymes of a mammal in various biotechnological fields as described above, P450s have low stability, catalytic activity, and availability, and thus, are not appropriate as a biological catalyst.
When a prodrug is converted into a biologically "active metabolite" by P450s by humans during development of the drug (see Johnson et al., Breast Cancer Res. Treat 85:151-159, 2004), a large amount of pure metabolites are required for a research of efficacy, toxicity, pharmacokinetics, and the like, of the drug. In addition, when the metabolite itself has a biological activity, direct administration of the metabolite in vivo has a large benefit, and thus, mass-production of the metabolite is important.
When the omeprazole is administered into a human body, since the omeprazole is metabolized by CYP2C19 and CYP3A4, a rate at which the metabolite is produced may vary depending on the degree of expression of the enzymes. In addition, a drug interaction problem with other drugs metabolized by the enzymes occurs. Therefore, when the omeprazole metabolite is directly used as a drug, the drug interaction problem may be avoided.
However, since there are various problems in chemically synthesizing pure metabolites, in order to product a metabolite of a drug or a drug candidate as an alternative of the metabolite chemical synthesis, P450 is used. The production of the metabolites using human P450s expressed from E. coli (see Yun et al., Curr Drug Metab 7:411-429, 2006) or insect cells (see Rushmore et al., Metab Eng 2:115-125, 2000; Vail et al., J Ind Microbiol Biotechnol 32:67-74, 2005) has been reported. However, these systems have problems such as expensive cost and low productivity due to limited stability, slow reaction rate, and the like (see Guengerich et al., Crit Rev Toxicol 26:551-583, 1996). Accordingly, a method for using engineered bacterial P450 enzymes having a desired catalytic activity as an alternative for producing metabolites in human has been suggested (see Yun C H et al., Trends Biotechnol 25:289-298, 2007).
Meanwhile, heme domain of P450 BM3 (CYP102A1) derived from Bacillus megaterium has a mono oxygenase activity, which is significantly similar to a member of mammalian of CYP4A (fatty acid hydroxylase) family. Naturally, it is formed of single polypeptides in which a CYP102A1 reductase domain having a mammal-like diflavin reductase function is fused to a C-terminal of the P450 heme domain. The fusion of two enzyme activities makes a fusible CYP102A1 to be a desirable mammal model, in particular, a desirable model of a human P450 enzyme. It has been reported that CYP102A1 mutants genetically engineered through logical design or directed evolution oxidize several substrates of human P450 to product a metabolite having higher activity (see Kim et al., Drug Metab Dispos 36:2166-2170, 2008, Kim et al., Drug Metab Dispos 37:932-936, 2009, Kim et al., J Mol Catal B: Enzym 63:179-187, 2010; Otey et al., Biotechnol Bioeng 93:494-499, 2006; Yun C H et al., Trends Biotechnol 25:289-298, 2007).
Based on the above-description, it has been suggested that the mutants of CYP102A1 may be developed as a biological catalyst for detection and synthesis of the drug. Recently, it has been reported that several selected mutants may allow the CYP102A1 enzyme to product a metabolite in human as a drug (see Kim et al., Drug Metab Dispos 36:2166-2170, 2008, Kim et al., Drug Metab Dispos 37:932-936, 2009); however, a method for biologically producing a metabolite in human from the omeprazole has not been reported yet.

Method for producing metabolites from omeprazole using bacterial cytochrome P450, and composition for same


An earbud comprises: a casing in which a sound cavity is provided; a speaker disposed in the sound cavity and dividing the sound cavity into a front sound cavity and a rear sound cavity; and an acoustic structure located in the rear sound cavity. The acoustic structure comprises a first sound guiding wall and a cover plate, the first sound guiding wall is attached to a bottom surface of the rear sound cavity and is configured to, together with at least a part of an inner wall of the casing, constitutes a sound guiding groove, and the cover plate is mounted at an upper opening part of the sound guiding groove, such that the sound guiding groove forms a bass pipe which communicates from the rear sound cavity to at least one aperture of the casing.

TWS is short for true wireless stereo. TWS Bluetooth earbud (headphones) can realize real wireless separation of Bluetooth left and right channels. Since two ear-hooks of the TWS Bluetooth earbuds need not a cabled connection, the left and right earbuds form a stereo system via Bluetooth, and the functions of listening to songs, making calls, and being worn are all improved.
In the TWS earbuds on the current market, the bass pipe is a separate pipe structure. Due to the comprehensive influence of the thickness of the pipe wall of the bass pipe and the thickness of the earbud casing, a relatively larger part of the internal space of the earbud will be occupied in order to provide a bass pipe with a certain space. Moreover, since the bass pipe is a separate structure, it must be assembled into the earbud in the actual production process, which is fairly difficult; moreover, the acoustic structure is complicated, so the production cost is high and the production yield is relatively lower.