The present invention relates to injectable, thermosensitive hydrogel compositions comprising linezolid for relieving and/or treating chronic low back pain (CLBP).

Chronic Low back pain (CLBP) is common among the general population worldwide. A positive association between Modic changes (bone edema) on MRI and non-specific LBP with a mean odds ratio (OR) of 4.5 has been observed. Jensen et al. reviewed that the prevalence for any type of Modic changes (e.g., Types I-III) in patients with non-specific CLBP was 46% as opposed to 6% in the general population (Jensen et al., Eur. Spine J. 2008, 17:1407-1422).
Modic changes, characterized by edema (or inflammation) in vertebrae, are likely caused by low-grade infection of the disc tissue, where disc/endplate damage and the persistence of an inflammatory stimulus create predisposing conditions. Propionibacterium acnes (P. acnes) inside nonpyogenic intervertebral discs has been shown to be one pathogen causing Modic changes (e.g., Type I) and nonspecific low back pain (Stirling et al. Lancet, 2001, 357:2024-2025; Agarwal et al. Spine J. 2010, 10: S45-S46; Albert et al., Eur Spine J., 2013, 22(4): 690-696; Capoor et al., PLoS One, 2016, 11(8):e0161676. doi: 10.1371; and Capoor et al., PLos One, 2017, 12(4): e0174518.doi:10.1371). Disc cells can develop an inflammatory response to P. acnes infection (Dudli et al., Eur Spine J., 2017, Sep. 7. doi: 10.1007/s00586-017-5291-4). P. acnes isolated from a patient associated with Modic changes and disc degeneration, when inoculated into the intervertebral discs, can induce inflammatory reaction, intervertebral disc degeneration and Modic changes (Chen et al., Biomed Res Int. 2016: 9612437. doi: 10.1155/2016/9612437. Epub 2016 Jan. 26; and Chen et al., Int Orthop. 2016, 40(6):1291-1298; and Dudli et al., J Orthop Res. 2016, 34(8):1447-1455). Studies done in animals also show that P. acnes infection in disc can induce degeneration of the disc and Modic changes (Zamora et al., Orthop Traumatol Surg Res., 2017, 103(5): 795-799; Shan et al., Spine, 2017, Apr. 10. doi: 10.1097/BRS.0000000000002192; and Shan et al, J Bone Joint Am., 2017, 99(6): 472-481). Strains of P. acnes associated with tissue infections also express hyaluronic acid degrading enzymes which may contribute to disc degeneration. (Nazipi et. al., Microorganisms. 2017 Sep. 12; 5(3). pii: E57. doi: 10.3390/microorganisms5030057).
It is hypothesized that anaerobic bacteria (like P. acnes) from mouth and skin may gain access to the disc. Local inflammation in the adjacent bone may be a secondary effect due to cytokine and propionic acid production, where the infection is in the disc and the Modic change is a "side effect" manifested in the bone (Albert et al., Eur Spine J., 2013, 22(4): 690-696).
Antibiotic therapy may be effective in the treatment of CLBP associated with Modic changes). Several studies have shown that oral administration of antibiotics such as amoxicillin-clavulanate can have a clinically important and statistically significant (p<0.001) improvement in all outcome measures in patients with chronic LBP (Albert et al., Br. J. Sports Med. 2008, 42(12): 969-973; and Albert et al. Eur Spine J. 2013, 22(4): 697-707). These results provided support for the hypothesis that bacterial infection may play a role in CLBP with Modic changes.
Although several non-surgical treatment approaches including intradiscal injections of steroid, anti-TNF-α antibody and bisphosphonates have demonstrated some short-term efficacy in non-replicated clinical studies in reducing Modic changes and CLBP, none of these approaches is successful and causes controversial results. On this background, there is a need in the art for modalities to address the treatment, alleviation, prevention, and/or mitigation of pain found to be coincident with diseases, conditions or disorders of the bones, joints, ligaments and/or tendons, especially those associated with Modic changes or bone edema. The present invention provides linezolid formulations to fill this need. Linezolid is an antibiotic used for the treatment of infections caused by Gram-positive bacteria that are resistant to other antibiotics. P. acnes clinical isolates which are resistant to linezolid (MIC>4 μg/ml) have not been widely reported. The linezolid formulations provide an effective delivery of linezolid to the diseased disc and vertebrae, therefore improve treatment efficacy of Modic changes and CLBP.


A tunnel thruster system for a vessel. The tunnel thruster system includes a thruster propulsion mechanism including a drive unit driving a transmission and propeller assembly located within a thruster tunnel. The thruster tunnel comprising a propeller section, first and second tapered tunnel sections interconnected with one another by the propeller section, the propeller section and the first and the second tapered tunnel sections oriented substantially transversely to a keel of the vessel and accommodating the transmission and propeller assembly. Each tapered tunnel section extends from the propeller section to a tunnel opening through a hull of the vessel. Diameters of the first and the second tapered tunnel sections corresponding to a diameter of the propeller section at the propeller section and taper outward toward a larger diameter at each of the corresponding tunnel openings through the hull of the vessel.

Marine craft frequently require the capability for precisely controlled navigation in confined or restricted waters and, in particular, for precise control and maneuvering of a vessel at low speeds. A typical and frequently occurring example of such low speed, precisely controlled maneuvering is the docking of a vessel wherein the vessel must be brought into a precisely controlled position with respect to a docking area, at very low speed which is often at or below the minimum speed at which conventional propulsion and steering systems can provide the necessary control of the vessel.
Although conventional propulsion and steering systems have been and still are commonly employed in such low speed, precise maneuvering of a vessel, conventional rudder and propeller systems present a number of difficulties in such maneuvers and typically require that a vessel be piloted by an experienced operator familiar with the particular and often unique characteristics of the vessel with respect to the steering and propulsion responses of the vessel and the responses of the vessel to such factors as, for example, wind and currents. In vessels having, for example, a conventional single propeller and rudder system or an odd number of propellers, the central propeller will typically generate an unbalanced transverse thrust that will tend to turn the vessel toward the port or the starboard side of the vessel, depending upon whether the central propeller has a right or left hand blade pitch and whether the propeller is rotating in a clockwise or counterclockwise direction. This effect may be mitigated or avoided in vessels having an even number of propellers by arranging the propellers with opposing blade pitches so that the propellers rotate in opposite directions, but still may occur if the engine speeds are different, thereby resulting in an unbalanced lateral thrust. This effect is accentuated at low speeds, and the problem is compounded because of the interactions between the angle and direction of water flow over the rudder or rudders caused by the propeller or the propellers and by the motion of the vessel through the water. While experienced pilots familiar with the characteristics of a given vessel or vessels may employ these effects while maneuvering a vessel, such experience is often lacking, and can result in undesirable outcomes, even for smaller vessels ranging from scratches, dents and damage to a docking area to major damage to or even the sinking of a vessel.
The above described problems with conventional propeller and rudder systems has resulted in the development of lateral thrusters mounted at or in the bow or bow and stern of a vessel and using transversely mounted propellers to generate lateral forces on the bow and/or stern of a vessel, thereby facilitating turning of the vessel and allowing a vessel to be moved or positioned laterally, including allowing a vessel to be held stationary against winds and currents. In general, bow thrusters are mounted in transverse tunnels extending from one side to the other side of the vessel at or near the bow, which is generally narrow compared to the mid-section of a vessel. Stern thrusters, however, because of the differing shapes assumed by the sterns of various vessels, may for example be mounted internally in the hull with inlet and outlet ports, in transverse passages or tunnels in a fin-like region of the keel forward of the propellers and rudders, or in cylindrical ducts or housings mounted transversely on the stern or transom of the vessel. In other implementations, thrusters may be mounted in or on retractable housings that are stored within the hull along the keel, when not in use, and that are extended below the keel when required.
Examples of conventional tunnel thruster installations of the prior art are shown in FIGS. 1A through 1C in which FIG. 1A illustrates a tunnel thruster system 1 that includes a tunnel thruster propulsion mechanism 10 having a single reversible propeller 12 mounted in a transverse tunnel 14 extending transversely to the keel axis 16K of the hull 16 of the vessel 18. A tunnel thruster system 1 is typically installed as far forward as possible in the hull to maximize the leverage effect around the pivot point and as deep as possible below the waterline to avoid any air from being sucked from above the water surface into the tunnel 14, which would significantly decrease the effectiveness of the tunnel thruster. As illustrated, the tunnel thruster propulsion mechanism 10 includes a drive unit 10A, typically an electric or hydraulic motor or a connection to an internal combustion engine, a motor mount 10B supporting a transmission and propeller assembly 10C, and a gearing or flexible drive shaft(s) for converting the rotation of a drive shaft 10D, connected with the drive unit 10A, into rotation of a propeller drive shaft 10E which drives a propeller 12. FIG. 1B illustrates a tunnel thruster system 1 similar to that of FIG. 1A, but in which the tunnel thruster propulsion mechanism 10 includes two opposed propellers 12A, 12B wherein the pitches of the blades of propellers 12A, 12B and the gearing of propeller assembly 100 are arranged so that the propellers 12A, 12B operate cooperatively to generate lateral thrust. In this regard, the pitches and drive trains of the propellers 12A and 12B may be arranged so that the propellers 12A and 12B either rotate in the same rotational direction or are counter-rotating, that is, the propellers 12A and 12B rotate in opposite rotational directions. FIG. 1C illustrates the central portion 14A of a transverse tunnel 14 of a tunnel thruster system 1 having opposed reversible propellers 12A, 12B, similar to that illustrated in FIG. 1B.
As discussed above, stern mounted tunnel thruster systems 1 are generally similar to the bow mounted tunnel thruster systems 1, illustrated in FIGS. 1A-1C, but may be mounted to a vessel differently due to the different shape of the stern regions of a vessel, as compared to the bow regions of the vessel. As described above, stern tunnel thruster systems 1 may, for example, be mounted internally in the hull with inlet and outlet ports, in transverse passages or tunnels in a fin-like region of the keel forward of the propellers and the rudders, or in cylindrical ducts or housings mounted transversely on the stern or transom of the vessel. In other implementations, the tunnel thruster systems may be mounted on or in retractable mountings, stored within the hull along the keel when not in use, and extended below the keel when required, and may be rotatable about a vertical axis to allow the thrust, generated by the thruster system, to be directed at a range of angles relative to the keel of the vessel or possibly mounted internally within inlet or outlet ports.
Tunnel thruster systems, however, suffer from a number of disadvantages and limitations that are inherent in the flow of water through a cylindrical passage, that is, the tunnel of a tunnel thruster system, and the interaction between a propeller and the water flowing in the tunnel. For example, the thruster tunnel inherently restricts the volume of the water flowing through the propellers region of influence, thereby correspondingly restricting the thrust than can be generated by the propeller, and the interaction between the water and the tunnel boundaries presents a significantly higher flow resistance compared to a propeller acting in an open flow region, both of which result in significantly reduced efficiency compared to a propeller acting in an open flow region. The effects of the tunnel on water flow characteristics also often result in the generation of high levels of noise due to propeller cavitation, as discussed in further detail below.                Considering the inherent disadvantages and limitations of tunnel thruster systems in further detail, and considering bow thruster systems as exemplary of all forms of tunnel thrusters, FIG. 2A is a diagrammatic illustration of the flow of water into and through a tunnel 14 of a conventional tunnel thruster system 1 of the prior art and illustrates the effects of the shape of the transition region 20 between the entrance of tunnel 14 and the hull 16 and, in particular, the effects of a too sharp or badly rounded tunnel 14 to hull 16 configuration. As indicated therein, a too sharp or badly rounded hull 16 to tunnel 14 flow transition region 20, such as at flow discontinuity 20D, or any other form of discontinuity or too abrupt a change in the path of fluid flow, such as a discontinuity or too sharp a gradient in the wall 22 surface, will result in the formation of a urbulence region 24T near the wall 22 surface wherein a turbulence region 24T is characterized by macroscopic turbulence, a detached boundary layer, eddies and vortices while the flow of water in a non-turbulent inner zone 24L is characterized by an undetached boundary layer and little or no turbulence, eddies or vortices. The turbulence, eddies and vortices in a turbulence region 24T results in and determines the magnitude of a reduction in the rate of flow of water in the turbulence region 24T, that is, a reduction in the mean axial flow speed of the water near the tunnel wall 22. This, in turn, results in a slowing of the fluid flow adjacent the walls 22 of the tunnel 14 and may adversely affect the effectiveness and the efficiency of the thruster propeller 12, 12A or 12B. That is, and as illustrated in FIG. 2C, the reduction in the mean axial speed (VA-speed of advance) of the water flow near the wall 22 will, in turn, result in and determine an increase in the angle between the velocity of the water relative to the blade and pitch line, that is, the angle of attack of the blade of the propeller 12, 12A or 12B. In addition, the turbulence in the water flow around the propellers creates irregular and unpredictable velocity variations along the propeller blade surfaces, thereby making it difficult to optimize the propeller design in order to reduce noise and increase efficiency and performance.
The solution to such fluid flow problems in thruster tunnels 14 that have been most commonly recommended and adopted in the prior art, as is illustrated in FIG. 2B, is to round the juncture between the hull 16 and the tunnel wall 22 to thruster tunnel flow transition region 20 so as to avoid flow separation and the formation of turbulence regions 24T, with the most common recommendation being that the optimum radius of the transition region 20 be on the order of 10% of the tunnel 14 diameter. This solution is believed to not only reduce the water flow characteristics leading to the turbulence region 24T, but to allow the thruster 10 to draw water from a region around the tunnel 14 opening in the hull 16. The increased movement of water over a larger area results in a suction pressure acting on the hull surface that increases the effect and efficiency of the thruster 10 proportional to the increase in area of the hull surface on which the suction pressure is exerted due to the increased radius of the transition region 20.
It is well known, however, that the achievement of the recommended optimum hull 16 to the thruster tunnel flow transition region 20 shape presents significant design problems in, for example, achieving the necessary hull structural strength, significant increases material and hull space costs and requirements and construction time and effort, so that these solutions of the prior art generally have proven unsatisfactory.
The present invention provides a solution to these and related problems of the prior.


A transmission device for a motor vehicle includes a multi-speed transmission; a multidisc clutch assigned to the multi-speed transmission for changing gears of the multi-speed transmission, and an actuating device for actuating the multidisc clutch, wherein the actuating device has a wedge mechanism which is operatively connected with the multidisc clutch for actuating the multidisc clutch.

The invention relates to a transmission device for a motor vehicle.
The following discussion of related art is provided to assist the reader in understanding the advantages of the invention, and is not to be construed as an admission that this related art is prior art to this invention.
In multi-speed transmissions a change between the multiple gears of the transmission can be accomplished for example by a multidisc clutch. The multidisc clutch can be actuated by an actuator. The actuator operates for example hydraulically and as a result a hydraulic pressure is required for changing a gear. In order to change the gear within a shortest possible time period the hydraulic pressure usually has to be provided permanently, which in turn results in a relatively high energy consumption.
It is therefore an object of the invention to provide an improved transmission device for a motor vehicle, which in particular has a lower energy consumption.


A heat recovery steam generation system is provided. The heat recovery steam generation system includes at least one superheater in a steam path for receiving a steam flow and configured to produce a superheated steam flow. The system also includes an inter-stage attemperator for injecting an attemperation fluid into the steam path. The system further includes a control valve coupled to the inter-stage attemperator. The control valve is configured to control flow of attemperation fluid to the inter stage attemperator. The system also includes a controller coupled to the control valve and the inter-stage attemperator. The controller further includes a feedforward controller and a trimming feedback controller. The feedforward controller is configured to determine a desired amount of flow of the attemperation fluid and the trimming feedback controller is configured to compensate for inaccuracies in the determined amount of flow of the attemperation fluid to determine a net desired amount of flow of attemperation fluid through the control valve into an inlet of the inter-stage attemperator based upon an outlet temperature of steam from the superheater. The controller also determines a control valve demand based upon the flow to valve characteristics. The controller further manipulates the control valve of the inter-stage attemperator, and injects the desired amount of attemperation flow via the inter-stage attemperator to perform attemperation upstream of an inlet into the superheater.

The present invention relates generally to control systems for controlling temperatures. More specifically, the invention relates to a temperature control of steam in relation to inter-stage attemperation, which may be used in heat recovery steam generation (HRSG) systems in combined cycle power generation applications.
HRSG systems may produce steam with very high outlet temperatures. In particular, HRSG systems may include superheaters through which steam may be superheated before being used by a steam turbine. If the outlet steam from the superheaters reaches high enough temperatures, the steam turbine, as well as other equipment downstream of the HRSG, may be adversely affected. For instance, high cyclic thermal stress in the steam piping and steam turbine may eventually lead to shortened life cycles. In some cases, due to excessive temperatures, control measures may trip the gas turbine and/or steam turbine. This may result in a loss of power generation that may, in turn, impair plant revenues and operability. Inadequately controlled steam temperatures may also lead to high cyclic thermal stress in the steam piping and steam turbine, affecting their useful life. Conventional control systems have been devised to help monitor and control the temperature of outlet steam from HRSG systems. Unfortunately, these control systems often allow temperatures to overshoot during transient periods where, for instance, inlet temperatures into the superheaters increase rapidly.
Conversely, while trying to control high outlet steam temperatures, there are other potential adverse attemperation control effects. There is a danger of causing the temperature to go too low resulting in subsaturated attempertor fluid flowing through the superheaters, interconnecting piping, or steam turbine. Control stability problems can also use cyclic life of the steam system downstream of the attemperator as well as effect the life of the attemperation system valves, pumps, etc.
In particular, a non-model-based technique commonly used consists of a control structure where an outer loop creates a set point temperature for steam entering the finishing high-pressure superheater based on a difference between a desired and an actual steam temperature exiting the finishing high-pressure superheater. An outer loop proportional-integral-derivative (PID) controller may establish the set point temperature for an inner loop PID controller. The inner loop of the control logic may drive the control valve based on the difference between the actual and set point temperature to suitably reduce the steam temperature before it enters the finishing high-pressure superheater. Unfortunately, this technique may not always work to control steam temperature overshoots during transient changes in the gas turbine output. In addition, this technique may often require a great deal of tuning in order to verify satisfactory operation during all potential transients.
Regarding the overshoot problem with the non-model-based technique, as the temperature of the exhaust gas from the gas turbine increases, the temperature of the steam exiting the finishing high-pressure superheater may not only increase beyond the set point temperature, but may continue to overshoot a maximum allowable temperature even after the temperature of the exhaust gas begins to decrease. This overshoot problem may be due in part to the presence of significant thermal lag caused by the mass of metal used in the finishing high-pressure superheater. Other factors affecting attemperation may include the type and sizing of attemperation valves, operating conditions of the attemperator fluid supply pump, distances between equipment used, other limitations of equipment used, sensor location and accuracy, and so forth. This overshoot problem may also become more acute when the gas turbine exhaust temperature changes rapidly.
The conventional attemperator control logic requires an interactive and long tuning cycle. The model-based predictive technique consists of a cascading control structure where the outer loop (some combination of feedback and feed-forward) creates a set point temperature for steam entering the finishing superheater (FSH) (i.e. at the inlet of FSH) based on the difference between a desired and actual steam temperature exiting the finishing superheater (FSH). The inner loop drives the attemperator valves based on the difference between the actual and set point temperature for the inlet to the FSH to suitably reduce the steam temperature before it enters the FSH. Due to the presence of a cascade control structure the control tuning is not easy as the changes in one controller affect the performance of the other. This necessitates an interactive and long tuning cycle. Due to a competitive market and tight commissioning schedules such a controller can end up being less than optimally tuned, thus adversely affecting the long term performance of the whole system.
Accordingly, there is a need for an improved temperature control system in heat recovery systems which is easily tunable to be stable, and also prevents large temperature overshoots, and prevents the flow of subsaturated attempertor fluid through the steam system downstream of the attemperator.


A method for manufacturing a wafer scale heat slug system includes: dicing an integrated circuit from a semiconductor wafer; forming a heat slug blank equivalent in size to the semiconductor wafer; dicing the heat slug blank to produce a heat slug equivalent in size to the integrated circuit; attaching the integrated circuit to a substrate; attaching the heat slug to the integrated circuit; and encapsulating the integrated circuit.

An integrated circuit (IC) die is often fabricated into a microelectronic device such as a microprocessor. The increasing power consumption of microprocessors results in tighter thermal constraints for a thermal solution design when the microprocessor is employed in the field. If the transistors of the integrated circuit get too hot they can be damaged. Accordingly, a thermal interface is often needed to allow the integrated circuit to release heat more efficiently. A thermal interface can include such things as a heat sink or fan.
Various techniques have been employed to transfer heat away from a die. These techniques include passive and active configurations. One passive configuration involves a conductive material in thermal contact with the backside of a packaged die. This conductive material is often a slug, a heat spreader, or an integrated heat spreader (IHS).
A heat spreader is employed to spread and dissipate the heat generated by a die, which minimizes concentrated high-heat locations within the die. A heat spreader is attached proximately to the back side of a microelectronic die with a thermally conductive material, such as a thermal interface material (TIM). A TIM can include, for example, thermally conductive gels, thermal greases, or solders. Heat spreaders include materials such as aluminum, copper, copper alloy, or ceramic, among others.
With conventional technology, a packaged microelectronic device includes a die which is bonded from the back side to an integrated heat spreader (IHS). An IHS adhesive layer acts as a TIM to bond the die to the IHS. The conventional IHS includes a lip portion that is formed by a bending process which gives rise to less than complete filling into the corner of the bend. Additionally to form the lip portion of the IHS from a rectangular blank, several stamping processes are required to deliver sufficiently flat upper and lower surfaces to achieve quality bonds with other structures such as heat sinks and dies, respectively. These stamping processes result in a relatively low yield in the production of heat spreaders, due, at least in part, to the processes used for forming heat spreaders. Additionally, the stamping processes result in a significant variation in flatness of the top surface of the IHS, as well as the bottom surface. The surface flatness can detrimentally affect adhesion to either side of the IHS.
The current IHS, typically manufactured from a high purity copper alloy, is difficult to form with existing stamping equipment limitations, especially with respect to maintaining high raw material yield metrics and fully-filled corner geometries that are achieved with the stamping process. In order to completely fill the corner locations of the IHS, typical industry raw material yields range as low as 35%, yet utilize multi-stage manufacturing with high-tonnage machinery. The surface flatness is a large contributor to the fall-out and yield problems. Thus far the manufacture of finished packages with heat spreaders has been expensive and time consuming.
Thus, a need still remains for a wafer scale heat slug system that can deliver good thermal performance, package integrity and can use existing assembly tools. In view of the ever increasing performance and shrinking space for integrated circuits, it is increasingly critical that answers be found to these problems.
Solutions to these problems have been long sought but prior developments have not taught or suggested any solutions and, thus, solutions to these problems have long eluded those skilled in the art.

This patent is subject to a terminal disclaimer.

Method for manufacturing wafer scale heat slug system


A 360 degree viewing angle lens unit, from the object side to the image side thereof, includes a 360 degree viewing angle lens and a relay lens. The viewing angle lens includes an annular incident surface, a first reflective surface, a second reflective surface, and an emitting surface. The annular incident surface has a positive radius of curvature and symmetrically concentric around an optical axis of the lens unit. The first reflective surface has a positive radius of curvature and is symmetrically concentric around the optical axis. The second reflective surface has a negative radius of curvature, and is coaxial with the incident surface. The emitting surface has a positive radius of curvature and is coaxial with the first reflective surface. The relay lens has a positive refractive power and is aligned with the emitting surface. The relay lens is configured for condensing image light output from the emitting surface.

1. Technical Field
The present disclosure relates to lens systems and, particularly, to a 360° viewing angle lens unit capable of imaging a lateral perspective of 360° circumference along the optical axis thereof, and an optical lens system utilizing the 360° viewing angle lens.
2. Description of Related Art
360° viewing angle lens systems are commonly used in a camera system for capturing images in full-360° angle-of-view. In a general 360° viewing angle lens systems, a 360° viewing angle lens is often arranged in front of a regular lens group along the optical axis of the regular lens group. As such, the regular lens group can collect the lights in front of the 360° viewing angle lens, while the 360° viewing angle lens can collect the image lights around the optical axis in a 360° circumference. However, in such an arrangement, the 360° viewing angle lens system may only capture an image including a front perspective along the optical axis of the regular lens group and another circumference perspective surrounding the optical axis of the regular lens group at the same time at most. It limits some special requirements for capturing images along different directions.
Therefore, it is desirable to provide a 360° viewing angle lens unit and an optical lens system using the 360° viewing angle lens, which can overcome the above-mentioned problems.

360 degree viewing angle lens unit and optical lens system using same

Hong Fu Jin Precision Industry (ShenZhen) Co., Ltd.


An event data transmission scheme is provided for reducing positron emission tomography event losses. The event data transmission scheme employs a more effective use of available data bandwidth. Each of a plurality of detector data slots is connected directly to a data aggregation control interface, and the control interface is connected to a coincidence processor.

Positron emission tomography (PET) scanners measure annihilation events. An annihilation event occurs when a positron emitted from a radionuclide encounters an electron and the positron and electron are converted into two photons. An image can be created based on data indicating the number of annihilation events at each location in a scanner's field of view. A PET scanner detects the annihilation events using a scintillator and light sensor. Data from a group or "bank" of PET detectors is generally aggregated into a single data path with each detector occupying a specific "slot" for efficient transmission to a coincidence processor. Within an individual bank, data can be daisy chained, or connected in series, from slot to slot, until the last slot is reached. Data that has reached the last slot or was generated in the last slot is then transmitted to the coincidence processor for further processing. Event losses occur in a daisy-chained scheme if one or more slots contain an event during the same sync period. Only one event can be transmitted along the daisy chain in a single sync period, which requires any additional events to be discarded. These types of event losses are especially prevalent at higher count rates as more events occur per sync period, which increases the probability of events being discarded.
A need exists, therefore, for an event data transmission scheme for reducing PET event losses, employing a more effective use of available data bandwidth.

Method and apparatus for reducing positron emission tomography (PET) event losses by effective bandwidth utilization


An image forming device includes a developing unit, which is removably inserted in the image forming device, and the developing unit includes an accumulating chamber, a developing member, and a storage medium. The accumulating chamber accumulates developer. The developing member moves the developer onto an image carrier and carries out an image forming process. The storage medium stores control information for determining a developing bias to be applied to the developing member, and usage performance information of the developing unit necessary for determining the developing bias.

1. Field of the Invention
The present invention relates to an image forming device, such as a copy machine, a printer, and a facsimile machine, and a developing unit included in the image forming device.
2. Description of the Related Art
A well-known electrophotographic image forming device uses a photoconductive drum as an image carrier. By charging and exposing a surface of the photoconductive drum, an electrostatic latent image is formed on the surface of the photoconductive drum. Toner adheres onto the electrostatic latent image, and a visible image is formed. This visible image is transferred onto paper. In such an image forming device, components are unitized according to necessity, and this unit is removably inserted in the image forming device. When a replacement timing of the components arrives, the unit is replaced as appropriate. In particular, a developing unit containing the toner, which is consumable, is replaced when a remaining amount of the toner becomes low. The photoconductive drum and the developing unit may be integrally provided as one unit.
In order to accurately grasp the replacement timing of such a unit to be replaced, information indicating an arrival of the replacement timing is loaded in the unit. For example, according to a first conventional device, a unit includes a nonvolatile memory which stores identification data indicating a serial number of the unit and count data indicating a cumulative used time. Accordingly, the unit inserted in a main body of the image forming device can be distinguished. Each unit includes the memory which stores the used time associated with the identification data. According to a second conventional device, a cumulative number of images is stored in a main body memory of a printer main body and a memory of a cartridge. When the cartridge is inserted in the printer main body, the cumulative number of images stored in the memory of the cartridge is read and stored into the main body memory of the printer main body. A number of sheets on which an image forming process has been performed is added to the cumulative number of images stored in the main body memory. After the image forming process has been completed, the cumulative number of images stored in the main body memory is also stored into the memory of the cartridge.
In the above-described image forming device, although a plurality of types of replaceable developing units are used, there is a disadvantage that a developing bias applied to a developing roller of the developing unit cannot be controlled accurately. The toner accumulated in the developing unit is charged while being agitated, and the toner adheres onto the surface of the photoconductive drum by an electric potential difference between the developing roller and the photoconductive drum. If the developing bias applied to the developing roller is not set according to a charged amount of the toner, a normal developing process cannot be carried out. The charged amount of the toner tends to decrease accompanying a usage performance of the developing unit (for example, a cumulative used time and a cumulative number of sheets on which the image forming process has been performed by the developing unit). Therefore, the developing bias is also required to be changed accompanying this tendency. However, when the developing unit is replaced, a usage performance of the image forming device does not match with the usage performance of the inserted developing unit. Therefore, if the developing bias is controlled in accordance with the usage performance of the image forming device, the developing bias does not match with the usage performance of the developing unit. Thus, the normal developing process becomes difficult to be carried out.
In the case of the conventional developing unit, when the remaining amount of the toner in the developing unit becomes low, the developing unit is replaced. However, reusable components such as a frame portion and a roller shaft of the developing unit are reused. With regard to the developing roller arranged in the developing unit, when a replacement timing of the developing roller arrives, the developing roller is replaced with a different developing roller. In this case, when a developing roller having a different developing property is installed, control information relating to the developing bias stored in the image forming device is required to be rewritten according to the newly installed developing roller. As a result, there is a restriction when replacing the developing roller, and the developing unit cannot be recycled efficiently.

Developing unit, image forming device, and developing bias control method


To realize a mixer with a charge subsampling circuit with which a base band signal can be readily obtained without being affected by noise from wide bandwidth signals or undesired signals. A current generating circuit 8 outputs a current in proportion to the input signal voltage. In response to a control signal from the timing generating block 6, a charge subsampling circuit 7 samples the current at the same sampling frequency as the carrier frequency. In a charge-integrating process accompanying the sampling, weighting is carried out on terms in the transfer function of the FIR filter using a set of selected weights.

Bandpass FIR filter properties can be obtained with conventional charge sampling circuits by controlling the integration/non-integration of a current proportional to an input signal. See, for example, "A 50-MHz CMOS Quadrature Charge Sampling Circuit With 66-dB SFDR," S. Karvonen et al., IEEE International Symposium Circuits and Systems 2004, May 2004, Paper 11.5 (hereinafter, "non-patent document 1"). In a charge sampling circuit introduced in non-patent document 1, an input voltage is converted to current which is then stored in the form of electric charge by an integrator containing a capacitor and an amplifier. The storage period is controlled by a switch. Filtering becomes possible by alternatively turning on/off the switch according to a specified pattern. If a signal is sampled below the Nyquist frequency, aliased noise occurs in base band, degrading an SN ratio. In non-patent document 1, however, an input signal is sampled at a frequency beyond the Nyquist frequency and subjected to bandpass filtering before downsampling (decimation) to generate a low frequency output. In this instance, the frequency of a signal controlling the input switch is set to four times the frequency of the input signal. The output signal has a low frequency.
Non-patent document 1 introduces a scheme whereby a signal is subjected to Nyquist sampling after it is downconverted from a RF (carrier frequency) to a low frequency (IF). Before that circuit, a Gilbert mixer is needed for the RF-to-IF downconversion as in conventional art.
The scheme of non-patent document 1 attenuates the aliasing undesired signals caused by the downsampling by 18 dB. If one wants to apply the scheme to a tuner, a bandpass filter (BPF) with a sharp cutoff frequency profile needs be coupled to the input to filter out the undesired signals.
However, the charge sampling circuit of non-patent document 1 has a sampling frequency four times the carrier frequency. The circuit is difficult to make compliant with the latest communications standards which involve high carrier frequencies. There already exists a subsampling circuit which addresses these problems. The circuit implements subsampling below twice the carrier frequency. However, the sampling frequency should be higher than twice the maximum frequency of a base band signal based on which the carrier is modulated.
An example of the conventional charge subsampling mixer is shown in FIG. 21. See, for example, "A Discrete-Time Bluetooth Receiver in a 0.13 μm Digital CMOS Process," K. Muhammad et al., 2004 IEEE International Solid-State Circuits Conference, February 2004, Paper 15.1 (hereinafter, "non-patent document 2"). A charge subsampling mixer 100 in FIG. 21 includes a transconductance stage 101, an input switch 102, two paths path_a and path_b, and an output capacitor 111. The transconductance stage (hereinafter, "gm stage") 101 is a current source generating a current in proportion to the voltage value of a radio frequency ("RF") input signal supplied at the input terminal IN. The paths path_a and path_b process signals.
The path path_a includes a switch 103, an integrating capacitor 107, a reset switch 105, and an output switch 109. The switch 103 opens/closes the path. The reset switch 105 discharges the integrating capacitor 107. The output switch 109 allows/disallows a voltage in proportion to the charge stored in the integrating capacitor 107 to be applied to an output terminal OUT.The path path_b includes a switch 104, an integrating capacitor 108, a reset switch 106, and an output switch 109. The switch 104 opens/closes the path. The reset switch 106 discharges the integrating capacitor 108. The output switch 109 allows/disallows a voltage in proportion to the charge stored in the integrating capacitor 108 to be applied to an output terminal OUT.
FIG. 22 shows signal waveforms, from a control circuit (not shown), controlling the switches in the charge subsampling mixer 100. When the signal level is 1 in the figure, the associated switch turns on; when the signal level is 0, the associated switch turns off. A signal LO, controlling the input switch 102, consists of pulses at 50% duty factor at the same frequency as the carrier frequency for the RF input signal. This frequency is designated a basic sampling frequency Fs for the system. An equivalent basic period to the frequency, termed Ts, is given by
  Ts  =      1    Fs
Both a signal enable_a, controlling the switch 103 opening/closing the path path_a, and a signal enable_b, controlling the switch 104 opening/closing the path path_b, are a rectangular wave at a frequency of Fs/N where N is an integer greater than 1. The signals enable_a and enable_b are 1 for certain periods. To set the phase difference between the signals enable_a and enable_b to 180 degrees, the signal enable_b is off when the signal enable_a is on. When the signal enable_a (enable_b) for the path path_a (path_b) changes to 0, a signal out_a (out_b), controlling the output switch 109, changes to 1 and remains so for a period of N/2×Ts (=0.5×N/Fs). The signal reset_a controlling the reset switch 105, when the signal out_a (out_b) for the path path_a changes to 0, changes to 1 and remains so for a period of N/2×Ts (=0.5×N/Fs). The signal out_b controlling the output switch 110, when the signal enable_b for the path path_b changes to 0, changes to 1 and remains so for a period of N/2×Ts (=0.5×N/Fs). The signal reset_b controlling the reset switch 106, when the signal out_b for the path path_b changes to 0, changes to 1 and remains so for a period of N/2×Ts (=0.5×N/Fs).
The operational principles of the charge subsampling mixer 100 will be now described in reference to FIG. 23. When the signal enable_a is 1, if the signal LO changes to 1, the gm stage 101 supplies current to the integrating capacitor 107, changing a charge Qi stored in the integrating capacitor 107. The charge accumulated by the integrating capacitor 107 from time k×Ts to time (k+½)×Ts is given by
      Δ                                q      k        =                    ∫                  k          ·                      T            s                                                (                          k              +                              1                /                2                                      )                    ·                      T            s                                                      i                                (            t            )                                                                              ⅆ          t                      =                  ∫                  -          ∞                          +          ∞                                                        i                                      (              t              )                                ·                      γ                                      (                                                kT                  s                                -                t                            )                                                                                ⅆ          t                    where i(t) is the output current from the gm stage 101, and γ(t) is the basic waveform of the signal LO in FIG. 24. The expression states the correlation between i(t) and γ(t), which is given byΔqk=[i{circle around (x)}Γ](kTs)Taking the Fourier transform of the expression, we obtainΔQk(f)=Ic(f)·Γ(f)·e−j2π·f·kTs=Ic(f)·Γ(f)·z−k where Ic(f) and Γ(f) are the Fourier transforms of i(t) and γ(t) respectively. In the expression, z is given byz=ej2π·f·Ts
Γ(f) is given by
      Γ              (      f      )        =                    ⅇ                  j                                              T              s                        4                              2                                π            ·            f                                                                  ⅇ                          j                                                              T                  s                                4                                          2                                            π                ·                f                                              -                      ⅇ                                          -                j                                                                            T                  s                                4                                          2                                            π                ·                f                                                              j2π          ·          f                      =                  ⅇ                  j                                              T              s                        2                                          π            ·            f                                                      sin                                (                                          π                ·                f                                                                            T                  s                                2                                      )                                    π          ·          f
The sinus cardinal (hereinafter, "sin c") function is defined by
      sin                                c                    (        x        )              =            sin                    (        x        )              x
Using the sin c function, Γ(f) is given by
      Γ              (      f      )        =            ⅇ              j                                      T            s                    2                                  π          ·          f                                        T        s            2            sin                                c                    (                              π            ·            f                                                        T              s                        2                          )
From this expression, the Fourier transform of the charge accumulated from a time when LO changes to 1 to a time when it subsequently changes back to 0 is given by
      Δ                                Q      k        =            ⅇ              j                                      T            s                    2                                  π          ·          f                                        T        s            2            sin                                        c                          (                                    π              ·              f                                                                  T                s                            2                                )                    ·              Ic                          (          f          )                    ·              z                  -          k
While the signal enable_a is 1, the integrating capacitor 107 is charged N times. As the signal out_a changes to 1, the integrating capacitor 107 discharges completely. Furthermore, while the signal enable_b is 1, the integrating capacitor 108 is charged N times. As the signal out_b changes to 1, the integrating capacitor 108 discharges completely. In the waveform example in FIG. 22 (or FIG. 23), N=5. After the integrating capacitors 107, 108 output voltage, the reset signals reset_a and reset_b are changed to 1 to discharge the integrating capacitors 107, 108. The reset enables the capacitors 107, 108 to integrate from 0 every time. The charge stored in the capacitors 107, 108 is given byqout=Δq0+Δq1+Δq2+Δq3+Δq4 This is shown in FIG. 23. Using this expression, the Fourier transform of the output charge is given by
            Q      out                  (      f      )        =            ⅇ              j                                      T            s                    2                                  π          ·          f                                        T        s            2            sin                                        c                          (                                    π              ·              f                                                                  T                s                            2                                )                    ·      Ic                          (        f        )            ·              (                  1          +                      z                          -              1                                +                      z                          -              2                                +                      z                          -              3                                +                      z                          -              4                                      )
It is understood that the expression represents a property (transfer function) of an FIR (finite impulse response) filter: FIR=(1+z−1+z−2+z−3+z−4). Hence, an FIR filter is realized by integrating the charge which forms the output current of the gm stage 1010, and unwanted signals are removed using that FIR filter.
In addition, letting Ci represent the capacitance of the integrating capacitor, the output voltage Vout(f) is given by
            V      out                  (      f      )        =                    Q        out                          (        f        )                    C      i      The relationship between the current Ic and the input voltage Vin(f) is given byIc(f)=gm·Vin(f)where gm is the transconductance of the gm stage 101.
In addition, transferring the charge stored in the integrating capacitors 107, 108 to the output capacitor 111 causes charge sharing. Therefore, the output voltage Vo(f) of the output capacitor 111 is given by
            V      o                  (      f      )        =                    z                  -          N                            1        +                                            C              o                                      C              i                                                      (                          1              -                              z                                  -                  N                                                      )                                                  V        out                          (        f        )            where Co is the capacitance of the output capacitor 111. This transfer function is a property of an IIR (infinite impulse response) filter.
From the expression, the frequency characteristic of the output voltage Vo (f) is given by
            V      o                  (      f      )        =            gm              C        i                                T        s            2            sin                                        c                          (                                    π              ·              f                                                                  T                s                            2                                )                    ·      FIR      ·      IIR      ·                        V          in                                  (          f          )
The factor,
      ⅇ          j                              T          s                2                          π        ·        f              ,does not affect the gain and is therefore neglected in the expression. The factor however affects the phase.
The zero point frequency for the FIR filter is equal to the aliasing frequency, lowering aliasing noise. Effects will be described in reference to FIGS. 25(a) to 25(e). The horizontal axes of all the graphs in FIGS. 25(a) to 25(e) show frequency. The vertical axes of all the graphs, except FIG. 25(c), show signal power. The vertical axis in FIG. 25(c) shows a FIR gain standardized with a maximum FIR gain. FIG. 25(a) is a signal spectrum at the input terminal of the gm stage 101. The signal spectrum demonstrates a desired signal, or a carrier frequency Fs, and noise. Integrating charge by the capacitors 107, 108 and sampling at a sampling frequency Fs generates a discrete time signal in the bandwidth 1/N times the sampling frequency Fs, as shown in FIG. 25(b). The desired signal aliases to DC, all noise is aliased to the bandwidth from 0 to Fs. FIG. 25(c) shows an FIR filter property realized by charge integration and resetting of the capacitors 107, 108. FIG. 25(d) is the signal spectrum in FIG. 25(b) after it is filtered by the FIR filter. Noise is filtered out at Fs/N, 2Fs/N, and other frequencies. FIG. 25(e) shows the signal spectrum in FIG. 25(d) after it is downsampled (the signal spectrum at the output terminal OUT of the charge sampling mixer 100). Noise is aliased to the bandwidth from 0 to Fs/N, but not in the signal bandwidth. The signal in FIG. 25(e) can be demodulated to obtain a base band signal.
The foregoing description is applicable in the absence of undesired signals and when the desired signal has a narrow bandwidth. If the desired signal has a wide bandwidth, like television broadcast waves (both analog and digital), noise is less attenuated on the edges of the bandwidth, with noise being aliased to the bandwidth of the desired signal. Furthermore, undesired signals are aliased, appearing at higher frequencies than the desired signal. Effects of these phenomena will be described in reference to FIGS. 26(a) to 26(e).
FIGS. 26(a) to 26(e) correspond to FIGS. 25(a) to 25(e). FIG. 26(a) assumes the presence of an undesired signal in addition to the desired signal. FIG. 26(b) shows the undesired signal being aliased the same way as the noise in FIGS. 25(a) to 25(e). FIG. 26(d) shows the aliased undesired signal being attenuated by the FIR filter. However, if the desired signal has a wide bandwidth, the undesired signal is insufficiently attenuated on the edges of the bandwidth of the aliased signal. The aliased undesired signal still has high power as shown in FIG. 26(e), making it difficult to retrieve the desired base band signal. To further reduce undesired signal aliasing, a filter with a sharp cutoff frequency profile is needed at the input of the subsampling mixer.
Raising the order of the FIR may possibly attenuate the undesired signal. However, to raise the order of the FIR, the downsampling factor N needs be increased, which in turn will narrow down the output bandwidth Fs/N. The bandwidth needs be twice that of the desired signal, placing limits on the increase of N. Should N be sufficiently large, the order of the IIR increases due to charge sharing, resulting in different gains in the bandwidth.


A toilet ventilating system for use with a bowl incorporating a sewer line connection and including an upstanding vent conduit leading from the bowl rim outlets to an elevated cross over in the water storage tank and then dropping downwardly to form an exhaust conduit connected with the sewer connection. A centrifugal fan having a flow rate of 60 cubic feet per minute is incorporated in the vent conduit and a trap valve is incorporated in the cross over for selectively opening and closing communication between the vent conduit and the exhaust conduit. The trap valve incorporates a floating cylinder, positioning of which is controlled by water pumped from an elevated reservoir through a positive displacement pump. A controller is provided for controlling the positive displacement pump to open the trap valve, actuation of the centrifugal fan and closure of the trap valve, deactuation of the fan and actuation of the flush valve.

1.Field of the Invention
The present invention relates to a ventilation system incorporated in a toilet to remove offensive odors during use to be dispensed directly to the sewer line.
2. Description of the Prior Art
Modern day bathrooms often incorporate high volume exhaust fans connected either in parallel with the light switch or connected with a separate exhaust fan operating switch for actuation thereof to remove offensive odors during use of the toilet. The shortcomings of such exhaust systems has long been recognized. By their very nature, bathrooms typically fill with offensive odors during use. Such odors are only partially withdrawn therefrom during any reasonable period of exhaust fan operation. Thus, when the bathroom door is opened or another user subsequently enters, offensive odors often remain thus leaving a socially embarrassing situation. Recognition of these shortcomings in conventional exhaust systems has led to the proposal of numerous different exhaust or ventilating devices to be incorporated directly in the toilet bowl in effort to provide for direct exhaust to either the atmosphere or directly to the sewer system.
One such device proposed contemplated a serpentine construction of multiple air traps formed in conduits installed in the water storage tank and operated by means of a complicated venting and drainage system requiring flow of control air through air control valves under influence of a water jet. A device of this type is shown in U.S. Pat. No. 3,579,650 to Sloan. Such an arrangement, while satisfactory for selected situations, suffers the shortcoming that the flush water must pass through a vent tube and that the air control valves serves to choke air flow thus severely limiting the volume of exhaust air available during use.
Other efforts have led to the proposal of custom design toilet bowls with rather complicated conduit arrangements and incorporating a secondary water storage tank with control elements therein. Such devices provide for a blower to be connected to the sewer upstream of a trap valve. A device of this type is shown in U.S. Pat. No. 4,800,596 to Menge. While satisfactory for some applications, systems of this type suffer the shortcoming that the toilet bowl construction required is rather complex and expensive to manufacture and requires a storage tank having an unacceptably high profile. Furthermore, in a design of this type the water trap is not utilized as the first barrier to the sewer. The assurance of a leak-free system is wasted by having placed the blower between the sewer line and the water trap. Moreover, the control systems utilized in this type are dependent on the availability of water pressure in the water main thus rendering such devices inoperable when water pressure is low or non-existent.
Other efforts to provide a satisfactory exhaust system have led to the proposal of another custom styled toilet bowl construction, mounting a water storage tank requiring a pneumatic seal for proper operation and which vents exhaust gases to the atmosphere. A device of this type is shown in U.S Pat. No. 5,029,346 to Fernald. While providing some improvement in operation, devices of this type suffer the shortcoming that the toil bowl construction is relatively expensive to manufacture and the use of the tank's overflow tube as an exhaust conduit severely limits airflow due to its small cross-section resulting in residual offensive odors remaining even after operation.
Thus, there exists a need for a toilet bowl ventilating system which provides for a high volume of exhaust air flow during use to be introduced directly to the sewer line and which will positively close off communication with such sewer line during the flush cycle and during any remedial household measures taken to rectify plugging of the sewer line as by application of conventional household plungers to the drain from the toilet bowl.


A method and apparatus is provided to implement rapid reconfiguration during either a full, or partial, reconfiguration of a programmable logic device (PLD). Rapid reconfiguration is facilitated by a massively parallel configuration data bus that is created to simultaneously reconfigure the entire height of a reconfiguration memory space. A direct link may be provided to the configuration memory space of the PLD by utilizing interconnect and input/output resources to form the massively parallel configuration data bus. An indirect link may also be provided to the entire configuration memory space by utilizing existing random access memory (RAM) resources within the PLD as configuration bitstream buffers.

PLDs are a well-known type of integrated circuit that may be programmed to perform specified logic functions. One type of PLD, the Field Programmable Gate Array (FPGA), typically includes an array of programmable tiles. These programmable tiles can include, for example, Input/Output Blocks (IOBs), Configurable Logic Blocks (CLBs), dedicated Random Access Memory Blocks (BRAM), multipliers, Digital Signal Processing blocks (DSPs), processors, clock managers, Delay Lock Loops (DLLs), Multi-Gigabit Transceivers (MGTs) and so forth.
Each programmable tile typically includes both programmable interconnect and programmable logic. The programmable interconnect typically includes a large number of interconnect lines of varying lengths interconnected by Programmable Interconnect Points (PIPs). The programmable logic implements the logic of a user design using programmable elements that may include, for example, function generators, registers, arithmetic logic, and so forth.
The programmable interconnect and the programmable logic are typically programmed by loading a stream of configuration data into internal configuration memory cells that define how the programmable elements are configured. The configuration data may be read from memory (e.g., from an external PROM) or written into the FPGA by an external device. The collective states of the individual memory cells then determine the function of the FPGA.
Another type of PLD is the Complex Programmable Logic Device, or CPLD. A CPLD includes two or more "function blocks" connected together and to input/output (I/O) resources by an interconnect switch matrix. Each function block of the CPLD includes a two-level AND/OR structure similar to those used in Programmable Logic Arrays (PLAs) and Programmable Array Logic (PAL) devices. In CPLDs, configuration data is typically stored on-chip in non-volatile memory. In some CPLDs, configuration data is stored on-chip in non-volatile memory, then downloaded to volatile memory as part of an initial configuration (programming) sequence.
For all of these PLDs, the functionality of the device is controlled by configuration data bits provided to the device for that purpose. The configuration data bits can be stored in volatile memory (e.g., static memory cells, as in FPGAs and some CPLDs), in non-volatile memory (e.g., FLASH memory, as in some CPLDs), or in any other type of memory cell.
Some PLDs, such as the Xilinx Virtex® FPGA, can be programmed to incorporate blocks with pre-designed functionalities, i.e., "cores". A core can include a predetermined set of configuration data bits that program the FPGA to perform one or more functions. Alternatively, a core can include source code or schematics that describe the logic and connectivity of a design. Typical cores can provide, but are not limited to, DSP functions, memories, storage elements, and math functions. Some cores include an optimally floor planned layout targeted to a specific family of FPGAs. Cores can also be parameterizable, i.e., allowing the user to enter parameters to activate or change certain core functionality.
Configuration, and/or full, or partial, reconfiguration of a PLD may be facilitated through dedicated configuration ports, and associated configuration control logic, which are tailored for ease of use, low cost, high flexibility, and backward compatibility. While these configuration ports provide adequate performance during configuration events that are not time critical, they are nevertheless inadequate for configuration events that are time critical.
A conventional configuration event of a PLD is one that is performed on the entire PLD after power-up. A full reconfiguration event, on the other hand, is one that is performed subsequent to a conventional configuration event.
A partial reconfiguration event may be accomplished subsequent to a conventional, or any type of reconfiguration, event, whereby only a portion of the PLD is reconfigured, while other portions of the PLD retain their current configuration. A partial reconfiguration event may also be accomplished dynamically, whereby the other portions of the PLD that retain their current configuration also remain active during reconfiguration of a portion of the PLD.
Each of the reconfiguration events, as discussed above however, are inadequate for time critical applications. For example, dynamic computing applications often require software controlled logic reconfiguration within hundreds of microseconds. Using known configuration techniques, however, the amount of time required for a typical reconfiguration event exceeds the dynamic computing requirements by at least an order of magnitude. That is to say, in other words, that the amount of time required to reconfigure a typical module during a partial reconfiguration event is on the order of several milliseconds, which is inadequate for dynamic computing applications.
One method to decrease the amount of time required for a reconfiguration event is to increase the dedicated configuration port's data width and the dedicated configuration port's data propagation rate. Such a method, however, would likely fail to decrease the amount of reconfiguration time to an acceptable level. Furthermore, such a method would increase the amount of dedicated configuration logic required within the PLD to support the increased configuration port width. Efforts continue, therefore, to obtain significant reduction in the amount of time required to complete a reconfiguration event.

Apparatus and method for reconfiguring a programmable logic device


Systems and methods are provided for detecting anomalous messages on a multipoint serial communications bus by extracting features from a first and a second message, including a time delay between the first and the second messages and, for each message, a sender address, a recipient address, a bus number, and a word count. A message transition pattern including the extracted features is generated. A probability of occurrence of the message transition pattern is determined by comparing the message transition pattern to a pattern dictionary, and the second message is determined to be anomalous when the probability is less than a predetermined threshold.

A Man-in-the-Middle (MitM) attack is a cyber-attack in which an attacker intercepts computer network traffic, impairing the confidentiality, integrity, and availability of the network. In an MitM attack, an attacker may eavesdrop on a communications channel between two or more endpoints, and may also manipulate and insert malicious traffic into the channel.
A MITM intrusion into a local area network (LAN) can be achieved by connecting a MITM device to a public Wi-Fi access point (for example, at a public café or airport), or by connecting the device physically to an exposed network cable or network switch. Malware may also be used to gain control of a trusted computer, which may then be exploited for MITM attacks.
After intruding into a LAN, a MITM device may intercept traffic through several known methods, such as corrupting a host's address resolution protocol (ARP) table or spoofing a domain name server (DNS). The ARP vulnerability gives an attacker the ability to spread spoofed ARP messages, causing network traffic to be routed to the MITM device. In general, solutions to MITM attacks on LANs have addressed specific flaws in a single protocol and are therefore difficult to generalize to other known or unknown attacks. Intrusion Detection Systems (IDS) have been proposed that combine both hardware and software, such as an add-on component plugged into a mirror port of a network switch. However, such solutions may not perform well against some MITM attacks, such as an active wiretap that acts as a network bridge, leaving no forensic evidence in packets that traverse it.

Echo detection of Man-in-the-Middle LAN attacks

B. G. NEGEV TECHNOLOGIES AND APPLICATIONS LTD.


A method for generating tokens for use in an email-based e-commerce transaction between third party vendor and a customer that is facilitated by a payment server is disclosed. The method may comprise generating a token for use with an email checkout, wherein the token comprises a customer name, and customer email address. The processor may generate an email message for at least one recipient, the email message including a mailto hyperlink including the token, wherein the mailto hyperlink generates an email response message addressed to the payment server including the token. The method may comprise receiving a notification from the payment server indicating that the at least one recipient that the email response message was successfully received by the payment server and the email-based e-commerce transaction is successful.

Vendors wishing to adopt an email-based payment method may need to integrate their own system with a third party system to use the email payment process. An email payment system may demand a close integration between the vendor and the e-commerce system. This setup may be time consuming and cumbersome for the vendor.
In designing an email payment system, problems may arise when the user base begins to scale the system to accommodate more users. The communication between the gateway and the vendor may be considerable depending on the size of the customer base and the array of offers. Larger numbers may use more bandwidth. Many online businesses' profits are dependent on the ability to scale their customer base. Any system that enters the marketplace must take into account large numbers of users. A system that would require the use of less bandwidth would be advantageous.
Online security is a concern for any vendor. Additionally, there are often security concerns since these third party systems are not located on the vendor's system. When adopting new systems many vendors prefer systems that allow them autonomy. Limiting the amount of communication between systems that may be communicating encrypted data over public networks reduces potential interference from outside parties. A process integrated directly in the vendor's system may reduce exposure.
Email-based payment systems contend with customers that are more familiar with web-based payment systems. Consumers expect to visit a URL to check out of merchandise. A two-click web URL checkout may be a desirable service for a vendor to provide to a client. The implementation of a tool that may generate tokens for web and email-based checkout may be desirable.


A method for facilitating greenhouse gas emission control in an enterprise is disclosed herein. In one embodiment, such a method may include taking an inventory of GHG-producing assets of an enterprise and monitoring the GHG emission rate for each of the GHG-producing assets. If the GHG emission rate for a specific GHG-producing asset exceeds a specified rate limit, or if the growth rate of the GHG emission rate for the specific GHG-producing asset exceeds a specified growth rate limit, maintenance may be automatically scheduled for that GHG-producing asset.

The invention relates to asset management systems, and more particularly, to asset management systems for tracking, storing, and utilizing greenhouse gas emission information to facilitate reductions in greenhouse gas emissions.
For the past several hundred years, increasing deforestation and burning of fossil fuels, such as coal and oil, have resulted in an extreme increase in the concentrations of heat-trapping "greenhouse gases" in our atmosphere. The implications of this rise in greenhouse gases have recently been brought to the forefront by political and environmental initiatives.
The Intergovernmental Panel on Climate Change ("IPCC"), a scientific intergovernmental body tasked with evaluating the risk of climate change, has concluded that most of the observed temperature increase since the middle of the twentieth century is very likely due to increased concentrations of greenhouse gases resulting from human activity. Consumers have since become more selective in purchasing "green" products having a reduced impact on greenhouse gas emissions and climate change. In turn, large corporations and industries increasingly strive to offer more ecologically-sound products and industrial processes to comply with environmental regulations and to remain competitive in the global market.
To track national trends in emissions and removals since 1990, the U.S. Environmental Protection Agency ("EPA") develops the official U.S. greenhouse gas inventory each year. In addition to the U.S. inventory, greenhouse gas ("GHG") emissions can be tracked at global, state, and local levels, as well as by companies and individuals, according to known methods. This information may be used to facilitate targeted reduction in actual GHG emissions, as well as to facilitate emissions trading and other GHG emission-limiting practices, such as those promoted by the Kyoto Protocol.
What are needed are apparatus and methods for efficiently gathering and using GHG emission information to reduce current and/or future GHG emissions.

Asset management system to monitor and control greenhouse gas emissions

International Business Machines Corporation


Embodiments of the invention provide a color filter substrate and a manufacturing method for the same, and a display device. The color filter substrate comprises a plurality of spacers. The spacer has a cross-sectional shape in a direction parallel to the color filter substrate, and the cross-sectional shape including a first supporting portion extending along a first direction and a second supporting portion extending along a second direction, which is connected to an end portion of the first supporting portion, the first direction being perpendicular to the second direction.

A Thin Film Transistor Liquid Crystal Display (TFT-LCD), as a flat-panel display device, is more frequently applied to a high-performance display field, due to characteristics such as small size, low power consumption, no radiation and relatively low production cost.
The TFT-LCD, as illustrated in FIG. 1a, consists of an array substrate 10 and a color filter substrate 11. Liquid crystal is filled between the array substrate 10 and the color filter substrate 11. In order to control stability of a thickness of a liquid crystal layer, a spacer 30 may be disposed between the array substrate 10 and the color filter substrate 11.
Specifically, as illustrated in FIG. 1a, before cell-assembling the color filter substrate 11 and the array substrate 10, a plurality of spherical spacers 30 prepared and molded in advance may be sprayed onto preset regions of a surface of the color filter substrate 11, then the cell-assembling process of the array substrate 10 and the color filter substrate 11 is performed, and finally a display device as illustrated in FIG. 1a is formed. The above-described preset regions correspond to a non-display region on the array substrate. However, the spherical spacers 30 are prone to roll. Therefore, positional deviation will occur, such that during the spraying process, some of the spherical spacers 30 are located outside the preset regions, thereby affecting an aperture ratio of the display device. In order to solve the above problem, in the prior art, cylindrical spacers are formed within the preset regions on the surface of the color filter substrate 11, so that positions of the spacers are fixed.
However, researchers find that, when a resistance test such as a pressure test, a thinning process and a polishing process is performed on the display panel constituted by the spherical or cylindrical spacers 30, or when a pressing operation or a sliding operation is performed on the display screen in use, the above spacers 30 may distort, rapture or slip because they are subjected to pressure or shearing force. In this way, debris of the damaged spacers 30, under an action of an external force, may enter the display region of the display panel, thereby causing display defect. And when the display panel is subjected to an external pressure, the panel may be dented due to insufficient restoring force of the damaged spacers 30, so that a light transmission path of a backlight will be changed, affecting grey scale of display, which further leads to uneven display of the display panel, and renders undesirable phenomena such as water ripples.

Color filter substrate and manufacturing method for the same, and display device

BEIJING BOE OPTOELECTRONICS TECHNOLOGY CO., LTD.


The present invention relates to a vaccine composition against the infection of human respiratory syncytial virus (RSV) comprising a replication-defective recombinant adenovirus carrying a nucleotide sequence encoding the F protein of RSV or fragment thereof. A method of preventing RSV infection-related diseases using the vaccine composition of the present invention is also provided.

Respiratory syncytial virus (RSV) is a single-stranded, negative sense RNA pleomorphic enveloped Pneumovirus of the Paramyxoviruidae family. Human RSV genome contains eight structural genes and two non-structural genes, wherein the major genes code for the attachment glycoprotein (G protein), the fusion protein (F protein), and a small hydrophobic envelope protein (SH protein), respectively.
The infection of RSV would lead to the induction of both humoral and cellular immune responses directed against the virus. It was proved in several studies in animal models that the RSV-specific neutralizing antibodies and cytotoxic lymphocytes (CTLs) contributed to a protection against RSV infection and/or diseases. For example, it was reported that RSV-specific antibodies played an important role in prevention from the RSV infection in terms of the protective efficacy of the passive transfer of immune sera containing RSV-specific antibodies of unvaccinated mice challenged by a live RSV (Graham et al., Immunoprophylaxis and immunotherapy of respiratory syncytial virus-infected mice with respiratory syncytial virus-specific immune serum; Pediatr Res 1993 August; 34(2):167-72). It was also reported that RSV-specific CTLs were detected more readily in adults who developed mild symptoms due to RSV infection exposure (Isaacs D., Viral subunit vaccines; Lancet 1991 May 18; 337(8751): 1223-4).
It was evidenced that F protein of RSV as target of vaccine antigen was better than G protein of RSV because the recombinant vaccinia virus expressing the G protein of RSV (vacvG) enhanced pulmonary eosinophilia upon RSV infection of mice (as reported in, for example, Openshaw et al., Pulmonary eosinophilic response to respiratory syncytial virus infection in mice sensitized to the major surface glycoprotein G; Int Immunol 1992 April; 4(4):493-500). However, it was also reported that Th-2 type response to RSV infection after F1-RSV-vaccination (a vaccination with the F1 subunit of F protein of RSV) played a role in an abnormal response, characterized by extensive eosinophils increasing in the blood, wheezing, and hyper reactive airways (Kim et al., Respiratory syncytial virus disease in infants despite prior administration of antigenic inactivated vaccine; Am J Epidemiol 1969 April; 89(4):422-34), and that the Th2-associated cytokines IL-4 and IL-13 both promoted the development of pulmonary eosinophilia (Johnson and Graham, Secreted respiratory syncytial virus G glycoprotein induces interleukin-5 (IL-5), IL-13, and eosinophilia by an IL-4-independent mechanism; J Virol 1999 October; 73(10):8485-95; and Johnson et al., IL-13 is sufficient for respiratory syncytial virus G glycoprotein-induced eosinophilia after respiratory syncytial virus challenge; J Immunol 2003 Feb. 15; 170(4):2037-45).
Given the above, it is still desired to develop a new vaccine for prevention against the RSV infection or the vaccine-enhanced diseases without undesired side effects, such as eosinophilia.

Human respiratory syncytial virus (RSV) vaccine


A cover assembly for a floor box including an access door for covering at least a portion of the floor box. The access door includes an opening for passage of at least one cord therethrough. The cover assembly further includes a cord door positioned to cover the opening in the access door. The cord door is removeably securable to the access door in at least two mounting orientations.

This invention pertains to floor boxes which house power and communication wires for termination and, more particularly, to a cover assembly having a smaller cord door that can be re-positioned as needed.
It is well-known to run electrical wires and telecommunications wires underneath the surface of a floor. These cables and electrical systems may be placed under the floor surface so as to be more efficient in supplying power and data/telecommunication signals in commercial buildings. The electrical cables or wires beneath the floor may be accessed through a hole in the surface of the floor. In order to provide convenient access to the wires or cables as well as the termination devices which terminate the wires, a floor box is typically placed in the hole through the floor.
Floor boxes are typically made of metallic material so that they are resistant to the outside elements, such as moisture, and are also strong enough to maintain the structural integrity of the floor. The cover used on these floor boxes oftentimes varies depending on the type of flooring to be employed, i.e. wood, tile, exposed concrete, and the like. Such covers oftentimes incorporate a smaller cord door that is used after the building is completed in order to allow wires to extend from the floor box through the cord door and to the device being powered or communicated with.
However, during construction, the exact placement of such devices is not known. Thus, it is common to find the cord door in an inconvenient/improper orientation following the installation process. Also, once the building is completed, it is quite common for the building layout to change over time and thus these powered or communicated devices will be moved to yet another location. Thus, the cover on these floor boxes will need to be adjusted once again to take into account the new location of these devices. Further, it is common for the building layout to require a new or different type of cover to be employed, such as one requiring connection to a flexible conduit. Hence the floor box and/or its cover may need to be altered accordingly.
In the past, when such a situation was encountered, it became necessary for the entire cover of the embedded floor box to be separated from the box. The cover would then be rotated (if possible) so as to properly position the smaller cord door to open in the desired direction. This required the removal of the flooring material surrounding the floor box (and oftentimes beyond) so that the fasteners securing the cover to the box could be accessed. In some cases, concrete had to be removed if the pour extended over these fasteners. Also, removal and replacement of this flooring material is costly and hence, in many situations, the cost and effort of re-positioning the cover was not deemed worth the effort.
Also, even if worth the effort of re-positioning the cover, some boxes may not permit this because the cover may only be secured to the box in one orientation. Alternatively, the box may not be square and hence the cover may only be able to be rotated 180 degrees and not 90 degrees which may be the desired cord door opening direction. Furthermore, even if the box is of some other shape that can accommodate a rotatable cover, the fastener locations may not be in alignment so that even if the box can accommodate a re-positioned cover, the fasteners cannot.
Regardless of the need required of the floor box and its cover, the design must also be adequate enough to support the weight and loading that a typical floor box is subject to and the floor box assembly must still comply with all local and national codes and or specifications pertaining to floor boxes.
It is thus an object of this invention to provide a floor box cover that incorporates a smaller cord door therein. Another object of this invention is to provide a floor box that complies with all local and national codes and specifications. A further object of this invention is to provide a floor box with a cord door such that the cord door can be adjusted so as to open in the desired direction without having to re-position or re-orient the entire cover. Still another object of this invention is to provide a cord door that can be removed and re-positioned as needed and further that can be replaced with another different cover plate if the need to do so arises. These and other objects and advantages of this invention will become evident upon further review.

Cover assembly for an electrical floor box


An NTSC compatible, single broadcast channel, widescreen EDTV system encodes and decodes a television signal comprising four components: (1) a main, standard format NTSC signal with low frequency side panel image information compressed into the overscan regions thereof; (2) time expanded high frequency side panel image information; (3) extended high frequency horizontal luminance image information; and (4) vertical-temporal luminance image information. Components (2) and (3) are intraframe averaged and quadrature modulate an alternate subcarrier, e.g., at 3.108 MHz, to produce a modulated signal. The modulated signal is summed with component (1) after intraframe averaging to produce an NTSC compatible 4.2 MHz baseband signal. This signal and component (4) quadrature modulate an RF picture carrier to produce an NTSC compatible RF broadcast signal for transmission via a single broadcast channel.

This invention concerns a widescreen extended definition television (EDTV) system which is operable with a single broadcast channel and which is compatible with conventional television receivers having a relatively smaller display aspect ratio.
A conventional television receiver, such as a receiver in accordance with NTSC broadcast standards adopted in the United States and elsewhere, has a 4:3 aspect ratio (the ratio of the width to the height of a displayed image). Recently, there has been interest in using higher aspect ratios for television receiver systems, such as 2:1, 16:9 or 5:3, since such higher aspect ratios more nearly approximate or equal the aspect ratio of the human eye than does the 4:3 aspect ratio of a conventional television receiver. Video information signals with a 5:3 aspect ratio have received particular attention since this ratio approximates that of motion picture film, and thus such signals can be transmitted and received without cropping the image information. However, widescreen television systems which simply transmit signals having an increased aspect ratio as compared to conventional systems are incompatible with conventional aspect ratio receivers. This makes widespread adoption of widescreen systems difficult.
It is therefore desirable to have a widescreen system which is compatible with conventional television receivers. One such system is disclosed in a copending U.S. patent application of C. H. Strolle et al., Ser. No. 078,150 titled "Compatible Widescreen Television System", filed July 27, 1987.
It is even more desirable to have such a compatible widescreen system with provisions for enhancing or extending the definition of the displayed image so as to provide extra image detail. For example, such widescreen EDTV (extended definition television) system may include apparatus for providing a progressively scanned image.
In accordance with the principles of the present invention, there are disclosed herein method and apparatus for encoding and decoding a compatible EDTV widescreen video signal representing a high resolution picture with an aspect ratio greater than the standard 4:3 aspect ratio, suitable for transmission via a single standard broadcast channel.

Extended definition widescreen television signal processing system


A computer-implemented method for visualizing a playback plan of a hypervideo, the hypervideo comprising a plurality of video segments from a plurality of videos linked together using a plurality of links, the method being performed in connection with a computerized system comprising a central processing unit, a display device and a memory, the computer-implemented method involving: generating the playback plan for an automated playback of the hypervideo, the automated playback comprising automatically following the plurality of links linking the plurality of video segments such that at least some of the plurality of video segments are played in a predetermined sequence, wherein the plurality of links are followed based on the playback plan; and generating a graphical user interface portion on the display device for visualizing the playback plan.

Technical Field
The disclosed embodiments relate in general to techniques for automating hypervideo playback and, more specifically, to systems and methods for visualizing playback plans of hypermeetings.
Description of the Related Art
Meetings are an important part of collaborative activities but are difficult to schedule, particularly when a set of collaborators is spread across multiple locations and time zones. Additionally, meetings often overlap in terms of content. This can cause difficulties as meetings that build on what was discussed in prior meetings result in barriers for those not at prior meetings and meetings that re-discuss topics are often viewed as unproductive by the participants that were at prior meetings.
Meetings with asynchronous participation are desired but currently not well supported. Systems either treat the original meeting as a series of independent discussions, losing their interconnections, or they record everything putting the onus of locating and responding to discussion on participants. U.S. patent application Ser. No. 14/574,386 describes a solution for recording multiple asynchronous meetings by representing a series of meetings in a form of navigable video recordings called a hypervideo. The hypervideo consists of several video segments that are linked together using links.
As would be appreciated by persons of ordinary skill in the art, such hypervideos may be displayed in many different ways. While manual link following is possible, automatic link following and other assisted navigation to support the viewer in seeing relevant parts of the hypervideo in the appropriate order during hypervideo playback would be desirable. Additionally desirable would be a system that would provide visualizations of playback sequences of video segments in hypervideo.

Systems and methods for visualizing playback plans of hypermeetings


A maximum voltage selection circuit and method and a sub-selection circuit are provided. The maximum voltage selection circuit includes a peripheral signal circuit and a selection circuit with N channels of input voltages. The peripheral signal circuit provides an operating mode signal and a reference voltage to the selection circuit including N sub-selection circuits coupled to the N channels of input voltages respectively. A sub-selection circuit determines its operating mode according to the operating mode signal. In the operating mode, when an input voltage of a sub-selection circuit is larger than the reference voltage, the sub-selection circuit sets itself to the output enable state and sets other sub-selection circuits to the output disable state, and outputs its input voltage as a maximum voltage through a PMOS.

A maximum voltage selection circuit is generally required in an integrated circuit. The main function of the maximum voltage selection circuit is to select and output a maximum voltage from a plurality of existing voltages to supply other circuits in the integrated circuit.
FIG. 1 is a maximum voltage selection circuit with three channels of voltages. As shown in FIG. 1, when the differences in voltage between a first input voltage VCC1, a second input voltage VCC2 and a third input voltage VCC3 are relatively large, the maximum voltage selection circuit can select a maximum voltage as an output voltage VMAX. However, since generally, neither of the first input voltage VCC1, the second input voltage VCC2 and the third input voltage VCC3 is zero volts, a gate connection of a P-type metal oxide semiconductor field effect transistor (PMOS) connected to one of the first input voltage VCC1, the second input voltage VCC2 or the third input voltage VCC3 may have inadequate driving capacity to provide the output voltage VMAX at the output of the maximum voltage selection circuit. Additionally, when the voltage differences between the first input voltage VCC1, the second input voltage VCC2 and the third input voltage VCC3 are relatively small or the voltages are the same, the PMOS devices in the maximum voltage selection circuit may not operate normally may not generate the output voltage VMAX.

Maximum voltage selection circuit and method and sub-selection circuit


A ducted fan core for an unmanned aerial vehicle is provided that accommodates a wide variety of payloads. The ducted fan core comprises a frame, attached to which are an engine, gearbox assembly, fan, and a plurality of control vanes. A first surface on the frame comprises a plurality of connects or electrical traces. The plurality of connects are used to removably attach a variety of pods carrying various payloads. Thus, a wide variety of payloads may be delivered using the same unmanned aerial vehicle, simply by removing and attaching different pods to a fixed vehicle core. These pods may be shaped so as to form part of the vehicle exterior, and when the pods are attached to the frame, they enhance the aerodynamics of the vehicle.

Unmanned aerial vehicles ("UAVs") are remotely piloted or self-piloted aircraft that can carry cameras, sensors, communications equipment, or other payloads. A UAV is capable of controlled, sustained, level flight and is powered by either a jet or an engine. The UAVs may be remotely controlled or may fly autonomously based on pre-programmed flight plans or more complex dynamic automation systems.
UAVs have become increasingly used for various applications where the use of manned flight vehicles is not appropriate or is not feasible. Such applications may include military situations, such as surveillance, reconnaissance, target acquisition, data acquisition, communications relay, decoy, harassment, or supply flights. These vehicles are also used in a growing number of civilian applications, such as firefighting when a human observer would be at risk, police observation of civil disturbances or crime scenes, reconnaissance support in natural disasters, and scientific research, such as collecting data from within a hurricane.
Currently, a wide variety of UAV shapes, sizes, and configurations exist. Typically it is the payload of the aircraft that is the desired product, not the aircraft itself. A payload is what the aircraft is carrying. UAVs are the delivery system for a payload and are developed to fill a particular application and a set of requirements. As previously mentioned, there are numerous applications for which a UAV may be used. For each new application, a different type of payload may be used. Because different payloads may require different processing capabilities, or may comprise different sizes, a variation of the UAV typically must be developed for each type of payload, or a completely new aircraft typically must be designed. Designing a new aircraft or developing a variation of the current UAV in use is time-consuming and costly.

Ducted fan core for use with an unmanned aerial vehicle