text:
Publication number | US4818901 A |
Publication type | Grant |
Application number | US 07/075,641 |
Publication date | Apr 4, 1989 |
Filing date | Jul 20, 1987 |
Priority date | Jul 20, 1987 |
Fee status | Paid |
Publication number | 07075641, 075641, US 4818901 A, US 4818901A, US-A-4818901, US4818901 A, US4818901A |
Inventors | William R. Young, Harold D. Davidson |
Original Assignee | Harris Corporation |
Export Citation | BiBTeX, EndNote, RefMan |
Patent Citations (11), Referenced by (78), Classifications (18), Legal Events (7) | |
External Links: USPTO, USPTO Assignment, Espacenet | |
The present invention relates generally to buffers and more specifically to an improved CMOS output buffer.
CMOS buffers generally include a pair of complementary MOS transistors having a conduction path connected in series between a pair of power terminals and the output being at the junction of the two transistors. The output transistors act as a current source or sink and must drive a generally capacitive load. Using this structure, the current available during switching typically is continuously changing. The maximum current occurs when the device is in its saturated region, once in the linear range the control current decreases as the voltage across the output device decreases. This change in output current requires a higher peak current than if the device delivered a constant current for the same switching time.
An effort to increase the speed of switching while dissipating less power and providing symmetrical rise and falls has been addressed in level shifting circuits as illustrated in U.S. Pat. No. 4,450,371 to Bismarck. A large device capable of carrying a lot of current is switched on at the beginning of the transition to quickly supply current to the output and is then switched off as the output approaches the appropriate output level. These devices are in parallel with smaller high-ON-impedance load devices.
One method of stabilizing the maximum output current that we initially derived is to convert the simple output inverter structure into switched current sources as illustrated in FIG. 1. Transistors Q1 and Q3 and transistors Q2 and Q4 form current mirrors with the output devices Q1 and Q2 being the output leg of the current mirrors. The problem with the current source approach of FIG. 1 is that as the output voltage VO approaches either of the power terminals V+ or ground, the power in the output transistors Q1 and Q2 approach zero. However, an internal DC power still occurs.
The object of the present invention is to operate the output transistor at a controlled current capacity during switching without an accompanying power dissipation at steady state.
This and other objects of the invention are attained by controlling the output transistor of the buffer to operate in a constant current mode in response to an input signal transition of the buffer and subsequently operating the output transistor in a constant voltage mode when the output signal approaches the desired output level. The output transistor is controlled by limiting the voltage applied to its gate until the output signal approaches a desired output voltage, then the maximum supply voltage is applied to the gate. The voltage limiting can be provided by either a voltage divider or using the output transistor as the output leg of a current mirror which is activated by the input signal transition to drive the output transistor in a constant current mode and deactivated by the output signal approaching the desired output level.
The voltage divider limits the gate-to-source voltage and thereby drives the output transistor in a saturated mode. Once the output reaches a desired level, the voltage divider is disabled and a constant voltage is applied to the gate to drive the output transistor in its linear region. The voltage divider may include a resistor and series connected switch responsive to input signal to activate the voltage divider and a second resistance/switch which is controlled by the output signal to perform the activation and deactivation of the voltage divider.
In the current mirror embodiment a switchable current source is responsive to the input signal transition to provide an input current to the current mirror and includes a series switch in the input leg to disconnect the input leg from a power terminal to disrupt the current source and drive the output transistor with a constant voltage.
In response to an opposite input signal transition, the two ends of the voltage divider or the input leg of the current mirror are connected to the same power terminals to prevent drive of the output transistor. An additional switching element may be provided directly to the control gate of the output transistor and being responsive to the input signal to quickly turn the output transistor off.
The buffer may have a complementary pair of output devices each being responsive to an opposite transition so as to be operated in a constant current mode during the initial stage and in a constant voltage mode as the output approaches a desired output level. Interconnecting logic may be provided to prevent activation of one of the output transistors until the other has been turned off. Input latches and tri-state control may also be provided as part of the input logic.
Other objects, advantages and novel features of the present invention will become apparent from the following detailed description of the invention when considered in conjunction with the accompanying drawings.
FIG. 1 is a schematic of a switched current source buffer.
FIG. 2 is a schematic of a current mirror embodiment of a buffer incorporating the principles of the present invention.
FIG. 3 is a schematic of a voltage divider embodiment of a buffer incorporating the principles of the present invention.
FIG. 4 is a schematic of another embodiment of a current mirror of a buffer with quick turn-off incorporating the principles of the present invention.
FIG. 5 is a schematic of a current mirror embodiment with quick turn-off for a single polarity buffer incorporating the principles of the present invention.
FIG. 6 is a graph of the output signal comparing a bipolar buffer to a CMOS buffer equivalent to that in FIG. 5.
FIG. 7 is a schematic of another embodiment of a voltage divider buffer with quick turn-off according to the principles of the present invention.
FIG. 8 is a schematic of another current mirror embodiment with quick turn-off and delayed turn-on actuation according to the principles of the present invention.
FIG. 9 is another embodiment of a current mirror with quick turn-off, delayed turn on actuation, input latches and tri-stating buffer according to the principles of the present invention.
An output of a buffer is sized to sink or source a specified current at a given drain-to-source voltage with a minimum supply voltage. The devices of the present invention are designed such that the desired current is in the saturation range of the output transistor. An insulated gate field effect transistor is in saturation when the drain-to-source voltage is equal to or greater than the gate-to-source voltage minus the threshold voltage of the device. The present invention drives the output transistor into saturation very quickly by controlling the gate-to-source voltage of the output transistor and thereby maintains the drain-to-source current constant. After the desired drain-to-source voltage is reached, the gate of the output device is driven to the maximum supply voltage.
In all of the embodiments to be discussed, transistors and gates having the same function will have the same reference number for sake of clarify and brevity.
In a first current mirror embodiment illustrated in FIG. 2, the input voltage VN is connected through an inverter G1 which includes complementary insulated gate field effect transistors Q8 and Q7 to one end of a pair of resistors R1 and R2. A first current mirror includes an input leg having R1, Q3 and Q5 and an output leg including the output transistor Q1 and a second current mirror includes resistor R2, transistors Q4 and Q6 and an output leg including output resistor Q2. The output VO is taken from the drains of Q1 and Q2. The control of transistors Q5 and Q6 is by logic including inverters G5, G4 and NAND-and NOR-gate G3 and G2 connected respectively to the gates of transistors Q5 and Q6. The inputs to G4 and G5 are connected to the output V0. The inputs to G2 are the input VN and the output of G4 and the inputs to G3 are the input VN and the output of G5.
To understand the operation of FIG. 2, we will assume that the input and output voltage VN and V0 equal the power source voltage V+ or a high. Transistor Q8 of the inverter G1 is on providing ground or a low at the common terminals of resistors R1 and R2. With the output V0 high, the outputs of G5 and G4 are both low. The output of logic gate G2 is low because input VN is high and the output of G3 is high because the output of G5 is low, thereby maintaining transistors Q5 and Q6 off. This disables the respective current mirror inputs and prevents current flow therein such that the low of Q8 provided at the output of the inverter G1 is applied to the gates of output transistors Q1 and Q2 maintaining Q2 off and Q1 on. Thus the output V0 is maintained high by Q1.
When the input VN changes from high to low, Q8 is turned off and Q7 is turned on providing a high at the common terminal of resistors R1 and R2. While V0 is a logic high, the outputs of G4 and G5 are low. With G5 low, G3 maintains a logic high on Q5 keeping it off and thus disables the current mirror. With VN and the output of G4 a logic low, G2 provides a logic high turning Q6 on and enabling the current mirror for Q2. Q5 being off and the high voltage at the intersection of R1 and R2 causes the gate of Q1 to go to V+, thus turning Q1 off. Transistor Q7 being on and resistor R2 provide current to the current mirror consisting of transistors Q4, Q6 and Q2. Thus, Q2 is driven in a constant current mode. As the output voltage V0 reduces to the threshold of the inverter G4, the output of G4 switches to high causing gate G2 to switch to a logic low signal to turn Q6 off. This disrupts the input leg of the current mirror allowing the high voltage from Q7 to be applied to the gate Q2 to drive it in a constant voltage mode. This turns on Q2 fully.
In order for Q4, Q6 and Q2 to act as a current mirror, the on resistance RON of Q6 must be much less than the on resistance of Q4, and Q2 and Q4 must both be operating in their saturated regions. Saturation occurs when an MOS transistor drain-to-source voltage is greater than or equal to its gate-to-source voltage minus its threshold voltage, i.e., VDS ≧VGS -VT. For the current to be determined by R2, the on resistance of Q7 must be much less than the resistance of R2 and the resistance of R2 must be much greater than the on resistance of Q4.
For the transition from VN and V0 being equal to a low signal to VN going high, the inverter transistor Q7 is turned off and Q8 is turned on putting a low voltage signal at the intersection of R1 and R2. With the output V0 being low, the outputs of G4 and G5 are high. The output of G4 being high causes G2 to produce a low output signal maintaining Q6 off. The output of G5 being high and VN going high cause NAND G3 output to be low, turning on Q5. Transistor Q8 and resistor R1 supply the input current for the current mirror formed by Q3, Q5 and output transistor Q1, driving it in a constant current mode. When the output voltage V0 rises sufficiently above the inverter threshold of G5, the output of G5 goes low and NAND-gate G3 goes high turning off Q5. This interrupts the input leg of the current mirror Q5, Q3 and Q1 and causes the substantially ground input from Q8 to be applied to the gate of Q1 to drive it in a constant voltage mode. When the output voltage of V0 is sufficiently above the inverter threshold of G4, its output goes low but NOR-gate G2 stays low because VN is high to maintain Q6 off.
An example of an application of the present invention to a voltage divider instead of a current mirror output drive method is illustrated in FIG. 3. A voltage divider including R1 and transistor Q5 for output transistor Q1 and a voltage divider R2 and Q6 form a voltage divider for output transistor Q2. The voltage divider is activated by the input signal VN through an appropriate transistor of inverter G1 to apply a high or low logic voltage signals to R1 and R2 with the appropriate second leg of the divider Q5 or Q6 being on depending upon the output voltage V0. The transistors Q5 and Q6 maintain a low gate-to-source voltage of the output transistors Q1 and Q2 to maintain it in saturation and operate in the constant current mode. As the output voltage approaches the desired voltage, transistors Q5 and Q6 change states deactivating the voltage divider for the appropriate output transistor Q1 or Q2 and allowing the output voltage from inverter G1 to be applied directly to the output transistors Q1 and Q2 and to operate it in a constant voltage mode.
Assuming that the input and output signals VN and V0 are both high, the output of G1 is low, Q1 and Q6 are on and Q2 and Q5 are off. When the input VN changes from a high to a low, the output of G1 becomes high turning Q1 off and forming a voltage divider between R2 and Q6. When the output voltage V0 becomes sufficiently low, Q6 is turned off and Q5 is turned on. Since the voltage at both ends of the voltage divider including R1 and Q5 are the same high value, it is inoperative even though Q5 is on and the gate of Q1 is pulled high to maintain it off. For a low to high input transition Q1 is controlled by its voltage divider R1 and Q5 to operate first in a constant current and then in a constant voltage mode.
In certain situations, it is desirable to prevent any throughput current flowing simultaneously between Q1 and Q2 by assuring that the previously on output transistor is turned off before the previously off transistor is turned on. A modification to the buffer of FIG. 2 is illustrated in FIG. 4 and includes quick off transistors Q9 and Q10 having their gates connected to the input VN and their respective drains connected to the gates of the output transistors Q1 and Q2 respectively. Assume that VN and V0 are both high. Thus, Q1, Q6, Q8 and Q10 are on, and Q2, Q3, Q4, Q5, Q7 and Q9 are off. With Q8 and Q10 both being on, there is no voltage drop across the resistor R2. As the input VN is changed from a high to a low, Q8 and Q10 turn off and Q7 and Q9 turn on. Q9 provides a high signal to the gate of Q1 and Q7 provides a high signal to the common connection of R1 and R2. Q9 by pulling the gate of Q1 quickly to V+ turns Q1 quickly off. In the embodiment of FIG. 2, the voltage on the gate of Q1 would be pulled up to Q7 through the resistor R1 and thus have a short time delay. Q7 being on and pulling up the gate of Q2 to turn it on is delayed by the resistor R2. Thus Q1 is turned off before Q2 is turned on minimizing any flow between Q1 and Q2. Q10 will operate in the same manner for a low to high transition to turn Q2 off before Q1 turns on.
The application of the present principle to a single polarity or single sided buffer is illustrated in FIG. 5. The complementary output transistor Q1 is connected to provide an additional electrostatic discharge protection element to the output V0 having its conduction path in parallel with conduction path of output transistor Q2. As a further distinction from FIG. 4, the quick off transistor Q10 is connected between the source of Q4 of the current mirror and ground and the gate of Q10 is controlled by the input voltage VN. With VN and V0 high, Q6, Q8 and Q10 are on and Q2, Q4 and Q7 are off. For an input transition of VN from high to low, Q8 and Q10 are turned off and Q7 turns on, activating the current mirror through R2 and driving Q2 in a constant current mode. As V0 approaches a low level, Q6 is turned off disrupting the current mirror, allowing the gate of Q2 to rise to V+ through Q7 and R2, thus driving Q2 in a constant voltage mode.
For a VN transition from low to high, Q7 is turned off and Q8 and Q10 are turned on. With Q10 turning on, the source of Q4 is brought low which allows the resistor R2, Q4 and Q10 to act as parallel discharge paths for the capacitance of the gate of Q2 to turn Q2 off with a controlled turn off delay. Since the turn on time of Q2 is a function of Q4, Q6, and R2, Q7 and the turn off time is a function of Q4, Q10 and R2, Q8, separate turn on and turn off times may be provided for Q2.
A curve of the output voltage V0 for the buffer of FIG. 5 is illustrated in FIG. 6 as Curve C. A prior art bipolar buffer output response is illustrated as Curve B. It is noted that although the bipolar responds more quickly and initially lowers the output voltage, there is substantial hunting or ringing before it settles to a final level. The output voltage produced by the buffer of FIG. 5 reaches a more stable output voltage substantially quicker.
One of the sources of ringing is the reflection of the change of voltage with respect to time or dv/dt. In the bipolar circuit of curve B, the device is driven hard with a high change of voltage in a very short period of time. This produces large reflections resulting in the curve B going below the desired final value and hunting. In the present invention, the output devices are operated as constant current sources having a constant dv/dt. This linear, constant change of voltage with respect to time results from maintaining the output transistor in saturation or its constant current mode as long as possible. When the transistor is in its constant current mode, the change of the output voltage with respect to time is a function of the capacitance of the output and current from the current source.
In order to maintain the output device in its constant current mode as long as possible, the output transistors Q1 and Q2 are selected to be substantially larger devices than transistors selected to be driven by the maximum supply voltage available. These larger devices are maintained in saturation by low gate voltage. The gate voltage and device size are selected to provide the desired current level to achieve switching in the desired time. By using a low gate voltage, the device stays in saturation longer since the output voltage must be substantially closer to the desired output voltage before it switches from its constant current to its constant voltage mode.
Another design incorporating the voltage divider concept is illustrated in FIG. 7. The resistors R1 and R2 are replaced by transistors Q11 and Q12 respectively. These transistors are controlled by the output of the inverter G1. The other leg of the voltage divider including transistors Q5 and Q6 are controlled by the output through inverters G5, G7 and G4, G6 respectively. The thresholds of the inverters determine the output voltage at which Q5 and Q6 are deactivated. The gates of quick turn off transistors Q9 and Q10 controlled by the input VN and their drains are connected to the gates of the output transistors Q1 and Q2 and their sources are connected to V+ and ground respectively. Transmission gate transistors Q13 and Q14 connect the output of the inverter G1 to the gates of output transistors Q1 and Q2 respectively.
With the input VN and output V0 both being high, the output of inverters G1, G4 and G5 are low and G6 and G7 are high, transistors Q1, Q6, Q10 and Q13 are on and Q2, Q5, Q9, Q11, Q12 and Q14 are off. On an input transition from high to low, Q9 is turned on to quickly pull up the gate of Q1 and turn it off. The output of G1 goes high turning Q12 on to form a voltage divider with on Q6 and drive Q2 in a constant current mode. Q14 is off. As the output voltage V0 decreases and switches G4 and G6, Q6 off disrupting the voltage divider with Q12, G6 going low also turns Q14 on and the high output of inverter G1 is then applied directly to the gate of Q2 through turned on Q14 to drive it in a constant voltage mode. As the voltage on the gate of Q2 rises to +V, Q12 is switched off by the reduction of its gate-to-source voltage.
The operation is similar for circuitry to turn Q1 on and Q2 off for an opposite transition of the input from low to high. By substituting transistors Q11 and Q12 for resistors R1 and R2, the need to provide resistors is eliminated. The quick turn off of Q1 and Q2 prevent a simultaneous activation and throughput current.
To completely eliminate any possibility that one of the output transistors turns on before the other is turned off, the circuit of FIG. 8 is provided. NAND-gate G6 is connected between the input VN and inverter transistor Q7 and quick off transistor Q10 and monitors the voltage on the gate of Q1. Similarly a NOR-gate G7 is connected between the input VN and the inverter transistor Q8 and the quick off transistor Q9 and monitors the voltage at the gate of output transistor Q2. It should be noted that the buffer of FIG. 8 is an inverting buffer such that for stable condition of VN being high and V0 being low, the gates of Q1 and Q2 are high such that Q1 is off and Q2 is on. With V0 low, Q5 is on and Q6 is off. Both inputs to NAND-gate G6 are high and the VN input to NOR-gate G7 is high and thus their outputs are both low. Thus Q7 is on and Q10 is off providing the high voltage on the gate of Q2, and Q8 is off and Q9 is on providing the high voltage on the gate of Q1.
With an input VN changing from high to low, the output of NAND-gate G6 changes to a high turning Q7 off and activating Q10 to immediately draw the gate of Q2 to a low and turning it off. The drop of the voltage at the gate of Q2 and the low on VN changes the inputs to NOR-gate G7 to both being low, changing its output from a logic low to a logic high. This turns off transistor Q9 and turns on transistor Q8 activating the input leg of the current mirror driving Q1 in a constant current mode. As the output V0 changes to a high, Q5 is turned off allowing the logic low voltage from Q8 to be provided to the gate Q1 and drive it in a constant voltage mode. As can be seen, the NOR-gate G7 did not change its output in response to a change in the input signal VN and waited until the gate signal for Q2 was sufficiently low to turn it off before activating the circuit which turns Q1 on.
The operation of the NAND-gate G6 is similar in that for the input transition from a low to a high the NAND-gate G6 will still maintain a high output until the gate of Q1 also goes from a low to a high turning Q1 off. At this point G6 will provide a low output turning off Q10 and turning on Q7 activating the input to the current mirror to drive Q2 in a constant current mode.
It should be noted that the inverting buffer of FIG. 8 requires two gate delays, namely G7 and Q9 or G6 and Q10 to turn off the previously on transistor Q1 or Q2 respectively and an additional two gate delays, namely G7 and Q8 or G6 and Q7 to turn on the previously off transistor Q1 and Q2 respectively. In some applications a four gate delay for turning an element on is not desirable.
FIG. 9 shows a buffer which can be adapted to have one gate delay to turn off a device and two gate delays to turn on a previously off device after the first device has been turned off. With respect to FIG. 9, the delays were measured from the output of the latch and do not include the additional delays of the input latches and tri-stating logic to be discussed. The input signal VN is provided as one input to a NAND-gate G9 and a NOR-gate G8 with the second input being a Tristate signal directly to G8 and through inverter G18 to a NAND-gate G9. Connected to the output of the NAND-gate G9 is a latch including tri-state inverters G11 and G15 and inverter G13. Connected to the output of the NOR-gate G8 is a latch including tri-state inverters G10 and G14 and inverter G12. Clock signal C and its inverse signal Care provided to the latches.
The NOR-gate G8 will provide a low output signal for all combinations of the input VN and Tristate except when they are both low. When G10 is enabled by C, the high output signal of G10 activates quick turn off transistor Q10 to ground the gate of output transistor Q2 and turn it off and turn off transistor Q7 which is in the conduction path of the resistor R2 of the input leg of the current mirror. NAND-gate G9 will provide a high output signal for all combinations of input except for the Tristate being low and VN being high. When tri-state inverter G11 is activated, the low output signal of G11 actuates a quick turn off transistor Q9 and turns off Q8 disrupting the path for resistor R1 of the input leg of the current mirror thereby turning Q1 off.
For the initial operation assume the Tristate is low, VN and the output V0 are both high. The latches should also be in their unlatched condition, namely C being high and Cbeing low. For this condition, the outputs of G8 and G9 are low and the outputs of G10 and G11 are high, thus turning transistors Q8 and Q10 on and Q7 and Q9 off. V0 being high turns Q6 on and Q5 off. With Q10 on and Q7 off, Q2 and Q4 are off and the output of G17 is high turning Q15 on. Since Q5 and Q9 are off and Q8 and Q15 are on, Q1 is on being driven in its constant voltage drive mode. With the gate of Q1 at ground, the output of G16 is high turning Q16 off.
As the input signal VN changes from high to low, the signal through G9 and G11 becomes low turning on quick turn off Q9 to pull up the gate of Q1 and turn it off. The low output of G11 also turns off Q8 interrupting the input path of the current mirror. Similarly, G8 and G10 provide a low input signal, turning off Q10 and turning on Q7. As the voltage on the gate of output transistor Q1 is being pulled up and exceeds the threshold of inverter G16, Q16 is activated completing the conduction path to the current mirror including Q2 and thereby operating it in a constant current mode.
Inverter G16 and the transistor Q16 enables the current mirror only after the voltage on the input gate to Q1 has been pulled up sufficiently to turn it off. As in the buffer of FIG. 8, this eliminates throughput of current between Q1 and Q2 by making sure that Q2 is not turned on until Q1 is turned off. The same is true using inverter G17 and transistor Q15 for not allowing Q1 to be turned on until Q2 is turned off.
As the output V0 decreases, the voltage to the gate of transistor Q6 decreases in a delayed fashion by time constant determined by the resistor R3 times the sum of the capacitance of the transistors Q5 and Q6. As the on-resistance of Q6 approaches the on-resistance of Q4, the voltage on the gates of Q2 and Q4 will rise turning the output transistor Q2 on harder. The resulting positive feedback will rapidly turn Q6 off and the voltage on the gate of Q2 will rise to V+, switching Q2 from a constant current mode to a constant voltage mode. The addition of resistor R3 allows the transistors Q5 and Q6 to be of smaller geometry by slowing the rate at which their respective gate voltages change. R3 also isolates the capacitance of the gates of Q5 and Q6 from the circuit output V0. If additional delay is required to prevent one of the output transistors Q1, Q2 from being turned on before the other is turned off, then the inverters G16 and G17 can receive their inputs from the other terminal of resistors R1 and R2 to add more resistance and therefore time delay to the path.
With C high and Clow, both latch G11, G13 and G15 and G10, G12 and G14 are open and data at their inputs, the output of G9 and G8 respectively, are inverted by G11 and G10 and flow to the gates of Q8 and Q9 and Q7 and Q10 respectively. Tristate inverters G15 and G14 are deactivated when the latches are open. When C is low and Cis high the latches are closed and retain their final open state. When the latches are closed G11 and G10 are deactivated, G15 and G14 are enabled to maintain the state of the latches.
It should be noted that if latches are not required, the output of NOR-gate G8 would be connected directly to the gates of Q8 and Q9 and the output of NAND-gate G9 would be connected directly to the gates of transistors Q7 and Q10. Similarly if the tri-state is not required, the input VN would be connected directly to the gates of Q8, Q9, Q7 and Q10.
Although FIG. 5 illustrates one of the circuits as a single polarity buffer, other of the circuits may also be built as a single polarity buffer. Also, FIG. 8 illustrates the buffer as an inverting buffer and the other buffers may also be inverting buffers with appropriate changes.
Although the present invention has been described and illustrated in detail, it is to be clearly understood that the same is by way of illustration and example only, and is not to be taken by way of limitation. The spirit and scope of the present invention are to be limited only by the terms of the appended claims.
Cited Patent | Filing date | Publication date | Applicant | Title |
US4450371 * | Mar 18, 1982 | May 22, 1984 | Rca Corporation | Speed up circuit |
US4485351 * | Jun 27, 1981 | Nov 27, 1984 | Philips Kommunikations Industrie Ag | Circuit for deriving of signals and counter cycle signals from one sided input signal |
US4533845 * | Feb 22, 1984 | Aug 6, 1985 | Motorola, Inc. | Current limit technique for multiple-emitter vertical power transistor |
US4536662 * | Nov 9, 1983 | Aug 20, 1985 | Nec Corporation | Bidirectional constant current driving circuit |
US4567378 * | Jun 13, 1984 | Jan 28, 1986 | International Business Machines Corporation | Driver circuit for controlling signal rise and fall in field effect transistor processors |
US4571511 * | Jun 27, 1983 | Feb 18, 1986 | Rca Corporation | Noise reduction system |
US4612466 * | Aug 31, 1984 | Sep 16, 1986 | Rca Corporation | High-speed output driver |
US4622482 * | Aug 30, 1985 | Nov 11, 1986 | Motorola, Inc. | Slew rate limited driver circuit which minimizes crossover distortion |
US4634894 * | Mar 4, 1985 | Jan 6, 1987 | Advanced Micro Devices, Inc. | Low power CMOS reference generator with low impedance driver |
US4638187 * | Oct 1, 1985 | Jan 20, 1987 | Vtc Incorporated | CMOS output buffer providing high drive current with minimum output signal distortion |
US4717869 * | Sep 2, 1986 | Jan 5, 1988 | Siemens Aktiengesellschaft | Controlled current source apparatus for signals of either polarity |
Citing Patent | Filing date | Publication date | Applicant | Title |
US4890010 * | Dec 22, 1988 | Dec 26, 1989 | Ncr Corporation | Matched current source serial bus driver |
US4924120 * | Jun 29, 1988 | May 8, 1990 | Texas Instruments Incorporated | Low noise output circuit |
US4937474 * | Feb 23, 1989 | Jun 26, 1990 | Northern Telecom Limited | Low power, high noise margin logic gates employing enhancement mode switching FETs |
US4939389 * | Sep 2, 1988 | Jul 3, 1990 | International Business Machines Corporation | VLSI performance compensation for off-chip drivers and clock generation |
US4952818 * | May 17, 1989 | Aug 28, 1990 | International Business Machines Corporation | Transmission line driver circuits |
US4954729 * | Jun 27, 1989 | Sep 4, 1990 | Nec Corporation | Output buffer circuit used for stable voltage source |
US4958088 * | Jun 19, 1989 | Sep 18, 1990 | Micron Technology, Inc. | Low power three-stage CMOS input buffer with controlled switching |
US4959561 * | Mar 26, 1990 | Sep 25, 1990 | Motorola, Inc. | MOS output buffer with reduced supply line disturbance |
US4959563 * | Jun 29, 1988 | Sep 25, 1990 | Texas Instruments Incorporated | Adjustable low noise output circuit |
US4961009 * | Jun 20, 1989 | Oct 2, 1990 | Goldstar Semiconductor, Ltd. | Current-voltage converting circuit utilizing CMOS-type transistor |
US4970452 * | Dec 19, 1989 | Nov 13, 1990 | U.S. Philips Corporation | Integrated circuit comprising a switchable current generator |
US4973861 * | Jan 10, 1989 | Nov 27, 1990 | U.S. Philips Corporation | Integrated circuit comprising logic circuits and at least one push-pull stage |
US4975599 * | Jul 26, 1989 | Dec 4, 1990 | International Business Machines Corporation | Method and resulting devices for compensating for process variables in a CMOS device driver circuit |
US4985646 * | Jul 11, 1989 | Jan 15, 1991 | Kabushiki Kaisha Toshiba | Output buffer circuit of semiconductor integrated circuit |
US5019725 * | Oct 3, 1989 | May 28, 1991 | Texas Instruments Incorporated | Input circuit |
US5029284 * | Apr 30, 1990 | Jul 2, 1991 | Motorola, Inc. | Precision switchable bus terminator circuit |
US5051619 * | Sep 7, 1989 | Sep 24, 1991 | Harris Corporation | Predrive circuit having level sensing control |
US5057720 * | Dec 5, 1989 | Oct 15, 1991 | Nec Corporation | Output buffering H-bridge circuit |
US5073727 * | May 25, 1989 | Dec 17, 1991 | Harumi Shizu | Cmos inverter with noise reduction feedback means |
US5097149 * | Mar 11, 1991 | Mar 17, 1992 | Micron Technology, Inc. | Two stage push-pull output buffer circuit with control logic feedback for reducing crossing current, switching noise and the like |
US5111075 * | Mar 5, 1991 | May 5, 1992 | Vlsi Technology, Inc. | Reduced switching noise output buffer using diode for quick turn-off |
US5117130 * | Jun 1, 1990 | May 26, 1992 | At&T Bell Laboratories | Integrated circuits which compensate for local conditions |
US5122690 * | Oct 16, 1990 | Jun 16, 1992 | General Electric Company | Interface circuits including driver circuits with switching noise reduction |
US5132565 * | Mar 29, 1991 | Jul 21, 1992 | Sharp Kabushiki Kaisha | Semiconductor integrated circuit including voltage level shifting |
US5151620 * | Mar 25, 1991 | Sep 29, 1992 | Industrial Technology Research Institute | CMOS input buffer with low power consumption |
US5165054 * | Dec 18, 1990 | Nov 17, 1992 | Synaptics, Incorporated | Circuits for linear conversion between currents and voltages |
US5212440 * | May 14, 1990 | May 18, 1993 | Micron Technology, Inc. | Quick response CMOS voltage reference circuit |
US5231319 * | Aug 22, 1991 | Jul 27, 1993 | Ncr Corporation | Voltage variable delay circuit |
US5237213 * | Apr 15, 1992 | Aug 17, 1993 | Oki Electric Industry Co., Ltd. | Semiconductor integrated circuit with low-noise output buffers |
US5241221 * | Nov 16, 1992 | Aug 31, 1993 | North American Philips Corp., Signetics Div. | CMOS driver circuit having reduced switching noise |
US5289051 * | Sep 24, 1992 | Feb 22, 1994 | Siemens Aktiengesellschaft | Power MOSFET driver having auxiliary current source |
US5293082 * | Jun 4, 1993 | Mar 8, 1994 | Western Digital Corporation | Output driver for reducing transient noise in integrated circuits |
US5332934 * | Jan 4, 1993 | Jul 26, 1994 | Masashi Hashimoto | Small to full swing conversion circuit |
US5337254 * | Dec 16, 1991 | Aug 9, 1994 | Hewlett-Packard Company | Programmable integrated circuit output pad |
US5355028 * | Oct 23, 1992 | Oct 11, 1994 | Micron Technology, Inc. | Lower power CMOS buffer amplifier for use in integrated circuit substrate bias generators |
US5367205 * | May 13, 1993 | Nov 22, 1994 | Micron Semiconductor, Inc. | High speed output buffer with reduced voltage bounce and no cross current |
US5367210 * | Feb 12, 1992 | Nov 22, 1994 | Lipp Robert J | Output buffer with reduced noise |
US5371420 * | Mar 19, 1993 | Dec 6, 1994 | Mitsubishi Denki Kabushiki Kaisha | Output circuit having reduced switching noise |
US5381055 * | Jul 29, 1993 | Jan 10, 1995 | Motorola, Inc. | CMOS driver using output feedback pre-drive |
US5426376 * | Apr 23, 1993 | Jun 20, 1995 | Vlsi Technology, Inc. | Noise isolated I/O buffer that uses two separate power supplies |
US5430335 * | Nov 29, 1993 | Jul 4, 1995 | Oki Electric Industry Co., Ltd. | Simplified low-noise output buffer circuit |
US5491436 * | Jul 29, 1994 | Feb 13, 1996 | International Business Machines Corp. | Compensated CMOS driver circuit with reduced DC losses |
US5563539 * | Feb 28, 1994 | Oct 8, 1996 | Fujitsu Limited | Output buffer circuit changeable of the output signal from a low to a high impedance state |
US5600261 * | Oct 5, 1994 | Feb 4, 1997 | Cypress Semiconductor Corporation | Output enable access for an output buffer |
US5614855 * | Aug 21, 1995 | Mar 25, 1997 | Rambus, Inc. | Delay-locked loop |
US5650742 * | Mar 29, 1995 | Jul 22, 1997 | Matsushita Electric Industrial Co., Ltd. | Voltage-level shifter |
US5656947 * | Jul 16, 1996 | Aug 12, 1997 | National Semiconductor Corporation | Low noise digital output buffer |
US5798972 * | Dec 19, 1996 | Aug 25, 1998 | Mitsubishi Semiconductor America, Inc. | High-speed main amplifier with reduced access and output disable time periods |
US5864254 * | Mar 19, 1996 | Jan 26, 1999 | Rohm Co., Ltd. | Differential amplifier circuit with enlarged range for source voltage and semiconductor device using same |
US5898242 * | Mar 17, 1993 | Apr 27, 1999 | Unisys Corporation | Self-calibrating clock circuit employing a continuously variable delay module in a feedback loop |
US5955893 * | Dec 16, 1996 | Sep 21, 1999 | Macronix International Co., Ltd. | Power saving buffer circuit buffer bias voltages |
US5959481 * | Feb 18, 1997 | Sep 28, 1999 | Rambus Inc. | Bus driver circuit including a slew rate indicator circuit having a one shot circuit |
US6014057 * | Apr 29, 1997 | Jan 11, 2000 | Fujitsu Limited | Amplifier circuit with wide dynamic range and low power consumption |
US6018271 * | Jul 19, 1999 | Jan 25, 2000 | Fujitsu Limited | Amplifier circuit with wide dynamic range and low power consumption |
US6025739 * | Apr 21, 1998 | Feb 15, 2000 | International Business Machines Corporation | CMOS driver circuit for providing a logic function while reducing pass-through current |
US6037827 * | Jun 27, 1997 | Mar 14, 2000 | United Memories, Inc. | Noise isolation circuit |
US6060938 * | Aug 19, 1998 | May 9, 2000 | Fairchild Semiconductor Corp. | Output buffer for reducing switching noise |
US6124748 * | Apr 9, 1999 | Sep 26, 2000 | Intel Corporation | Method and apparatus for improving ringback tolerance in an input receiver |
US6335632 * | May 30, 2000 | Jan 1, 2002 | International Business Machines Corporation | CMOS small signal switchable terminator network |
US6369638 * | Dec 5, 2000 | Apr 9, 2002 | Rohm Co., Ltd. | Power drive circuit |
US6441653 * | Feb 20, 2001 | Aug 27, 2002 | Texas Instruments Incorporated | CMOS output driver with slew rate control |
US6624669 * | May 25, 2000 | Sep 23, 2003 | Nec Corporation | Drive circuit and drive circuit system for capacitive load |
US6624672 * | Dec 21, 2001 | Sep 23, 2003 | Stmicroelectronics S.R.L. | Output buffer with constant switching current |
US6670836 * | Aug 15, 2002 | Dec 30, 2003 | Micron Technology, Inc. | Differential buffer having bias current gated by associated signal |
US6724260 * | Nov 27, 2002 | Apr 20, 2004 | Texas Instruments Incorporated | Low power current feedback amplifier |
US7109758 * | Jan 30, 2004 | Sep 19, 2006 | Macronix International Co., Ltd. | System and method for reducing short circuit current in a buffer |
US7123045 * | Sep 9, 2004 | Oct 17, 2006 | Rohm Co., Ltd. | Semiconductor integrated circuit device |
US7239182 * | May 5, 2005 | Jul 3, 2007 | Freescale Semiconductor, Inc. | Predriver circuit |
US7635998 | Jul 10, 2008 | Dec 22, 2009 | Freescale Semiconductor, Inc. | Pre-driver for bridge circuit |
US8624680 | Feb 15, 2011 | Jan 7, 2014 | Steven T. Stoiber | Ring based impedance control of an output driver |
US20050052800 * | Sep 9, 2004 | Mar 10, 2005 | Rohm Co., Ltd. | Semiconductor integrated circuit device |
US20050168250 * | Jan 30, 2004 | Aug 4, 2005 | Macronix International Co., Ltd. | System and method for reducing short circuit current in a buffer |
US20050280440 * | May 5, 2005 | Dec 22, 2005 | Hidetaka Fukazawa | Predriver circuit |
US20090115464 * | Nov 5, 2007 | May 7, 2009 | Matsushita Electric Industrial Co., Ltd. | Multiple-branching configuration for output driver to achieve fast settling time |
US20100007399 * | Jul 10, 2008 | Jan 14, 2010 | Freescale Semiconductor, Inc | Pre-driver for bridge circuit |
EP0398016A2 * | Apr 6, 1990 | Nov 22, 1990 | International Business Machines Corporation | Driver circuits |
EP0398016A3 * | Apr 6, 1990 | Dec 16, 1992 | International Business Machines Corporation | Driver circuits |
EP0513663A1 * | May 7, 1992 | Nov 19, 1992 | Oki Electric Industry Co., Ltd. | Simplified low-noise output buffer circuit |
U.S. Classification | 326/27, 326/30, 323/315, 326/87, 326/58, 330/288 |
International Classification | H03K19/094, H03K19/00, H03K19/017, H03K19/003 |
Cooperative Classification | H03K19/09429, H03K19/01721, H03K19/0013, H03K19/00315 |
European Classification | H03K19/094M2, H03K19/00P4, H03K19/003C, H03K19/017B2 |
Date | Code | Event | Description |
Jul 20, 1987 | AS | Assignment | Owner name: HARRIS CORPORATION, 1025 WEST NASA BOULEVARD, MELB Free format text: ASSIGNMENT OF ASSIGNORS INTEREST.;ASSIGNORS:YOUNG, WILLIAM R.;DAVIDSON, HAROLD D.;REEL/FRAME:004750/0020 Effective date: 19870709 |
Sep 30, 1992 | FPAY | Fee payment | Year of fee payment: 4 |
Sep 30, 1996 | FPAY | Fee payment | Year of fee payment: 8 |
Sep 27, 1999 | AS | Assignment | Owner name: INTERSIL CORPORATION, FLORIDA Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNOR:HARRIS CORPORATION;REEL/FRAME:010247/0043 Effective date: 19990813 |
Nov 8, 1999 | AS | Assignment | Owner name: CREDIT SUISSE FIRST BOSTON, AS COLLATERAL AGENT, N Free format text: SECURITY INTEREST;ASSIGNOR:INTERSIL CORPORATION;REEL/FRAME:010351/0410 Effective date: 19990813 |
Oct 3, 2000 | FPAY | Fee payment | Year of fee payment: 12 |
Oct 24, 2000 | REMI | Maintenance fee reminder mailed |


text:
Artist description:
srry it looks funny i just didnt kno wat u excatly wanted so yea ^^' if u dont like it tell me and ill make u a new one okiez lady-dark? :)
Flash Draw Created Jan 10, 2008 470 x 338px Unless noted Copyright 2008 DARK-ANGEL.
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subset: commoncrawl


text:
ECG report send to the mobile (android application) using GPRS sessions
This project received 14 bids from talented freelancers with an average bid price of $306 USD.
Get free quotes for a project like thisProject Budget
$30 - $250 USDTotal Bids
14Project Description
In my proposed system patient's ECG signals are measured by the functional unit at the patient's end and real time signal is sent to doctor's mobile phone over a GPRS session. So the doctor will able to monitor patient's real time ECG signal over his/her mobile using my proposed mobile application. And also proposed ECG measuring unit has the functionality of displaying ECG signal real time in the patient's end also.
Have further projects will give them if this was done in a satisfactory way. Project duration would be around1-2 months.
Further details can be discussed.
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text:
Who's in?
A poem a day is NEVER a bad thing.
Happy Writing!
Allyson-- Good luck on your novel! I learned that "Like Water for Elephants" began there!
Drew-- I feel good (and I wrote my first poem), but I come at these things with LOW expectations. I have whipped out some terrible poems just to be done with them, then the next day, something good comes about...or doesn't. I figure at the end of the month, I'll 30 poems that would have never been written, who knows if they'll ever go someplace.
My April poem-a-day got me one or two poems in the end. the rest I have never been able to revise into more.
Do you try to do the prompts or do you just try to write a poem? I look at the prompt and if it doesn't inspire me, I read another poet's poem and write from that.
Since you're feeling resistance, you should continue on and see what happens. And no expectations. Just write. I consider these poem-a-day similar to being in a batting cage, I may miss quite a few, but every so often a good hit.
Good luck and let me know what you end up doing.


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MP brakes
I've installed MP under floor brakes on my 39 plymouth. Have'nt got around to fully adjust and bleed yet. At the moment I have to pump them once or twice and even then if I press hard enough I lose pedal. I've installed the portioning valves, proper lines, etc but think I still have air in them. Have a fat man Mustang two front end and a crysler rearend.Disc on front and drums on rear. My question is that I've been told by some people that I'll never be able to get good breaking with this system. Oh also I have the small power booster which came with the kit. Your opinion would be appreciated. Thanks John
Sponsored Links | |||
When you say you press hard enough you loose pedal do you mean if you maintain pressure on the brake pedal the pedal will slowly go all the way to the floor? If so your master cylinder is probably bad. Don't assume if it is new it is good.
1. Try bleading the master cylinder seperatly from the rest of the car while still installed on the car. Called bench bleading. Once you get all the air out of the master cylinder reconect the lines. If you can not get the air out of the master cylinder replace it. 2. Blead each wheel with a one man brake blead kit with the recovery bottle ABOVE the wheel cylinder or caliper. Start with the longest brake line and work to the shortest. |
John, you don't mention having a residual valve. Under floor brakes must have residual valves to keep the fluid from draining back to the master cyl. The best way would be to replace the prop. valve with a combination valve and add a 2lb residual valve to the front disc line. The combination valve has a 10lb residual valve built in for the rear. If you want to keep the prop. valve you have add a 2lb to the front and a 10lb to the rear.
Jack |
Thanks guys. I'm not sure but I think I did install a residual and combination valve but it has been awhile so I'll have to look. I've had allergies so bad lately that all I want to do is stay in. Thanks again I'll let you know as soon as I've checked the valves
Aloha John,
I am having similar problems with a similar set-up on my '39 Ford. If you find a good value (quality and price) on a combo valve that you really like, let me know which one you chose. Thanks. Quote:
Recent Suspension - Brakes - Steering posts with photos |
Currently Active Users Viewing This Thread: 1 (0 members and 1 guests) | |
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China > Nongfu Oriental Leaf Tea
June 8, 2011
Designed to bring the heritage of Chinese tea to life, Nongfu Spring introduces its new range of Oriental leaf tea. The premium teas are available in red, green, jasmine and oolong and feature vibrant images that represent the history of tea in China (e.g., a boat that signifies the first transport of tea from China to Britain). "The combination of striking and rich imagery with traditional Mandarin text fuses the best of Eastern and Western styles," says Natalie Chung, creative partner at Pearlfisher, which designed the packaging.
May 2011
Package design
Pearlfisher, www.pearlfisher.com
Pearlfisher, www.pearlfisher.com and Nongfu Spring Company, www.nongfuspring.com
Did you enjoy this article? Click here to subscribe to BRAND PACKAGING Magazine.


text:
Family and Friends Remember Victim of Deadly Beating
LAS VEGAS -- On Sunday, family and friends came together to mark the one year anniversary of the death of a 46-year-old woman who was beaten to death in her Summerlin apartment.
Police discovered Shauna Tiaffay's ex-husband, a Las Vegas firefighter, had allegedly paid a man $600 to kill her.
"I think about the last time I talked to her and think about what I wish I would have done, leading up to it and things like that," said Tiaffay's sister, Paula Stokes-Richards. "It is a difficult milestone, but at the same time I miss her just as much today as I did a year ago."
For family and friends of Tiaffay, time has done little to comfort the loss they carry in their hearts.
On September 29, 2012, police discovered Tiaffay's brutally beaten body in her Summerlin apartment.
Investigators later discovered she was the victim of a murder-for-hire plot allegedly orchestrated by her husband George Tiaffay.
Tiaffay's sister says the time since Shauna's murder has only brought more remorse. She says, "It sounds ridiculous, but you know all these things run through your mind, and you wish you could go back in time and try to change the course of events."
With candles lit and photos of Tiaffay, Stokes-Richards and her husband say they are using the anniversary to bring attention to domestic violence and highlight the signs they missed. "For many years in Shauna's marriage, we heard about verbal abuse and a lot of controlling issues between her husband and her."
"There is nothing we can do to bring her back, but maybe there is something we can do to make sure this doesn't happen to anyone else," said Tiaffay's brother-in-law.
A trial has yet to begin in Tiaffay's case, but her family says they have full faith in the justice system and wait for a day of closure.
"It's a daily process. I think about it all the time, and I hope that someday I will get to the point that I'm not consumed by it," said Stokes-Richards.
Tiaffay left behind a daughter who is now 9-years-old. She is in primary custody of the Tiaffay family and is doing well.
George Tiaffay's trial date is scheduled for January 13, 2014.
More Stories
Three people were arrested for being connected to the human sex…
A Clark County School District bus was involved in a crash with a…
Homicide detectives are investigating a stabbing related homicide,…


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This Sanibel Condo is my Home Away from Home. I spend about 12 weeks per year on the island with my husband, family and friends. I truly love this island!
We have owned this unit for five years and are working to make it the "best Sanibel has to offer"!
Whenever I travel, I have to check out TripAdvisor, so FlipKey was the logical place to list my rental unit!


text:
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22nd June 2010, 11:28 AM | #1 |
diyAudio Member
Join Date: Jun 2010
Location: rickmansworth herts
comparing hi fi sound to car sound
This is my first post on this site. Hello there!! Some time in the future(after I move) I hope to be building new cabs for my Tannoy hpd 385's At present they are in custom built cabs very similar to Berkeleys.The point I want to make,while I am deciding which diy cab to construct, is the issue with modern car audio. I know this is an odd topic but I recently bought a modern car,and as I thought,the car audio sound is just great. Just Something that is just thrown in with the car.No system building whatsoever............Music,male announcers voice, everything effortlessly deep resonant,all of it! BUT.....to got this KIND of sound on hi fi ,even with good equipment seems hard to do. I mean standared car audio is based on small cheap speakers,and at normal listening volumes male announcers voices are incedible.Even the doors vibrate.I realise that sitting in a car is like sitting inside a speaker cab with toally different values to a living room,but I've never really understood just why it sounds so good. Sure,my hi fi has a big powerful sound(both set ups) and I love it,can shake the room and all that,but the car sound is just so good. I am trying to find out the reason why.However it's done I would like to apply the principle to home audio.It must be down to near perfect system matching and some kind of advanced processing that doesn't seem to present in home audio .When the subject of car audio is ever dicussed anywhere,a lot of folk say how bad it is.I don't really understand that.Yes the sound could be tidied up a bit on the top end,but the basic sound is liquid gold. Any views on this? REGARDS BIAMP |
22nd June 2010, 11:38 AM | #2 |
diyAudio Member
Join Date: Jun 2010
I would love to know the same thing. My car stereo sounds fantastic. the bass is perfect, and the treble and midrange is smoooth but not harsh. Mine is a mcintosh stereo in my car, and it is the model on how i wish my house sounded.
22nd June 2010, 11:55 AM | #3 |
diyAudio Member
Join Date: Aug 2009
Location: Germany
I don't know exactly how they calculate that, but they use the doors and door boards, the dashboard and whatnot as a part of a speaker enclusure. As most modern cars have sound proofing applied, this sound proofing is like stuffing the enclosure. My almost 20 year old car doesn't have this and the front speakers sound dull, because of their low position, no real enclusure (the dashboard is open on the back), plastic parts rattle... etc.
Also, the car is a MUCH smaller room to listen. Put all your speakers and gear in a small 2 m x 2 m room, put a seat in the middle and start listening. I think this is the greatest difference in home and car sound. |
22nd June 2010, 12:15 PM | #4 |
diyAudio Member
Join Date: Aug 2003
Location: Cape Town
Could it be that within a car environment the car audio system has access to much more current compared to the 15 amps from the average 220 mains socket?
22nd June 2010, 01:43 PM | #5 |
diyAudio Member
Join Date: Jun 2010
Location: rickmansworth herts
Comparing car sound with hi fi sound.
Thanks for the response! Another unsettling aspect is that car audio seems to break every known rule in the hi fi book.And there isn't an oak cone foot in sight!For a long time.I have a feeling there is a lot of audio secrets locked in there,but as it's another totally different medium to home sounds so they may always have to be seperate.I still feel, though there is something going on there,that might just be of use to us home audio entusiasts . ALSO Have you ever checked out the sound systems on modern fair grounds?The fairground operators are total professionals ,know their music.The cabs in their rain jackets are just loaded onto the ride,no fancy speaker supports,cryptonite pucks or amp racks or any of the hi fi stuff,driver alignment of the hi,mid and bass,Not an issue ..... but the sound...............It's seismic....AND pure and undistorted .The mids and tops fairly spit the sound out at you,and NO DISTORTION!!!!Bass of course is the same quality. Wouldn't really know how this stuff images or how a string quartet would sound(probably great) but this stuff MOVES ME. One of the top specialist sound companies who supply this gear, is Disco Smash (DS) of Holland. Boy have they got their act together.I think there could be a lot to be learned from studying the approach of these systems.Of couse there are several of these professional type systems which I believe ,if studied hold a lot of clues to good home sound.A sort of trickle down proceedure,to be applied to home hifi.....I say this by observing the results achieved with the LACK of hi fi paraphinalia.......Check out Jamiacan reggae sound systems. Cinema systems, quality PA's..............Yeah,I know,again,all this is a TOTALLY different medium to what we have in the front room,the laws of phisics ,the length of bass sine waves and all that sort of thing and being able to ACTUALLY use most of the power of the amps,instead of just for headroom.....One of the main problems is the sheer physical space this stuff operates in.I know that,.......Butttt Still feel there is something going on, in equipment developed for the pro workplace that we need to know.(and not just the reliability factor.)It all seems to get better and better. REGARDS BIAMP |
23rd June 2010, 08:39 AM | #6 |
diyAudio Member
Join Date: Jun 2010
Location: rickmansworth herts
trying to find a useable link between pro sund and hi fi
Having said all that in the previous post,maybe the laws of phisics preclude any possible link with home hi fi. Any views? REGARDS BIAMP |
23rd June 2010, 10:48 AM | #7 |
diyAudio Moderator
I would hazard a guess that you like the sound in the car because it is "coloured", and distorted... I know exactly what you mean in your description too, I have experienced the same thing. It just sounds "nice"
It's not an "accurate" sound however... and it's a fact that most listeners prefer this. When it come to hifi in the home, very very few systems achieve a "satisfying" musical performance... and the amps that manage it are usually the ones designed from the ground up with an "ear" to sond quality. The amps designed to iron out distortion at all levels, and in general designed just for ultimate specs usually sound "bland", "boring" and "fatigueing". |
23rd June 2010, 12:14 PM | #8 |
diyAudio Member
Join Date: Jun 2010
Location: rickmansworth herts
Hi Mooly
Thanks for the reply.....I agree with that!! ...... REGARDS BIAMP |
23rd June 2010, 01:52 PM | #9 |
diyAudio Moderator
Your car environment is very small. Makes any system sound better. Take your car system to where your Hi-Fi system is and it will sound terrible. Move your Hi-Fi system into your car and you'll wonder why you ever thought the car system sounded good.
27th June 2010, 04:37 PM | #10 |
diyAudio Member
Join Date: Jun 2010
Location: Powell River (pearl on the Sunshine Coast)
That's why it's called 'High Fidelity' eh ?
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Whilst attending my mandatory four years in a state-operated institution of patchwork, dubious learning (aka, high school) in the mid-1980s, I was taught that the basic narrative for the women's "lib" movement was it allowed the fairer sex to make their own way in life, free themselves from the oppressive control of men, and chart their course upon a silver sea of endless, male-free possibilities. In everyday life, this meant that opening a door for a woman or thoughtlessly attempting to pay for both meals on a date were grounds to be viewed as demeaning to women and subservise of their liberated cause.
Now, in 2012, we learn that men who oppose the federal government's mandate that nearly all employers to pay for contraception and abortifacients are wicked, evil, and extremist. (Sure, lots of women also opposed said mandate, but let's not confuse folks who can't comprehend that the truly liberated women are the ones rejecting government handouts.) But don't believe me (I'm a man, after all); listen to that calm, measured voice of reasona national treasure! a cosmic delight!the sweetheart of liberal columnists, Maureen Dowd:
As secretary of state, [Hillary] Clinton is supposed to stay out of domestic politics. But this was a moment pregnant with possibility, a titanic clash of the Inevitable (Hillary) and the Indefensible (Republican cavemen).
The attempt by Republican men to wrestle American women back into chastity belts has not only breathed life into President Obama, it has roused and riled Hillary. And that could turn out to be the most dangerous thing the wildly self-destructive G.O.P. leaders have done.
In some kind of insane bout of mass misogyny, Republicans are hounding out the women voters including Republicans and independents who helped them gain control of the House in 2010.
Senator Olympia Snowe, who's fed up and leaving Congress, told The Washington Post's Karen Tumulty that "it feels as if we are going back to another era," warning that Republicans could drive women into Democratic arms.
And that other era would be, what, the winter of 2011? The first week of January 2012 (as Jonah Goldberg dryly observed)? But, goodness, how many moments pregnant with possibility actually exist when one's time, talents, and passion for "reproductive justice" are spent clamoring for funding to eliminate the possibility of pregnancy and to terminante those pregnancies that somehowunintended and unplanned, of coursesuddenly threaten to punish the hapless, liberated, man-free woman?
To be fair to Dowd, she nearly comes off as moderate and thoughtful compared to a March 12th editorial in the New York Times that wails and flails like a Knicks fan coming down off the Jeremy Lin high because "the Republican-controlled House held a hearing to promote a mean-spirited and constitutionally suspect bill called the Child Interstate Abortion Notification Act." And what acts of shocking barbarism would this vile "Act" promote among the fair citizens of the land? It would "[impose] a mandatory parental notification requirement and 24-hour waiting period on women under 18 who travel outside their home state to get the procedure." The procedure, of course, being the killing of the unborn baby of a teenage mother.
This deeply traumatic requirement, the editors howled, "is both an attack on women's rights and on the basic principles of federalism." One must acknowledge their obvious agitation: after all, they would never take down a dictionary and look up the word "federalism"never mind use the baffling termunless they were profoundly moved by the fear that somewhere and somehow a confused and distraught 16-year-old girl might have to stop and rethink her rash decision to destroy the innocent life in her womb.
And, as if to ensure their fiercely uttered (and feebly argued) sentiment could not be spoofed or satired in any way, shape, or form, the editors tossed in this desperate smokescreen:
Under threat of criminal and civil penalties, doctors also would be forced to comply with a burdensome legal regimen involving the interaction of varying state laws and those of the provider's home state. A similar measure is pending in the Senate.
Ah, so doctors would be "forced to comply with a burdensome legal regimen involving [blah, blah, blah]", something that surely will never be a problem with the 425,116 words in the Obamacare statutes and the 2,163,744 words crammed into the Obamacare regulations. At least not until Nancy Pelosi has read all such statutes and regulations and informed us differently. But since she is busy being a flack for the fishy facts foisted by Sandra Flake (say it fast, faster, and fastest), we may never know.
Meanwhile, in related news:
A new CBS News/New York Times poll shows that most Americans believe there should be an exception for employers who may have a moral or religious objection to covering birth control for their employees. According to the poll, which surveyed more than 1,000 adults nationwide from March 7-11, 51 percent of Americans believe employers of any kind should be allowed to opt out of covering birth control for religious or moral reasons. Forty percent say all employers should have to cover contraceptive care.
And, from the Wall Street Journal:
But when asked whether the government should mandate that Roman Catholic and other religiously affiliated hospitals and colleges offer birth control paid for by the institutions' insurance companiesas required by the ruleAmericans were opposed by 45% to 38%. Women split evenly, with 40% in favor and 40% opposed.
Here is the actual poll.
All comments posted at Catholic World Report are moderated. While vigorous debate is welcome and encouraged, please note that in the interest of maintaining a civilized and helpful level of discussion, comments containing obscene language or personal attacks—or those that are deemed by the editors to be needlessly combative and inflammatory—will not be published. Thank you.
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text:
Severe Gape |
Description: In This scene, Mika Tan slobs on knob, taking it deep down her throat. Her pussy gapes so wide, you could easily slide a beer can in there. When her stud explodes all over her face and tongue, she just smiles, loving every last drop. |


text: On Fri, 14 Jul 2006 11:35:28 +0530, Parag N(पराग़) wrote: > Hi, > While reviewing some packages i am getting following errors in mock > build for rawhide repository > > checking for intltool >= 0.18... 0.34.1 found Is this the one that is included with the package or the system one? Do you have BR intltool? > checking for perl... /usr/bin/perl > checking for XML::Parser... configure: error: XML::Parser perl module > is required for intltool > error: Bad exit status from /var/tmp/rpm-tmp.20633 (%build) > > What am i missing that leads mock build to fail? I am doing mock build > using local rawhide mirror repository. > Regards, > Parag. >


text:
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COLUMBUS, Ohio (AP) – Gas prices in Ohio are up slightly to start the work week.
The cost for a gallon of regular gas in Ohio was averaging $3.70 in Monday's survey from auto club AAA, the Oil Price Information Service and WEX Inc. That's up about 2 cents from a week ago.
Monday's Ohio price is 16 cents higher than a month ago, and about 5 cents higher than last year at this time.
The national average Monday was 3.67 per gallon. That's up 3 cents from last week, and it's 15 cents higher than a month ago.
Department of Energy forecasters expect the April through September national average to be about $3.57 a gallon, a little lower than the past few summers.
AAA Daily Fuel Gauge Report: http://fuelgaugereport.aaa.com
(Copyright 2014 The Associated Press. All rights reserved. This material may not be published, broadcast, rewritten or redistributed.)


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Thomas Greene | |
Birthdate: | |
Birthplace: | Bobbing Manor, Bobbing, Kent, England |
Death: | Died in St. Mary's County, Province of Maryland |
Place of Burial: | St. Mary's City, St. Mary's County, Maryland, United States |
Immediate Family: |
Son of Sir Thomas Greene, Knight and Margaret Greene |
Occupation: | 2nd Proprietary Governor of Maryland Colony, 2nd. Governor of Maryland. |
Managed by: | Private User |
Last Updated: |
Immediate Family
About Thomas Greene, 2nd Proprietary Governor of Maryland
From his English Wikipedia page:
Thomas Greene of Bobbing, Kent, 2nd Proprietary Governor of Maryland (1610, Bobbing, Kent, England - 20 Jan 1651 St. Mary's County, Maryland) was an early settler of the Maryland colony and second Provincial Governor of the colony from 1647 to 1648.[3]
He was the son of Sir Thomas Greene and Lady Margaret Webb. His father was created Knight Bachelor of the Realm by James I in 1622 at Windsor Castle.
Thomas came over from England on the Ark and Dove expedition in 1634. Greene was among the earliest settlers of the colony after its founding in 1634 as a haven of religious tolerance for English Catholics among other groups. He was already prominent in the politics of the colony by 1637 or 1638, when he became a prominent leader of moderate Catholics. More radical Catholics led by Thomas Cornwaleys resisted attempts by the colony's proprietor, Cecilius Calvert, 2nd Baron Baltimore to ensure a broader religious tolerance by, for example, restricting the activities of the Jesuits. Greene and others voted against some of these measures, but despite pressure from Cornwaleys and the Jesuits accepted the laws once they were passed.[4]
In 1647, Greene was appointed to the governorship by the colony's first governor, Leonard Calvert, as an emergency measure only hours before Calvert's death due to a sudden illness.[3] He was by this point one of the few early settlers still active in colonial leadership. Some, such as Leonard Calvert, had died and some, such as Thomas Cornwaleys, had returned to England.[4] Greene, who had been a member of the colonial council prior to his appointment and was familiar with the issues confronting the colonial government, quickly set about strengthening the colonial militia in response to threats from the Nanticoke and Wicocomico tribes of Native Americans. Among his actions was the payment of arrears to soldiers at St. Inigoe's Fort as well as appointment of John Price as the new commander of colonial militia.[5] These were necessary steps given that the colonial militia had been severely taxed during armed conflict with Virginian William Claiborne and his allies during the previous three years. Greene also appointed a number of Catholics to government offices, but was unable to build Catholic influence in the colony and suffered severe political setbacks when the Protestant-dominated colonial assembly passed legislation unfavorable to the proprietary government.[4]
By 1648, Cecilius Calvert replaced him with William Stone. Greene was a Catholic and a royalist, and some historians have speculated that Stone, a Protestant and supporter of Parliament, was appointed in his place to appease the Protestant majority in the colony.[6] Following his removal from office, Greene served as Deputy Governor under Stone. In November 1649, while Stone was in neighboring Virginia, Greene used this position to publicly declare Maryland in support of Prince Charles, the heir to the English throne. Earlier that year, the Prince's father, King Charles I, had been executed by the mainly Puritan Parliamentarians in the culminating event of the English Civil War. Stone quickly returned and retracted the declaration, but the event was enough to convince Parliament to appoint Protestant commissioners Richard Bennett and William Claiborne to help oversee the colony. Bennett and Claiborne appointed a Protestant council to oversee the colony, creating some confusion as to whether this council of the proprietary governor and his deputies was in charge. The council, among other decisions, rescinded the Maryland Toleration Act which had guaranteed religious freedom in the colony and banned Catholics from worshiping openly. Stone attempted to regain control of the colony by force, but was defeated in the Battle of the Severn.[3]
The Greene family of Maryland did not descend from the Green family of Norton's Green, but rather through the illegitimate child of Sir John Norton of Northwood, Sir Thomas Norton who took on the alias Greene; hence the descendants surname of Greene.[7] He was descended from Nicholas de Norton, who lived in the reign of King Stephen,[8] and was possessed of much land in the neighborhood of Norton and Faversham, as appeared by the chartulary of the monastery of St. Augustine.[8]
Governor Thomas Greene was the son of Sir Thomas Greene Of Bobbing Kent and Margaret Webb of Frittenden, Kent, England. Gov. Thomas had three brothers; Jerimiah Greene, John Greene, and the Hon. Robert Greene, Lord of Bobbing Manor who had joined his brother in Maryland for a time, but returned to England as the eldest son to inherit his father's property. Governor Greene's father, Sir Thomas, was created a Knight Bachelor of the Realm by King James I on 5 September 1622.[9][10] at Windsor Castle in Berkshire, England.
Sir Thomas Greene's father was Sir Robert Green of Bobbing Kent who married Frances Darrel, daughter of Thomas Darrel of Scotney. Sir Robert was the son of Sir Thomas Norton alias Greene and his wife Alice Heveningham, daughter of Sir George Heveningham. George, by his mother Alice Bruyn, was a first cousin of Charles Brandon, 1st Duke of Suffolk.[11][12] Sir Thomas was the illegitimate child of Sir John Norton of Northwood through whom the family descended.[7] Between 1536 and 1541, Sir Thomas Norton Greene was granted royal favours by Henry VIII. During the dissolution of the monasteries the rectory at Bobbing Manor along with "all manors, messuages, glebe, tithes and hereditaments in the parishes and fields of Bobbing, Iwade, Halstow, and Newington" were granted to him by the King.[9]
Sir John Norton of Northwood's wife was Joan Northwood, co-heiress with her brother to the estates of John Northwood, Esq. Sir John Norton's father was Sir Reginald Norton of Lee's Court in Sheldwich, Kent who married Katherine Dryland of Cooksditch in Faversham, Kent, England.[13]
Lees Court
Sir Reginald's grandfather Sir John Norton married Lucy At-Lese. It was through her that their descendants came into the possession of Lees Court alias Sheldwich, some of whom lie buried at Faversham. The property of Lees Court which seems to have comprehended the manor of Sheldwich, became the property of that family during the reign of Edward I. From their residence at the Lees, the family assumed the name of At-Lese, their mansion here being called Lees-court, a name which this manor itself soon after wards adopted, being called THE MANOR OF LEESCOURT, alias SHELDWICH. It was the previously mentioned Sir John Norton of Northwood who alienated this manor to Sir Richard Sondes, of Throwley, whose son Sir George Sondes, K. B. succeeding him in it, pulled down a great part of the old mansion of Lees-court, soon after the death of King Charles I. He then completed the present mansion of Lees-court, the front of which is built after a design of Inigo Jones, to which he after wards removed from the antient mansion of his family at Throwley.[8][14] The current court was inherited and is currently inhabited by Phyllis Kane, Countess Sondes, wife of the former Henry George Herbert, 5th Earl Sondes Milles-Lade who died in 1996.
Marriage and Issue
In 1634, the Hon. Thomas Greene married Anne Gerard. Anne was a passenger on the Ark and the Dove said to have come over with her brother Sir Richard K.B. Gerard. Originally Anne was listed as Mrs. Anne Cox as a passenger on the Ark and the Dove, but research has begun on the theory that she was most likely the sister of Sir Richard K.B. Gerard who made the voyage as well. Author Harry Newman states that "Mistress Ann Cox" was one of the few "gentlewomen" on the initial voyage of the Ark and the Dove that sailed from England to Maryland. Another author, Edwin W. Beitzell, states that Ann Cox was actually Ann Gerard, sister of Richard and Thomas Gerard who also arrived in Maryland on the Ark and Dove. He states that she was the widow of someone named Cox. However, he does not give a source for that statement or relationship. On the other hand, "Mrs. Ann Cox" received a special grant of 500 acres (2.0 km2) of land from Lord Baltimore in 1633. The title "Mrs." in that land grant suggests that possibly Cox was a married rather than a maiden name. Thomas and Anne were wed in 1634 on the banks of the St. George River. Their marriage was considered to have been the first Christian marriage performed in Maryland and had issue.[2]
- 1. Thomas Greene (1635 - abt 1665)
- 2. Leonard Greene (1637–1688). Married Anne Clark and had issue. Leonard's godparent was Leonard Calvert. Their daughter Mary married Francis Marbury.
Thomas married Mistress Winifred Seybourne [Seaborne] (b. abt 1610, England) on 2 April 1643 and had issue. Mistress Winifred Seybourne emigrated to Maryland in 1638 who by her title indicated gentle birth and likewise one who arrived to the age of discretion to be recognized as a femme sole in matter of ethics and business. On 30 July 1638, she received 100 acres for transporting herself and another 100 for transporting Mistress Troughan. She emigrated, that is, financed her own passage thus indicating a lady of means.[2]
- 1. Robert Greene (1646–1716)
- 2. Francis Greene (1648–1707)
A third wife is often cited for Thomas Green, Millicent Browne. There is a Thomas and Millicent Green residing in Stafford County Virginia a few years after the death of Governor Thomas Green, therefore, Millcent Browne was not another wife of this Thomas.
The house Green's Inheritance was built by Francis Caleb Green, on part of the 2,400 acres (9.7 km2) of land granted in 1666 to the sons of Thomas Greene, the second Provincial Governor of Maryland. It was listed on the National Register of Historic Places in 1977.[15]
- 1. ^ Edward C. Papenfuse, et al. A Biographical Dictionary of the Maryland Legislature, 1635-1789. 2 Vols. (Baltimore: Johns Hopkins University Press, 1979, 1985), 373-4, 943; Maryland State Archives Online
- 2. ^ Newman, Harry Wright (1984). The flowering of the Maryland palatinate: an intimate and objective history of the Province of Maryland to the overthrow of proprietary rule in 1654, with accounts of Lord Baltimore's settlement at Avalon (Google eBook). Genealogical Publishing Com. pp. 213–219.
- 3. ^ Brugger, Robert J. (1988). Maryland: A Middle Temperament, 1634–1980. pp. 20-21. Baltimore: Johns Hopkins Press. ISBN 0-8018-3399-X
- 4. ^ Jordan, David William (2002). Foundations of Representative Government in Maryland, 1632-1715. Cambridge University Press. pp. 40–52. ISBN 978-0-521-52122-2.
- 5. ^ Radoff, Morris L. (1971). The Old Line State: A History of Maryland. Hall of Records Commission, State of Maryland. p. 248. ISBN 978-0-942370-07-2.
- 6. ^ Gambrill, J. Montgomery (1904). Leading Events of Maryland History. Ginn & Company. p. 37. Retrieved December 5, 2008.
- 7. ^ Hasted Hist. of Kent 6 (1798): 24–34, 201–202, 288.
- 8. ^ 'Parishes: Milton'. The History and Topographical Survey of the County of Kent: Volume 6 (1798). pp. 163–192. Retrieved 10 August 2010.
- 9. ^ Harry Wright Newman. The Flowering of the Maryland Palatinate, Genealogical Publishing Com, 1961. pg 213.
- 10. ^ Edward C. Papenfuse, et al. A Biographical Dictionary of the Maryland Legislature, 1635-1789. 2 Vols. (Baltimore: Johns Hopkins University Press, 1979, 1985), 373-4, 943.
- 11. ^ Douglas Richardson. Magna Carta Ancestry, 2nd Edition, Vol. II, p. 360.
- 12. ^ 'County of Kent: Beckenham', The Environs of London: volume 4: Counties of Herts, Essex & Kent (1796), pp. 291-306. British History Online Date accessed: 20 September 2012.
- 13. ^ The Ark and the Dove Adventurers By George Ely Russell, Donna Valley Russell
- 14. ^ England's topographer: or A new and complete history of the county of Kent; from the earliest records to the present time, including every modern improvement. Embellished with a series of views from original drawings by Geo. Shepherd, H. Gastineau, &c. with historical, topographical, critical, & biographical delineations by William Henry Ireland
- 15. ^ "Maryland Historical Trust". Green's Inheritance, Charles County. Maryland Historical Trust. 2008-06-08.
Early Families of Frederick County, Maryland, and Adams County, Pennsylvania by Steve Gilland
Political offices
Provincial Governor of Maryland (1647-1649)
- Preceded by Leonard Calvert
- Succeeded by William Stone
Thomas Greene Esq., Proprietary Governor of Maryland
- In office: 9 June 1647[1] – 26 April 1649[2]
- Preceded by Leonard Calvert
- Succeeded by William Stone
- Personal details
- Born 1610 - Bobbing Manor, Bobbing, Kent, England
- Died 20 January 1651 - St. Mary's County, Maryland
- Spouse(s)
- 1. Anne Gerard
- 2. Winifred Seybourne
- Religion Roman Catholic
Green, Thomas, Governor,St. Mary's Co.,18th Nov., 1650. After reserving a livelihood for himself, assigns to his friends Henry Adams and James Langworth entire estate, real and personal, for benefit of wife Winifred and children Thomas, Leonard, Robert and Francis; but desires wife afsd. to have full possession during her life, except that a certain amount of tobacco is to be given to friend Thos. Copley. Wife to give to sons afsd. designated shares in succession. In event of death of wife and of children without issue, ¾ of estate to be given to charity and balance to Henry Adams and James Langworth afsd. Test: Richd. Willan, Alice Smith. Pat. Rec. 1, 188
Thomas Greene, 2nd Proprietary Governor of Maryland's Timeline
1609 |
March 27, 1609
Bobbing, Kent, England
1635 |
Age 25
1637 |
Age 27
St. Mary's County, Province of Maryland
1648 |
Age 38
Great Mills (Greens Rest), St. Mary's County, Province of Maryland
Age 38
Near St. Mary's City, St. Mary's County, Maryland
1651 |
January 20, 1651
Age 41
St. Mary's County, Province of Maryland
???? |
???? |
St. Mary's City, St. Mary's County, Maryland, United States


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Kristina Krause gave props (27 Jul 2012):
Another shot with wonderful lighting.....Beautiful in black and white as well.....


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In Reply to: Update on effects of apomorphine posted by Bruce on September 29, 2000 at 23:48:40:
: The board is looking a little listless, so I thought I would share a commebt I read about the effect of apomorphine on the sex drive. The comment said the pwp "must show some restraint" after starting on the drug. Have a good one. Bruce
That Is a good one!
Betty H.


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Critical Care and Trauma
Staff in intensive care units are constantly faced with the challenge of making critical decisions quickly and accurately. Our research is designed to provide them with the evidence they need make the best decisions as often as possible. We do this by conducting high-quality research, multi-national, large-scale and investigator-led, in areas where evidence is lacking or is insufficient.
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Vic Goel is Managing Partner of Goel & Anderson, LLC. His practice includes strategic immigration planning facilitating the recruitment and hiring of international professionals, skilled technicians, managers, executives, and students. His clients include multinational information technology companies, telecommunications providers, biotech and engineering firms, insurance and financial services firms, manufacturing entities, and luxury hotel chains all of which rely on international personnel to meet their worldwide staffing needs. Vic focuses on the development of management plans that take an enterprise-wide approach to handling a client's needs, allowing companies to hire international staff in a timely and cost-effective manner. His innovative immigration strategies have resulted in his clients saving of millions of dollars and untold man-hours.
Vic is an active speaker and writer on immigration law and appears as a featured and keynote speaker on immigration issues at national and international industry meetings and trade association conferences. He has been interviewed on immigration issues by the NBC Nightly News, and his articles and quotations have appeared in print and online forums such as The Wall Street Journal, The Washington Post, CNN.com, ComputerWorld magazine, SiliconIndia magazine, the Times of India and India Abroad, among others.
In addition to being a longtime member of the American Immigration Lawyers Association, Vic is also an active member of the Technology Association of America's Immigration Policy Committee, the Compete America coalition, and the International Bar Association. He also provides advisory information on the intersection of immigration policy and foreign trade policy to business and trade associations around the world.


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Thursday, August 02, 2007
Kiss Kiss
13 comments:
Quit your joblah. Be a nipple pin up boy full time! :-) You're right, looks burnt in the photo but it wasn't burnt at all.
Sounds like top secret stuff! Do you don a disguise too? I'm thinking blonde wig, sunglasses and trench coat! hahaha. The most conspicuous disguise ever!
Spoken like a mum! How to keep your whites white?! ;-) Its true lah. I was thinking how nice it would be to have a white kitchen until I saw how hard it was to maintain! Forrrget it! See you later for some torture!Oh they're definitely targetting the women, alright. From the all white decor to the dainty cupcakes to the fairy lights....hehe...can't imagine a bunch of masculine men saying, "Oooh, let's go to Bisou for a drink"...LOL (trying to imagine Bald Eagle and Hunky and Splashie Boy agreeing to go there for a man's night out hahaha).
ReplyDeleteWah Joe! 2.5k just to flash your nipples? Hmmmm, might scare my clients away wor...
I love xmas. Everyone is so much more cheerful around that time.
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text: Use mouse scroll wheel over image or pinch-to-zoom on touch devices. You can also click and drag around on image. Park it 1 1 Follow La Raiz BMW R100/7 Parked to BMW Motorcycles by Goodhal Garage For some reason, scrambler style bikes really don't appeal to me. Maybe it's because .... (Read More At Link) Vehicle Info: BMW R100/7 Keywords La Raiz Motorcycles Scrambler Sign up to add your own keywords More from this Garage: More from this Profile: Garage Aprilia Motorcycles Garage BMW Motorcycles Garage BSA Motorcycles


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Browne, Cameron B. (2007) Harmonograms. Computers & Graphics, 31(2), pp. 292-300.
PDF (806kB) |
Harmonograms are visual designs based on harmonic analyses of strings of characters. Fourier descriptors are synthesized according to character positions and values, and then traditional methods are used to generate the resulting curves. Undersampling introduces visual artifacts that actually enhance the final designs. While their primary use is for the creation of artistic designs, harmonograms may have a practical application as a method for encoding and decoding information via the frequency domain.
Impact and interest:
Citation counts are sourced monthly from Scopus and Web of Science® citation databases.
These databases contain citations from different subsets of available publications and different time periods and thus the citation count from each is usually different. Some works are not in either database and no count is displayed. Scopus includes citations from articles published in 1996 onwards, and Web of Science® generally from 1980 onwards.
Citations counts from the Google Scholar™ indexing service can be viewed at the linked Google Scholar™ search.
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Full-text downloads displays the total number of times this work's files (e.g., a PDF) have been downloaded from QUT ePrints as well as the number of downloads in the previous 365 days. The count includes downloads for all files if a work has more than one.
ID Code: | 15015 |
Item Type: | Journal Article |
Refereed: | Yes |
Additional Information: | Figures are at the end of the author manuscript. |
Keywords: | Fourier descriptor, Harmonic series, Harmonogram, Undersampling, Art |
DOI: | 10.1016/j.cag.2006.10.002 |
Subjects: | Australian and New Zealand Standard Research Classification > STUDIES IN CREATIVE ARTS AND WRITING (190000) > VISUAL ARTS AND CRAFTS (190500) Australian and New Zealand Standard Research Classification > INFORMATION AND COMPUTING SCIENCES (080000) > COMPUTER SOFTWARE (080300) Australian and New Zealand Standard Research Classification > MATHEMATICAL SCIENCES (010000) > PURE MATHEMATICS (010100) > Algebraic and Differential Geometry (010102) |
Divisions: | Past > QUT Faculties & Divisions > Faculty of Science and Technology |
Copyright Owner: | Copyright 2007 Elsevier |
Copyright Statement: | Reproduced in accordance with the copyright policy of the publisher. |
Deposited On: | 03 Oct 2008 00:00 |
Last Modified: | 09 Jun 2010 13:05 |
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In this romantic comedy-drama, two people whose lives were touched by the same tragedy find love. Buddy Amaral (Ben Affleck) is a successful L.A. advertising executive who has a way with the ladies, but inside he longs for a meaningful long-term relationship. One day Buddy sells his seat on a sold-out airline flight to a stranger; he's shocked when the jet crashes and the man is killed. A year later, still haunted by the incident, Buddy looks...more
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Lot 785: 1872-1920's collection written up in four Senator albums from 187
Postage Stamps & Postal History of the World
by Corbitt Stamps Ltd
10 November 2016
Newcastle upon Tyne, United Kingdom
Looking for the realised and estimated price?
Description: 1872-1920's collection written up in four Senator albums from 1872 Eagle with Small Shield vals to 5g U, Large Shield to 5g, a few covers/postcards, 1880's issues on covers/cards, 1880-87 vals to 50pf (3) M, & FU range to 50pf, strength in Germania issues both on & off cover/packet cards etc, also many marginal provisional blocks, H.A Numbers, booklet panes & three complete booklets etc. Nice lot, viewing recommended.
Notes: Philatelic
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In Banff
Begin your day by devouring a pile of pancakes and maple syrup at the annual pancake breakfast. Stomach full, make yourself comfortable in Central Park as local musicians and cultural performances fill the valley with sound from noon until late. During the intermission, take in the colour and energy of the famous Canada Day parade down Banff Avenue, before settling into the park again for the remainder of the evening performances.
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The Green Party invited President Barack ObamaBarack ObamaCoal executive: Trump 'can't bring mining jobs back' Nunes was on WH grounds day before announcing Trump surveillance info Graham: Left is 'going insane' after Trump's win MORE's green-jobs czar to join their ranks, possibly as a future presidential candidate, after he stepped down last Sunday following controversial statements and activities.
Van Jones had recently come under fire for making derogatory comments about Republicans, calling them "a—holes," earlier this year, and likening former President George W. Bush to a "crackhead" in a speech captured on YouTube.
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