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Barack Obama just finished his big address on race and politics in Philadelphia. This was a big one for him, as he's been forced to address many racially charged issues in the past week because of his friendship and affiliation with the controversial Reverend Jeremiah Wright. Wright is Obama's pastor and officiated his wedding with Michelle Obama. He's also blamed the United States for 9/11, the AIDS virus, and "creating a racist society." In the lull before the Pennsylvania primary on April 22, this has become the main political plotline of the Democratic contest. Today, he addressed these issues and the broader scale of racial tension in America. It was strikingly reminiscent of Mitt Romney's much-touted "Faith in America" address. Beginning with a discussion of the Declaration of Independence and a nod to Obama's mixed heritage, it honestly bared the anger and confusion (and roots thereof) that black and white people still face in America today. Some highlights:
• "For as long as I live I will never forget that in no other country on earth is my story even possible," he explained, referencing the slave ancestry in his wife and daughter's heritage.
• He exclusively referred to Reverend Wright as his "former pastor." He also conceded that he had heard him sermonize controversial ideas but compared it to the many Americans who have heard similar things from their own priests, rabbis, and religious leaders. He called Wright's opinion "a profoundly distorted view of this country."
• But he added that "[Wright's church] embodies the black community in its entirety." He read a passage from his book, Dreams From My Father, that explained his first experience in the Trinity United Church.
• "As imperfect as he may be, he has been like family to me. He strengthened my faith," Obama explained. "I can no more disown him than I can disown the black community. I can no more disown him than I can disown my white grandmother, a woman who once confessed her fear of black men who pass her on the street." [OMG! That's just like our white grandmother!]
• He explained the roots of the quiet anger still simmering in middle-class black families over the social injustices of the twentieth century and compared it to the frustration of similar white families. "The anger is real, it is powerful," he said. "And to simply wish it away, to condemn it without understanding its roots, serves only to widen the chasm of understanding between the races."
• Obama also reminded listeners of his main campaign message: "The profound mistake of Reverend Wright's sermons is not that he spoke about profound racism in our society, it's that he spoke of our problems as if it was static." After a long pause, he continued. "We know, because we have seen, that America can change. What we have already seen has given us hope, and the audacity to hope."
• He closed by challenging voters and the press not to defer discussions over race to a later date, but to face them now in order to come together to solve larger problems. "The children in America are not 'those people's kids,'" he said, raising his voice. "They are our kids."
What did you think? Was all this honesty and difficult subject matter the right thing for Obama to bring up right now? Or will it change the way people view his candidacy for the worse? Let us know in the comments.


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Sunday, December 29, 2013
Carolina Clear, Clemson Universitys stormwater pollution education and awareness program, wants to gauge what Lowcountry residents understand about local water quality and what impact their actions can have on these resources.
During the next four weeks, through a partnership between Clemson and George Mason University, students will conduct telephone surveys with households in Berkeley, Charleston and Dorchester counties to better understand what information and educational programs are needed to help protect the areas valuable water resources.
Carolina Clear wants to gauge what Lowcountry residents understand about local water quality.
The surveys will be conducted from 5 to 9 p.m. Mondays to Fridays and 10 a.m. to 5 p.m. Saturdays. Each survey is designed to last no longer than 15 minutes. The goal is to have 400 residents complete the survey.
The purpose of the surveys is three-fold, said Katie Giacalone, Carolina Clears statewide coordinator.
First, the surveys will yield a better understanding of how South Carolinians utilize local waterways, whether for recreation, fishing, commercial means or other uses. This information helps watershed managers know who their audiences are and how much they value clean water, Giacalone said.
Second, the survey will illustrate what people know about how their actions affect local water quality.
Whether we know it or not, we all generate polluted runoff, Giacalone said. From not picking up after our dogs to coolant that drips from our car, stormwater pollution is people pollution, and we all can play a meaningful role in keeping South Carolinas waters clean.
The third way the survey will be utilized is to measure program impact over time, which is meaningful for federal stormwater regulatory compliance, she said.
Through area consortia and local partnerships, Carolina Clear works with communities to meet these permit requirements and in the end minimize polluted stormwater runoff by educating and involving the public about how to keep water in the states streams, rivers and basins as clean as possible for now and future generations.
Carolina Clears Lowcountry consortium is Ashley Cooper Stormwater Education Consortium.
In the coming months, Carolina Clear will conduct a similar survey in the Upstate. Surveys of Midlands, Pee Dee- and Grand Strand-area residents also have conducted.
Preliminary results from the surveys will be available to the public in the winter of 2014 through the Carolina Clear website, local newsletters and presentations. A full report will be published in the summer of 2014.
The Berkeley Independent is pleased to offer readers the enhanced ability to comment on stories. We expect our readers to engage in lively, yet civil discourse. We do not edit user submitted statements and we cannot promise that readers will not occasionally find offensive or inaccurate comments posted in the comments area. Responsibility for the statements posted lies with the person submitting the comment, not The Berkeley Independent.
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subset: commoncrawl


text:
Ni no Kuni: Wrath of the White Witch - Story Trailer
A story trailer in English for Ni no Kuni: Wrath of the White Witch.
by Mike Tao on
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The best part of Ni No Kooni is when the cheese head dripped snot on the dragon
I believe I know the next game I'm buying
an RPG with quality of Ghibli story telling is priceless...
this game reminds me of those cartoons i used to watch when i was 6-7, and used to spend hours watching them, now i am living them on my HD Screen, look at this game as a life, a life you will live in your imagination....an intresting one.....Bravo Namco Bandai...
this has not happend in years but the music actualy brought a tear to my eyes.
@sharky131 *actually


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Pupils wear red to aid disaster relief
Posted: February 14, 2014|
A SCHOOL held a 'wear red' non-uniform day on Friday which has raised £700 for charity.
Cakes were also on sale at lunch at Ivanhoe College, in Ashby, and two of its pupils, Euan and Alex, were responsible for organising the event.
Half the money raised will go to RedR - is an international disaster relief charity that helps to save lives around the world by training aid workers and providing skilled professionals to humanitarian programmes worldwide.
The remaining money will go towards funding Euan and Alex's trip to the 23rd World Scout Jamboree in Japan.
Many donations were also made to the Ashby Food Bank which will go towards supporting those who need food in the local area.
Anne-Marie Blewitt, principal, said "We're very proud of our students, especially Euan and Alex, who have taken the initiative to organise today. Alongside providing the highest standards of education Ivanhoe College is keen to raise money for charities and support those that need help in our local community."


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Reflection amid resurgence
Former Duke football players gathered at the Westin Hotel a few blocks from Bank of America Stadium on Wednesday.
Current Duke coach David Cutcliffe was more than glad to meet them and share his team's moment.
These moments, you see, haven't happened often for Duke football.
Tonight, for the first time since Jan. 2, 1995 and only the third time in the last half-century, Duke will participate in a postseason football bowl game when the Blue Devils face Cincinnati in the Belk Bowl (6:30 p.m., ESPN).
"We've come a long way," Cutcliffe said Wednesday. "This is the third bowl game in 50 years, so it's not like it's a recent downturn."
Cutcliffe took on this task in December 2007 when he was hired at Duke's football coach. The team had won 10 games over the previous eight seasons and didn't even have a full-length practice field at its disposal.
But Cutcliffe's goal was to get Duke back to the postseason. He recruited players to Duke talking about that very possibility, as remote as it seemed to them at the time.
"You could see that a lot of work needed to be done," said Duke defensive end Kenny Anunike, who signed with the Blue Devils in February 2008.
That work got done – slowly, in fits and spurts – over the past five seasons. Duke won nine games over Cutcliffe's first two seasons and appeared ready to take the big step toward bowl eligibility.
Still, Cutcliffe had to keep selling his program to anyone who would listen as he tried to bring larger crowds to outdated, mostly uncomfortable Wallace Wade Stadium.
"Everybody says change the culture, we really had to change the culture and it wasn't just our team," Cutcliffe said. "We had to change expectations from our fans, almost teaching fans how to follow major college football."
Back-to-back 3-9 seasons in 2010 and 2011, when the Blue Devils managed only one ACC win in each of the two seasons, represented a step back on the field.
But last spring, Cutcliffe said, he and his coaching staff looked at the roster and harbored serious hope of a breakthrough.
"As we started spring practice and came out of it, I don't think there was a player or coach who didn't expect we'd be somewhere in the postseason," Cutcliffe said. "We knew we had a good football team. We had all the ingredients."
Duke had experienced, accomplished skill players on offense in quarterback Sean Renfree, wide receiver Conner Vernon and running back-turned-wide receiver Desmond Scott. All three seniors had started in the previous three seasons.
On defense, the Blue Devils had an emerging star in cornerback Ross Cockrell, who after two up-and-down seasons as a starter became a first-team, all-ACC selection this season as a junior. Cockrell played alongside seniors Walt Canty, Jordon Byas and Lee Butler in the secondary.
Heavy attention in recruiting brought more talent and depth to Duke's defensive line.
Still, getting to six wins and bowl eligibility would not be easy.
The team was stunned on July 4 when sophomore wide receiver Blair Holliday, the team's offensive most valuable player in spring practice, suffered a traumatic brain injury in a personal watercraft accident on Lake Tillery. Holliday remained near death at UNC Hospitals for weeks before beginning a remarkable recovery that has him hopeful of returning to school soon.
Duke sophomore wide receiver Jamison Crowder was piloting the other personal watercraft that collided with the one Holliday was controlling. Crowder's grief at injuring his friend was deep, but he eventually worked through the emotional toll to have a breakout season on the field with 70 catches for 1,025 yards and eight touchdowns.
A mountain of other injuries, mainly but not limited to the defense, had Cutcliffe and his staff mixing and matching parts to hold together game plans all season.
By winning six times in the first eight games of the season, including a dramatic last-minute, 33-30 win over rival North Carolina on Oct. 20, Duke had won more games than in any season since 1994.
The goal of being bowl eligible had been reached.
"The thing that we didn't know that made it more satisfying is that we'd go through one of the more challenging years of any team I've been on or any time I've followed," Cutcliffe said. "I think it's a great tribute to the character of this team."
The former Duke players who understand what Cutcliffe and this team has accomplished traveled to Charlotte to be part of today's historic bowl game. Only eight other Duke teams before this one have played in bowl games.
Tonight, in the 100th season of Duke football, the Blue Devils appear in a bowl game for the ninth time.
The current Duke players and coaches have been in Charlotte participating in Belk Bowl festivities since Saturday. The former players joined the party on Wednesday.
This year's Blue Devils plan to give them a good show.
"Guys are getting more locked in," Canty said. "We've got the bowl events behind us. It's time to focus on football."


text:
A dual-mode radiotelephone capable of operation in analog or digital modes. According to exemplary embodiments, a digital signal processor receives a speech signal to be transmitted in the digital or analog mode and generates In-phase (I) and Quadrature (Q) modulating signals. The I and Q signals are supplied to a quadrature modulator for generating a digitally modulated signal and are supplied to an analog modulator for generating an analog modulated signal.
1. A radio transmitter/receiver for selectively transmitting digitally modulated signals in a digital mode or analog modulated signals in an analog mode comprising:
digital signal processing means having an input for receiving an information signal, a first output for supplying an In-phase modulating signal I and a second output for supplying a Quadrature modulating signal Q;
quadrature modulation means coupled to the first and second outputs for digitally modulating a carrier frequency in the digital mode to produce a digitally modulated signal; and
analog modulation means coupled to the first and second outputs for generating an analog modulation of a carrier frequency in the analog mode to produce an analog modulated signal, wherein said In-phase modulating signal I and said Quadrature modulating signal Q bypass said quadrature modulation means in order to produce said analog modulated signal.
2. The radio transmitter/receiver of
3. The radio transmitter/receiver of
4. The radio transmitter/receiver of
5. The radio transmitter/receiver of
6. The radio transmitter/receiver of
7. The radio transmitter/receiver of
8. The radio transmitter/receiver of
9. The radio transmitter/receiver of
10. The radio transmitter/receiver of
11. The radio transmitter/receiver of
12. The radio transmitter/receiver of
13. The radio transmitter/receiver of
14. A radio transmitter/receiver for selectively transmitting a bandwidth-compressed digital speech signal or an amplitude-compressed analog speech signal comprising:
analog-to-digital conversion means having an input for receiving an analog speech signal and an output for producing a sample stream of numerical samples representative of the analog speech signal;
digital signal processing means having an input for receiving the sample stream and one or more outputs for supplying an In-phase modulating signal I and a Quadrature modulating signal Q, the digital signal processing means converting the sample stream into a bandwidth-compressed and coded digital speech signal and an I and a Q sample stream representative of a digital vector modulation of the bandwidth-compressed digital speech signal or a numerical stream on at least one of the outputs representative of an amplitude-companded version of the analog speech signal;
digital-to-analog conversion means for converting the I and Q sample streams to associated I and Q analog modulating waveforms;
quadrature modulator means coupled to the digital-to-analog conversion means for vector modulating a carrier frequency with the I and Q analog modulating waveforms for transmitting the bandwidth-compressed digital speech signal; and
analog modulation means coupled to the digital-to-analog conversion means for producing an analog modulation of a carrier frequency using at least one of the I or Q analog modulating waveforms for transmitting the amplitude-compressed analog speech signal.
15. The radio transmitter/receiver of
16. The radio transmitter/receiver of
17. The radio transmitter/receiver of
18. The radio transmitter/receiver of
19. The radio transmitter/receiver of
20. The radio transmitter/receiver of
21. The radio transmitter/receiver of
22. The radio transmitter/receiver of
23. The radio transmitter/receiver of
24. The radio transmitter/receiver of
25. An apparatus for alternatively modulating a carrier signal with an analog signal or a digital signal, comprising:
digital signal processing means for generating a first pair of delta-modulation bitstreams representative of either a balanced In-phase component of a digitally modulated signal or an unbalanced high-frequency component of an analog frequency modulated signal plus an In-phase balanced low-frequency component, and a second pair of delta-modulation bitstreams representative of either a balanced Quadrature component of a digitally modulated signal or a balanced Quadrature low-frequency component of an analog modulation waveform;
Quadrature modulator means, responsive to the balanced In-phase and Quadrature signals, for Quadrature-modulating the carrier signal; and
frequency modulation means responsive to the unbalanced high-frequency component for frequency modulating the carrier signal,
wherein the carrier signal is either quadrature modulated with a digital modulation signal or frequency or phase modulated with both a low-frequency and a high-frequency component of an analog modulation signal.
26. The apparatus of
27. A radio transmitter/receiver for selectively transmitting digitally modulated signals in a digital mode or analog modulated signals in an analog mode comprising:
a digital signal processor having an input for receiving an information signal, a first output for supplying an In-phase modulating signal I and a second output for supplying a Quadrature modulating signal Q;
a quadrature modulator coupled to the first and second outputs for digitally modulating a carrier frequency in the digital mode to produce a digitally modulated signal;
a selecting unit coupled to the first and second outputs for selecting said In-phase modulating signal I and said Quadrature modulating signal Q and generating a modulating waveform, or a combining unit coupled to the first and second outputs for combining said In-phase modulating signal I and said Quadrature modulating signal Q and generating a modulating waveform; and
an analog modulator for receiving said modulating waveform and producing an analog modulated signal.
28. The radio transmitter/receiver of
29. The radio transmitter/receiver of
wherein one of said In-phase modulating signal I or said Quadrature modulating signal Q is used to frequency modulate the voltage controlled oscillator while the other signal is injected into a synthesizer loop controlling the voltage controlled oscillator.
30. A method for selectively transmitting digitally modulated signals in a digital mode or analog modulated signals in an analog mode comprising the steps of:
phase receiving an information signal in a digital signal processor and generating an In-phase modulating signal I and a Quadrature modulating signal Q;
determining whether a digital mode or an analog mode has been selected;
digitally modulating, in a quadrature modulator, a carrier frequency to produce a digitally modulated signal if said digital mode has been selected;
selecting, if said analog mode has been selected, an In-phase modulating signal I or a Quadrature modulating signal Q, or combining an In-phase modulating signal I and a Quadrature modulating signal Q, to produce a modulating waveform; and
generating, in an analog modulator, an analog modulation of a carrier frequency to produce an analog modulated signal using said modulating waveform if said analog mode has been selected.
31. The method of
upconverting said digitally modulated signal, if said digital mode has been selected, from a first frequency to a second frequency; and
upconverting said analog modulated signal, if said analog mode has been selected, from a third frequency to a fourth frequency.
The present invention generally relates to radio transmitters capable of both digital and analog modulation for impressing information on the transmitted signal, and in particular to personal portable communications devices such as cellular phones using frequency modulation or quadrature modulation.
In U.S. Pat. No. 5,745,523, filed Oct. 27, 1992, the entirety of which is incorporated herein by reference, a dual mode radio apparatus having both a digital information transmission mode and an analog transmission mode is described. The modulation in either the digital or analog mode is applied by first computing In-phase (I) and Quadrature (Q) signals representative of the desired modulated signal vector and applying the I,Q signals through I and Q D/A converters to a quadrature modulator.
U.S. Pat. No. 5,020,076 to Cahill discloses a hybrid modulation apparatus that in a digital modulation mode applies I,Q modulation to a quadrature modulator, and in an analog modulation mode applies an analog frequency modulation waveform to a phase lock loop to generate a signal which is then passed straight through an I,Q modulator which is biased with constant I,Q signals.
It would be desirable to generate the analog modulation waveform needed in the Cahill method by using a digital signal processor employed for digital modulation to compute a sampled digital representation of the analog modulation waveform, and then converting the digital representation to the required analog modulation waveform using either the I D/A converter or the Q converter or both.
It would further be desirable for an analog modulation implementation to avoid the Cahill technique of passing the modulated signal through a permanently-biased I,Q modulator, since the Cahill method may sometimes result in a digital modulation frequency which is undesirable for analog modulation.
The present invention is directed toward a transmitter/receiver, such as a radiotelephone, which is capable of operating in two modes. In a first mode, the transmitter signal is modulated with digital information. Specifically, a digital signal processor computes sampled digital representations having a real or In-phase waveform (I) and an imaginary or Quadrature waveform (Q).
After digital-to-analog conversion in respective I and Q D/A converters, a quadrature modulator impresses the I,Q signals on an intermediate radio frequency. The intermediate frequency is subsequently upconverted to a desired transmission frequency by a local oscillator signal from the radiotelephone receiver.
In a second mode, the transmitter signal is modulated with an analog signal. Specifically, the digital signal processor forms the analog signal by computing a sampled digital representation of the analog modulation signal. The sampled digital representation is converted to an analog waveform using either or both of the I or the Q D/A converter, and applied to an analog modulator to produce an analog modulated radio signal that may be at a second intermediate frequency. This second intermediate frequency signal is subsequently converted to the desired transmission frequency with the aid of a local oscillator signal from the radiotelephone receiver.
In a preferred implementation, both the digital modulation and the analog modulation are constant envelope modulations that vary only the signal's phase angle. A preferred method of transferring the desired angle modulation to the desired transmission frequency is to use a voltage-controlled oscillator to produce a signal at the desired transmission frequency and mix the signal with a local oscillator signal from the receiver to produce an intermediate frequency signal. The intermediate frequency signal is phase-compared with either a modulated or unmodulated reference signal to produce a feedback signal to control the oscillator to follow the desired angle modulation waveform. The feedback loop bandwidth is furthermore adapted according to the modulation mode selected either to follow digital modulation on the reference signal or not to follow analog modulation applied to the voltage controlled oscillator.
The invention will be more readily understood upon reading the following Detailed Description of the Preferred Embodiments in conjunction with the accompanying drawings, in which like reference indicia indicate like elements, and in which:
FIG. 1 is a block diagram of an exemplary dual-mode radiotelephone according to the present invention;
FIG. 2 is a block diagram of an exemplary quadrature modulator suitable for use in the radiotelephone of FIG. 1;
FIG. 3 is a block diagram showing an exemplary frequency assignment scheme in the radiotelephone of FIG. 1;
FIG. 4 is a block diagram showing exemplary upconversion circuitry suitable for use in the radiotelephone of FIG. 1; and
FIG. 5 is a block diagram of an alternative quadrature modulator suitable for use in the radiotelephone of FIG. 1.
Referring to FIG. 1, a dual-mode radiotelephone according to an exemplary embodiment of the present invention is shown. The dual-mode apparatus of FIG. 1 is suitable for selectively producing analog modulation when operating in a first frequency band or digital modulation when operating in a second frequency band. For example, the first frequency band may be an 800 MHz cellular band in which the analog modulation conforms to the U.S. AMPS standard while the second frequency band may be the 1900 MHz "PCS" band recently licensed by the FCC, which employs digital modulation according to the GSM standard.
A dual band 800/1900 MHz antenna 10 operates at both frequency bands. A band-splitting filter 11 separates signals in the two frequency bands for application to a diplexing filter 12 for the 800 MHz AMPS bands and a transmission/reception (T/R) switch 13 for the 1900 MHz band in which time-duplex is preferably employed. The signals output from diplexing filter 12 and T/R switch 13 are applied to the inputs of a receiver front-end 14 for amplification and downconversion to a suitable intermediate frequency or frequencies. The intermediate frequency signals are filtered and amplified in intermediate frequency processor 16 and may be digitized for digital signal processing in DSP 17. A suitable digitizing method is the logpolar digitizing technique described in U.S. Pat. No. 5,048,059, the entirety of which is incorporated herein by reference. Front-end 14 includes one or more local oscillators to provide mixing frequencies for downconversion, and outputs one or more local oscillator signals for use in the transmitter 15. The local oscillator signal frequency is controlled by frequency synthesizer 18 which is controllably programmed according to the selected channel frequency. The synthesizer preferably operates according to U.S. Pat. Nos. 5,095,288 and 5,180,993 which are hereby incorporated by reference and provides a fast locking capability from power up or on channel change to implement the standby power saving features described in U.S. Pat. No. 5,568,513 (Harte, Dent, Croft and Solve), filed May 11, 1993, which is also incorporated herein by reference. The synthesizer 18 may also contain circuits coupled to transmitter 15 for controlling the transmit intermediate frequency.
Transmitter 15 provides transmit power outputs at the analog and digital frequency bands. These outputs are fed to antenna 10 via diplexing filter 12 or T/R switch 13 respectively. T/R switch 13 is controlled by DSP and control processor 17 to allow either transmission or reception of TDMA signal bursts in an alternating manner known as Time Duplex. Transmitter 15 also receives either analog or digital modulation waveforms respectively from DSP 17 via the I-waveform connection 19 a or the Q waveform connection 19 b.
I-waveform modulation connection 19 a preferably supplies balanced I signals to transmitter 15 via two lines labelled I and {overscore (I)} in FIG. 1. Likewise, the Q-waveform modulation connection 19 b preferably supplies balanced Q signals to transmitter 15 via Q and Q. These signals are preferably generated by an I,Q modulator such as the one disclosed in U.S. Pat. No. 5,530,722 (Dent, filed Sep. 14, 1994) which is a continuation-in-part of U.S. Pat. No. 5,745,523 and is incorporated herein by reference in its entirety. U.S. Pat. Application No. 5,530,722 discloses the use of digital converters to generate balanced I/Q signals from a stream of binary words that numerically represent sampled I/Q waveforms, and high bitrate streams of single-bit samples and their complements, wherein the desired I or Q value is represented by the ratio of binary 1's to binary 0's in a stream. This allows the analog waveforms and their inverses to be recovered simply by low-pass filters, without the use of additional D/A converters.
The balanced, analog I,Q waveforms supplied to transmitter 15 are then fed to a quadrature modulator composed of an I modulator 15 a and a Q modulator 15 b to generate respectively a cosine waveform and a sine waveform at an intermediate transmit frequency TXIF. The I,Q modulator is preferably performed in transmitter 15, while the cos/sin TXIF signal generation may be contained in the transmitter 15 or alternatively in the receiver section 16, which will be described in more detail below with reference to FIG. 3.
As described in U.S. Pat. No. 5,745,523, the balanced I,Q waveforms represent digital information modulated in a digital transmission mode, or alternatively represent analog frequency modulation in the analog mode. It will be appreciated that the analog mode may conform to the U.S. AMPS standard or indeed any analog FM cellular standard including the British ETACS or Scandinavian NMT systems, all of which employ companding to compress amplitude variations of speech into a reduced dynamic range.
According to the present invention, an alternative analog modulation mode employing the I,Q modulation lines 19 a and 19 b from DSP section 17 can be achieved, wherein the analog modulation is not applied to the I,Q modulator but to a separate analog modulator. FIG. 1 shows an exemplary embodiment wherein the analog modulator is formed by combining one of the I,Q signals (here the I signal) supplied over an analog modulation input line 15 c with a phase lock feedback signal from synthesizer 18 in a loop filter 15 d. The choice to use the I signal is arbitrary, as the {overscore (I)} signal or one of the Q signals or both or all could be combined with the phase lock feedback signal in order to achieve analog frequency modulation. The choice of frequency modulation is also arbitrary and amplitude modulation could alternatively be used. The principle of the present invention is illustrated more generally in FIG. 2.
Referring to FIG. 2, it can be seen that DSP 17 includes digital signal processor logic 20 for computing either a sampled numerical I,Q representation of a digital modulation waveform or a sampled numerical representation of an analog modulation waveform. The result of the computation is applied to at least one of D/A converters 21 a and 21 b which preferably operate by converting an input to a high bitrate delta-sigma modulation signal and then low-pass filtering the signal in one of balanced low-pass filters 22 a and 22 b as disclosed in the patent applications referenced above. The D/A converted, balanced waveforms are applied to balanced modulators 27 a and 27 b which modulate respectively a cosine and a sine waveform at a first transmit frequency or an intermediate frequency TXIF(D) that is desired for the digital modulation mode. The digital modulation mode can be, for example, a GSM mode in which a speech encoder compresses the bitrate and thus the occupied transmission bandwidth for digital speech for transmission using time-duplex TDMA in the 1900 MHz PCS band; the modulation would be 270-833 kilobits per second for the GSM mode.
If the digitally modulated signal is first generated at an intermediate transmit frequency by quadrature modulator 25, it is upconverted to the desired final transmit frequency using an upconverter. For constant amplitude modulation schemes such as GMSK, only the phase of the signal is modulated and must be transferred to the output frequency, which can be performed by a phase lock loop as will be described-below with reference to FIG. 4.
FIG. 2 further shows that the I,Q signals produced by D/A converters 21 a and 21 b can be supplied via select/combine unit 24 to analog modulator 26 to produce an analog modulated signal at a desired frequency TXIF(A) for analog modulation. TXIF(A) can be either the desired transmission frequency or an intermediate transmit frequency signal, which is upconverted to the desired transmission frequency as will be described later with reference to FIG. 4. Select/combine unit 24 can be simply a hardwired connection between one of the I,{overscore (I)},Q or {overscore (Q)} signals and modulator 26, but can alternatively combine the I and {overscore (I)} (or Q and {overscore (Q)}) signals in a balanced to unbalanced converter, or perform more sophisticated combining of an I signal representing the coarse part of an analog modulation waveform with a Q signal representing the error between the coarse representation and the ideal waveform, in order to achieve a reduction in quantizing noise. Another method of combining separate I and Q signals to produce a desired modulation would be two-point frequency modulation of a frequency synthesizer, wherein one of the I or Q signals is used to frequency modulate a voltage controlled oscillator (VCO) while the other signal is injected into the synthesizer loop controlling the VCO to counteract the loop's tendency to correct the first signal's modulation of the VCO. Still another method of using I and Q signals to produce an analog modulated signal would include frequency modulating the signal with one of I or Q waveforms while using the other to determine the amplitude of transmission.
Any of the above methods of selecting one or more of the I,Q signals or using them in combination to effect analog modulation while bypassing the quadrature modulator 25 can be implemented in the present invention.
Referring now to FIG. 3, an exemplary frequency plan for a dual-band, dual-mode apparatus according to an embodiment of the invention is shown. To further enhance the present invention, as many components as possible are reused in both bands or modes in order to achieve the most economical design. In particular, it is desirable to employ a dual-frequency antenna (10 of FIG. 1), synthesizer 18, IF amplifier 16 etc. for both modes.
One problem in employing a single synthesizer 18 to provide both a first local oscillator frequency and to assist in generating the transmit frequency is that the duplex spacing (the frequency difference between transmit-receive frequency pairs) may not be the same in the digital and analog modulation mode, or in the 800 MHz cellular band compared to the 1900 MHz PCS band. The synthesizer 18 produces a local oscillator frequency (L01) that is higher (for example) than the receive channel frequency Frx by the desired first intermediate frequency IF1. To use the same value of L01 to produce the transmit frequency when operating in the same band (800 MHz or 1900 MHz) the apparatus must include means to offset L01 by an amount TXIF(A or D) to produce the desired transmit channel frequency Ftx. It can readily be seen that
Therefore DUPLEX SPACING=Frx−Ftx=TXIF−IF1 or alternatively TXIF=IF1+DUPLEX SPACING.
If substantially the same frequency IF1 is to be used in both modes, but the duplex spacing is different, then TXIF(A) in one mode will not be the same as TXIF(D) in the other mode. This hinders the use of the same I,Q modulator for modulation in both modes, as it may be difficult to produce an I,Q modulator that performs well at both TXIF(A) and TXIF(D). The actual duplex spacings are 45 MHz in the 800 MHz band and 80 MHz in the 1900 MHz band. Therefore TXIF(A) and TXIF(D) will differ by approximately 80−45=35 MHz if the same IF1 is to be used. It would of course be possible to configure a design which uses the same TXIF in both bands and modes, by instead allowing different IF1s. However, this hinders the use of common components in the receive path and increases cost and complexity. The preferred arrangement uses values of IF1 that are the same or nearly the same in both modes, thus allowing TXIF(A) and TXIF(D) to be separately adapted to produce the desired duplex spacings. This is facilitated by the invention which provides an economic way to perform analog modulation using a TXIF(A) that is different from the TXIF(D) employed by the quadrature modulator 25 for digital modulation.
FIG. 3 shows a preferred frequency plan based on a 13 MHz reference oscillator. 13 MHz is the basis for deriving the GSM bitrate (13 MHz/48) and the GSM channel spacing (13 MHz/65) in the 1900 MHz band. To obtain 30 KHz channel steps in the 800 MHz band, synthesizer 18 needs a reference frequency that is a multiple of 30 KHz, and preferably a multiple of 8×30 KHz in order to provide fast channel changing time and low phase noise by use of the fractional-N technique of incorporated U.S. Pat. No. 5,180,993. Neither 30 KHz nor 240 KHz divides into 13 MHz, but this problem is solved by multiplying the frequency from reference oscillator 30 by six in frequency multiplier 31 to obtain 78 MHz, which is 325 times 240 KHz. 78 MHz is also a convenient second local oscillator frequency for mixing signals at the chosen first IF frequency of 72 MHz down to a second intermediate frequency of 6 MHz in second mixer 33. The 6 MHz signal is then further amplified and filtered in second IF 34 to produce an output for digitizing and processing in DSP 17. The choice of second intermediate filter equal to 6 MHz allows the use of existing off-the-shelf filters available at that frequency, but it will be appreciated that other suitable frequencies may be chosen.
In the time-duplex TDMA digital mode (GSM at 1900 MHz), the duplex spacing is 80 MHz, which requires a TXIF(D) equal to IF1 (=72 MHz) plus 80 MHz, or 152 MHz. By further frequency doubling the 2nd local oscillator signal L02 from 78 MHz to 156 MHz, a useable TXIF(D) is obtained. The 4 MHz discrepancy between 152 and 156 MHz can be accommodated because transmission and reception do not take place at the same time. Therefore, using a fast switching synthesizer 18, the value of L01 may be changed 4 MHz between reception and transmission. To facilitate this, the phase comparator reference frequency used by synthesizer 18 in the digital mode is 1 MHz, derived by dividing the 78 MHz signal by 78 in reference divider 40. Fractional-N synthesizer circuit 41 then further interpolates by a factor of 5 to obtain the desired 200 KHz steps of GSM. In the analog mode, 30 KHz steps are obtained by first dividing 78 MHz by 325 in reference divider 40, then interpolating by a factor of 8 using the fractional-N synthesizer 41. Synthesizer 18 is appropriately programmed for these different modes and channel frequencies by control signals sent from control processor of DSP 17.
The frequency multipliers used to produce 78 MHz and 156 MHz can employ phase lock loops that divide an oscillator running at the desired frequency by 6 or 12 to produce a 13 MHz signal which is compared with the 13 MHz signal from oscillator 30 to produce a feedback control signal to control the oscillator to the desired multiple. For example, a 156 MHz signal can be produced in this manner and a 78 MHz signal can be derived from an intermediate divide-by-2 output of the loop divide-by-12 circuit.
The 156 MHz signal is modulated by digital information in the digital mode by I,Q modulator 25, which includes quadrature network 28 to generate cosine and sine waveforms. The modulated signal at TXIF(D) (=156 MHz) is then upconverted to the desired 1900 MHz band in the following manner applicable to constant envelope modulations: Voltage Controlled Oscillator 54 operates at the desired output frequency to drive transmit power amplifier 55. The output signal from oscillator 54 is mixed with the receive local oscillator signal L01 which has been sidestepped 4 MHz as described above during the transmit burst. The resulting signal after low pass filtering in filter 51 is at TXIF(D) and is phase compared in comparator 50 with the I,Q modulated signal at TXIF(D) from quadrature modulator 25. Comparator 50 generates a phase error signal which, after loop filtering using an integrator in filter 53 produces a control signal coupled to VCO 54 that controls its phase to follow the modulation imposed on TXIF(D) by modulator 25. In this way, the phase modulation is transferred to the transmit frequency.
In analog mode however, IF1 is chosen to be 72.06 MHz. This choice of an IF1 for analog mode that is nearly the same as for digital mode; however, the same IF1 of 72 MHz could have been chosen, or alternatively 71.94 MHz. Small differences such as 60 KHz in IF1 between analog and digital mode do not prejudice the use of the same 6 MHz IF amplifier 34 as its filter bandwidth is sufficiently broad to encompass 5.94 MHz as well as 6 MHz or 6.06 MHz.
The duplex spacing of 45 MHz in the 800 MHz band leads to a TXIF(A) equal to 72.06+45=117.06 MHz. This is a multiple (×1951) of 60 KHz and may easily be produced using auxiliary synthesizer 43, sharing reference divider 40 with main synthesizer 41. The auxiliary synthesizer may further divide the 240 KHz reference signal by 4 to obtain the desired 60 KHz reference signal, at which frequency it is phase-compared with the signal TXIF(A) divided by 1951.
An oscillator 64 running at the desired transmit frequency in the 800 MHz cellular band drives power amplifier 65 and is also coupled to mixer 62 where it is mixed against the receive local oscillator L01 operating at the appropriate frequency for reception in the 800 MHz band. The resulting signal at 117.06 MHz is applied, after low pass filtering in filter 61, to auxiliary synthesizer 43 where it is divided by 1951 to 60 KHz and phase compared to the 60 KHz reference signal to produce a phase error signal.
The phase error signal is filtered and integrated in loop filter 63 and then added to the selected I or Q or combined signal, the desired analog frequency modulating waveform to produce a control signal for oscillator 64. The control signal limits the oscillator 64 to the desired transmit channel frequency and modulates the oscillator 64 with the desired frequency modulation waveform.
It should be noted that while separate mixers 52,62, low-pass filters 51,61 and power amplifiers 55,65 are illustrated in FIG. 3, any or each pair can be combined to reduce complexity. For example, mixers 52 and 62 can be the same mixer, the selection of which is based on which of oscillators 54,64 was enabled to drive it. Had the value of IF1 for the analog mode been chosen instead to be 72 MHz, the value of TXIF(A) would be 117 MHz, which is 1950×60 KHz or 975×120 KHz. This would allow the choice of a 120 KHz phase-comparison frequency in the auxiliary synthesizer. Alternatively, the 117 MHz is nine times the 13 MHz reference crystal frequency, which can be generated using the same technique as for the 156 MHz TXIF(D). This would be a good choice if a quadrature modulator operating at both 117 MHz and 156 MHz used, together with I,Q modulation in analog mode. However, producing wideband I,Q modulators is difficult and costly, and therefore the exemplary embodiments of the present invention teach the use of one or more of the I,Q D/A converted signals as a conventional analog modulation signal applied to the auxiliary synthesizer loop. When the synthesizer loop is used to control a phase or frequency modulated signal, it is desirable to have a large division factor (1950) in the loop in order to reduce the amount of modulation reaching the phase comparator at 60 or 120 KHz. This is because a large phase error signal due to the modulation can cause distortion of the modulation frequency response or non-linear distortions due to non-linearities of the phase detector.
Thus, the exemplary frequency plan of FIG. 3 includes a range of options for the values of IF1 and TXIF(A) used in the analog modulation mode. The choice of IF1, in the analog mode to be 72.06 or 71.94 MHz can be useful also in the digital mode. According to the digital GSM standard, the cellular network radiates a special signal called the Frequency Correction Burst or Frequency Correction Channel (FCH) as part of the Broadcast Control Channel (BCCH). The FCH is an unmodulated TDMA burst. More precisely, the burst is modulated by an all-1's or all-0's pattern, which produces a CW carrier that is offset by Ľ of the bitrate, due to the characteristics of Gaussian Minimum Shift Keying modulation (GSMK). Since the bitrate is 13 MHz/48 (270.833 KB/s), the frequency is offset by +67.708 KHz. This is translated to the first intermediate frequency with a sign change if the receive local oscillator frequency L01 is greater than the receive frequency Frx. The FCH burst may be readily detected by using a narrow bandpass filter such as filter 38 of FIG. 3, centered on the offset frequency. Since the bandwidth of filter 38 is chosen to be approximately ±15 KHz for analog mode, it is approximately of the correct width to detect the FCH burst in digital mode, despite the selection of filter 38 to be centered on 72.06 with an FCH frequency of 72.067708 or 71.94 with an FCH of 71.932292 MHz. The error of +7.708 KHz is within the ±15 KHz bandwidth of the filter and so passes through to DSP 17 for detection. DSP 17 may digitally correct for the 7.708 KHz of error and may further reduce the bandwidth prior to detection. Detection can be performed by monitoring the signal energy out of the narrowband filtering to determine if it increases at the predefined FCH burst interval repetition rate compared to energy outside the FCH burst intervals. All possible interval timings can be explored. The timing which exhibits the greatest increase in narrowband energy is used to establish coarse TDMA network timing, and then other signal and message content are searched for in the BCCH signal.
FIG. 4 shows more detail of the upconversion process from intermediate transmit frequencies TXIF(A) or TXIF(D) to the final transmit frequency Ftx in either the 800 MHz or 1900 MHz bands.
Quadrature modulator 25 (FIG. 2), composed of balanced I-modulator 27 a and Q-modulator 27 b, is driven by cosine and sine outputs from Quadrature VCO 84 through buffers 86,87. A buffered output through buffer 85 is also coupled to divide by 12 circuit 81,83 having an intermediate divide by 2 output at 78 MHz coupled through buffer 82 to IF amplifier 16. This 78 MHz output is used in a second downconverting mixer in IF amplifier 16, which is preferably of the image rejection type. An image rejection mixer also requires cosine and sine injection waveforms at 78 MHz, and can be derived easily from the 156 MHz signal by producing a 78 MHz divide-by-2 output delayed by one half cycle of the 156 MHz waveform, as an undelayed output from buffer 82. The extra components for this embodiment are not shown in FIG. 4, but suitable components will be readily apparent to those skilled in the art.
The output of divide by 6 circuit 81 from 78 MHz is at 13 KHz, the same as the reference crystal oscillator signal frequency, with which it is compared in phase comparator 80 having a bipolar current-mirror output. A phase error signal output by comparator 80 is produced in the form of a current proportional to the phase error, which can be low-pass filtered and integrated using purely passive loop filter components 88. The filtered and integrated error signal is fed back to control QVCO 84 to the desired 156 MHz frequency. The loop is preferably a second order servo having a fast lock time that enables rapid power-up and power-down in order to reduce battery consumption by activating the entire QVCO and its control loop only during digital TDMA receive timeslots and digital transmit timeslots, or during analog receive periods. The duty factor during reception of the analog control channel, to which the apparatus listens on standby, may be minimized using known battery saving techniques.
The outputs of modulators 27 a, 27 b are summed through low-pass filter 51 and applied to phase detector 50, where the GMSK modulated signal is compared with a signal derived from transmit power amplifier 55 by downconversion against the receive local oscillator in mixers 52,62.
FIG. 4 illustrates the previously mentioned inventive feature of combining certain parts common to both frequency bands. Mixers 52,62 have been combined into a single mixer with selection of the signal source by the enable inputs of input buffers 521,621. When transmission in the 1900 MHz band is required, buffer 521 is enabled by a signal EN1900 from DSP 17 to allow a sample of the 1900 MHz transmit signal taken by coupler 552 to pass to the mixer 522. Alternatively the signal EN800 is activated to pass a sample of the 800 MHz signal to mixer 522. The local oscillator from dual-band front end 14 is selected at its source to deliver a signal appropriate to the selected band in order to convert the selected transmit signal frequency to the desired transmit IF TXIF(A) to TXIF(D). The converted signal output is low-pass filtered in combined filter 51,61 and fed by dual-output buffer 81 to both phase detector 50 and auxiliary synthesizer circuit 43 comprising divider 90, reference divider 91 and phase detector 92.
When a 1900 MHz transmit operation is selected, quadrature modulator 25 and phase detector 50 are powered up. Phase detector 50 compares the phase of the modulated TXIF(D) at 156 MHz with the output from buffer 89 to produce a current signal proportional to the phase error. The current is filtered and integrated using only passive filter components 53. Optionally, the phase lock time from power up can be minimized by recording previous voltages on loop filter capacitor 531 at the end of a TDMA burst transmission in a look-up table, versus channel frequency, within DSP/Control processor 17.
The previously digitized and stored voltage value is then recalled, D/A converted, and applied to principal integrator capacitor 531 to precharge the capacitor to approximately the correct voltage just before transmission of a TDMA burst on the same previous frequency, thus reducing relock time. When the loop is locked, the closed-loop bandwidth provided by loop filter 53 is preferably wide enough to cause the phase of the transmit signal sample to be controlled to follow the phase of the GMSK signal from quadrature modulator 25.
When transmission in the 800 MHz band is selected, the output from buffer 89 is divided by 1951 in programmed divider 90 and compared with a 60 KHz reference obtained by further dividing the 240 KHz output of divider 40 by four in divider 91. The comparison of the two 60 KHz signals in phase detector 92 produces an error current signal whose mean value is proportional to the phase error which can be low-pass filtered and integrated using passive loop-filter 63 to obtain a control signal for 800 MHz transmit VCO 64. Passive loop filter 63 includes components 634, 635, 633, 632 and 631 designed to filter a balanced I signal I′,{overscore (I)}′ from DSP 17 to produce the balanced I,{overscore (I)} drive signals from modulator 27 a as well as to filter common mode components of I′,{overscore (I)} with a different filter characteristic for injection into the loop via capacitors 634,635. The arrangement of this filter illustrates the option of using both I and {overscore (I)} signals to produce analog modulation. In this case, I′ and {overscore (I)}′ signals from DSP 17 are not complementary signals, but are selected to be the same or to have a sum or mean value representing the desired analog modulation. The phase lock loop filter will pass the modulation signals to VCO 64 causing phase or frequency modulation. The feedback signal from phase detector 92 will tend to counteract this modulation, but this tendency is reduced by divider 90. Nevertheless, the modulation at the lowest modulation frequencies will be partially counteracted, perhaps necessitating boosting the low modulation frequencies prior to D/A conversion in DSP 17. Such a boost combined with other filtering operations in the digital domain in DSP 17 are designed to achieve the overall modulation frequency response desired in analog FM mode, including pre-emphasis.
In one implementation PA 65, oscillator 64 and mixer 62 are constructed as a single unit using a Gallium Arsenide (GaAs) integrated circuit, while 55, 54 and 52 form a second GaAs circuit. Both GaAs circuits may also be combined into a single dual-band GaAs integrated circuit.
In the digital mode, loop filter 53 is preferably designed to obtain a closed loop transfer function broad enough to follow the digital modulation. In the analog mode, loop filter 63 is preferably narrow, so as to prevent the loop from attempting to correct for the impressed analog modulation. Specifically, by tailoring the characteristics with the loop integrating filters 53,63, the desired angle modulation is transferred to the oscillator at the output frequency while suppressing noise at other frequencies and in particular in the receive frequency band. A first loop filter characteristic is employed for AMPS modulation, which has desired modulation components only up to about 10 KHz, while a second loop filter characteristic is employed for a GSM 270.833 KB/S GMSK waveform that has desired components up to 150 KHz. The wider loop filter characteristic in the GSM case allows rapid acquisition of phase lock at the beginning of the TDMA burst such that the VCO accurately tracks the desired angle waveform only a few tens of microseconds after the circuit is enabled. The phase lock circuit may thus be powered down to save power during the receive part of the TDMA frame and powered up just prior to the transmit part of the frame.
The invention can include the use of an analog-to-digital converter to measure the loop filter integrator voltage at the end of a burst and to record the value numerically in a microprocessor memory against the channel frequency. When the same channel frequency is selected later, the voltage value is recalled and applied to a D/A converter to precharge the loop integrator, e.g., during the receive or idle part of the TDMA frame. Just prior to the transmit part of the frame, the D/A connection to the loop integrator capacitor is open-circuited (tri-stated) and the phase error current is used to finely adjust the oscillator control voltage under closed loop control. After transmission, the find-adjusted voltage may be read to overwrite the previous value in memory to provide continuous recalibration. This feature can be used to speed up phase lock acquisition and can also be used in the analog FM mode by recording the loop voltage against frequency eery time the transmitter is operated at any frequency.
An alternative embodiment incorporating the aforementioned Cahill disclosure is shown in FIG. 5. Control processor/DSP 17 in this case produces I′,{overscore (I)}′ and Q′,{overscore (Q)}′ signals which are filtered using balanced filter 63 a to obtain a first balanced, filtered signal I,{overscore (I)} to drive modulator 27 a, a second balanced filtered signal Q,{overscore (Q)} to drive modulator 27 b, and a common mode filtered signal I″ to inject into combined loop filter 53,63. In the digital mode, the common mode signal is suppressed by causing I′ and {overscore (I)}′ to be generated as complementary signals. In the analog mode, the balanced mode signal is suppressed by generating I′ and {overscore (I)}′ to be non-inverted signals. This results in modulator 27 a having nominally no output. The output in the analog mode is caused by supplying constant signals Q,{overscore (Q)}′ at their maximum complementary levels to allow the QVCO signal at 117 MHz to pass through Q-modulator 27 b at the same time the QVCO loop receives an injection of analog modulation from the common mode I′,{overscore (I)}′ signal. In addition, reference divider 40 and auxiliary divider 43 are programmed to different values depending on whether the digital or analog modulation mode is selected.
An improvement over Cahill may be achieved by programming DSP 17 to generate both analog and I,Q modulation substantially simultaneously. In this mode, high-frequency components of the desired analog modulation are generated in the common mode part of the I′,{overscore (I)}′ signals and modulate frequency or phase angle inside the QVCO loop. Low frequency components of the desired angle modulation which would otherwise be counteracted by the loop's feedback action are applied outside the loop by generating the balanced part of the I′,{overscore (I)}′ and Q′,{overscore (Q)}′ signals to be proportional to the cosine and sine respectively of the desired low-frequency phase modulation signal. In this way, phase modulation down to zero frequency can be obtained. Optionally Q and {overscore (Q)}′ can also be fed to loop filter (53,63) and the common-mode part of Q,{overscore (Q)}′ can be used together with the common-mode part of I′,{overscore (I)}′ to provide enhanced accuracy for frequency-modulation VCO 84. In general, the I signal can be generated as a delta-modulation representation of half the sum of a desired balanced (odd mode) and unbalanced (even mode) waveform, while {overscore (I)}′ is a delta-modulation representation of half the difference. Likewise, Q and {overscore (Q)}′ represent half the sum and half the difference of desired even and odd waveforms.
The selection of division ratios has been previously described. The selection of low division ratios 6 and 12 respectively results in a high loop bandwidth in the digital mode for controlling the frequency of QVCO 84 to 156 MHz. The selection of high division ratios 1300 and 1951 in the analog mode result in a low loop bandwidth for controlling QVCO 84 to 117.06 MHz. By suitably selecting division ratios and designing loop filters 53,63 according to well known techniques, different loop bandwidths may be produced even at the same intermediate transmit frequency (e.g., 117 MHz) in the case that analog and digital modulation was required in the same frequency band, for example for the purpose of implementing the dual-mode phone of U.S application Ser. No. 07/967,027. In that case, the modulation in digital mode is not a pure phase modulation but also includes amplitude modulation, so that upconverter 100 is a linear upconverter to the final transmit frequency, and power amplifier 551 is a linear PA.
The power amplifier requirements for implementing constant amplitude modulations as used in GSM and AMPS are easier than for the varying amplitude modulations used in D-AMPS, therefore it is preferable from a transmitter point of view to combine GSM and AMPS standards into a dual-mode phone. On the other hand, AMPS and GSM use different channel bandwidths and spacings of 30 KHz and 200 KHz respectively. From a receiver point of view it is, according to the prior art, preferable to use the same bandwidth in both modes. The inventive architecture of a dual mode phone disclosed here economically achieves both low cost, dual-band or single band, digital and analog modulation of the transmitter while accommodating both wide and narrow band filtering for reception of GSM, AMPS or D-AMPS respectively.
A further aspect of the present invention provides for facilitating the construction of radio transmitter-receivers, such as digital cellular phones or personal wireless communicators, that operate according to two different standards using non-integrally related bandwidths or bitrates.
In an exemplary implementation, a radio receiver for GSM and AMPS signals includes a reference clock at a frequency of 39 MHz, which is divided by 144 to produce a first sampling rate of 270.833 KS/S, or alternatively divided by 150 to produce a second sampling rate of 260 KS/S. When receiving GSM (digital) signals, the received signals are digitized by any suitable means (Cartesian or Logpolar) using the first sample rate, and when receiving AMPS (analog) radio signals the received signals are digitized using the second sample rate. The analog signal stream sampled at the second (260 KS/S) rate is then digitally filtered to narrow the receiver pass bandwidth to a value adapted to the AMPS mode, and simultaneously the sampling rate is reduced by downsampling to 80 KHz, being a convenient multiple of a 10 KB/S signalling rate used in AMPS and of a standard 8 KS/S speech processing rate for processing sampled and digitized (PCM) speech.
Downsampling in a digital filter is well known when the output sample rate is an integral submultiple of the input sample rate. In certain applications as exemplified above, it can be desirable to produce an output sample rate that is not an integral submultiple of the input rate, i.e. 80:260 or 4:13. The present invention provides a means in general to compute N output samples for every M input samples in a digital downsampling filter.
According to an exemplary embodiment, the inventive method comprises using N digital filters such as FIR filters each having an associated set of filter coefficients adapted to compute one output sample per M input samples. The coefficient are chosen such that the output samples computed by successive filters represent a filtered signal value at N successive time intervals equispaced over each period of M input samples. In an exemplary application, a 260 KS/S input sample rate is applied to four filters, each of which produces an output sample at a 20 KHz rate. The four 20 KHz streams may then be multiplexed to produce an 80 KS/S stream which is further processed to extract 10 KB/S Manchester coded and frequency modulated signalling data or 8 KS/S PCM speech which is then D/A converted using a PCM CODEC circuit to produce an analog speech waveform that is fed to an earpiece.
Many variations to the illustrative embodiments disclosed above will be readily apparent to a person skilled in the art without departing from the spirit and scope of the invention as defined by the following claims and their legal equivalents.
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Former Electronic Gaming Monthly editor Dan Hsu is profiled on Crispy Gamer. Scribe Kyle Orland serves up the questions and Shoe provides the answers. Here's a quick sample:
[the single biggest problem in game journalism today] could be the relationship the press has with the people and companies it's covering. Everyone likes to play so nice that they forget what they're supposed to be doing in the first place. So some writers are afraid to ask the tough questions, or to criticize what should be criticized, because they're afraid of backlash from the companies from a support standpoint, from an advertising standpoint or worse, from their own editors who don't want to piss anyone off. This may not be a blatant problem, but it's there, unspoken, hanging over everything in the industry.
Even big outlets like EGM feel that pressure. It's been hinted to me several times that some developers and publishers don't want to work with us because we're too tough or critical, that they'd rather work with others where they feel more in "control" over the message that would be getting out. I guess that's yet another reason I needed to get out and look for a change. This shit is just too frustrating, and I'm getting a little angry just thinking about all that BS in the business we had to put up with.
Shoe offers far more insights on Sore Thumbs, a highly entertaining - and informative - blog that he and another ex-EGMer, Crispin Boyer, are running.


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MAC Perky Lipglass Review, Photos, Swatches (Taste Temtpation)
MAC Perky Lipglass
Perk Up Your Winter with MAC's New Lipgloss
MAC Perky Lipglass ($15.00 for 0.17 fl. oz.) is described as a "mid-tone shimmering lilac." It's a light-medium lilac purple with lighter lilac and multi-colored shimmer. On my lips, it adds a light lavender color but it's the multitude of shimmer that really stands out. MAC Docile is lighter, less shimmery. MAC Gone Romancin' is lighter and more tinted. MAC Frozen Dream has less shimmer.
This is the third gloss from MAC's Taste Temptation Collection, which launched online this week and will hit stores and counters this Thursday. It's a semi-sheer gloss that adds a lot of shimmer, as the base color is fairly sheer. The base color lightens my natural lip color with a light milkiness that's tinted lilac. Lipglass is one of those formulas that runs from sheer to opaque and everything in-between. The consistency was a little thinner than the average Lipglass, though it was still tacky. It was also vanilla-scented but had no discernible taste. This shade lasted three and a half hours on me and was neither drying nor hydrating.
The Glossover
|The multi-colored shimmer makes it a great layering shade, and because there is so much shimmer, it can be worn on its own and doesn't look like just any ol' sheer gloss with shimmer.
|Login or Register to be able to add this to your Vanity or Wishlist! Plus rate and review!
See more photos & swatches!
MAC Perky Lipglass
MAC Perky Lipglass
MAC Perky Lipglass
MAC Perky Lipglass
MAC Perky Lipglass
MAC Perky Lipglass
Product & Review FAQ
Where can I purchase it? How much is it?
Is it limited edition?
Any dupes?
MAC Docile is lighter, less shimmery. MAC Gone Romancin' is lighter and more tinted. MAC Frozen Dream has less shimmer.
What makeup are you wearing?
On eyes: Lancome Petit Tresor Eyeshadow, Edward Bess Dusk Eyeshadow, Lancome Lumieres de Paris Les Paillettes, Burberry Trench Eyeshadow, bareMinerals 5AM Eyeliner, and bareMinerals Midnight Eyeliner. On cheeks: (your left) MAC Silver Dush Iridescent Powder, Kevyn Aucoin Natura, (your right) Chantecaille Rose Petals Highlighter Powder, Kevyn Aucoin Natura.
Discussion and debate are highly encouraged, and we expect community members to participate respectfully. When asking a question, please check the FAQ section (above) for information about purchasing, price, dupes, and the like. If you have general feedback or need technical support, please contact us.
Comments that include advertisements, self-promotion, insults, etc. may be in violation of our comment policy and subject to deletion. Please see our comment policy for more information.


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The annual Every Goal series will run Monday to Thursday through July and August, remembering every goal scored by the Canucks, player by player. Today, we take a look at Manny "Patch" Malhotra.
Odd as it may seem, Malhotra was an even more proficient, or at least efficient, goalscorer in 2011-12 than he was in 2010-11. Though he may have dropped from 11 goals down to 7, he did it with less ice time at even-strength while starting even fewer shifts in the offensive zone. He scored at a rate of 0.55 goals per 60 minutes of even-strength ice-time this season, up from 0.47 in 2010-11. Considering his role was almost purely defensive, starting only 88 of his even-strength shifts in the offensive zone all season, the fact he increased his goal rate is impressive.
It all sounds pretty good when you put it that way, but Malhotra didn't have a particularly good season. He received less ice time because he was bumped down to the fourth line. He didn't receive many offensive zone starts because he wasn't particularly useful offensively. And while it's nice to get 7 goals from a fourth liner, when that fourth liner is getting paid $2.5 million per season, you hope for more.
That said, Malhotra was still effective in his role as an enabler. No one else in the NHL came even close to his 13.2% offensive zone starts, the two closest being his linemates Dale Weise and Max Lapierre. Thanks to them, the Sedins and Burrows led the league in offensive zone starts, so at least a few of that trio's 72 goals can be attributed to Malhotra and co.
But this isn't about their goals. This is about Manny's goals. Here are all 7 goals Manny Malhotra scored this season.
Dan Hamhuis gets the ball rolling on Malhotra's first, anticipating a Ryan Wilson outlet pass up the middle and forcing a turnover. The play nearly ends second later, as Jannik Hansen makes a pass to Malhotra that would be in the back of the Avalanche net if not for a good pokecheck. But Malhotra doesn't quit on the puck, chasing it into the corner and throwing it down the wall. Seconds later, he's rewarded for his persistence by being cast as the toe in in a lovely tic-tac-toe. He even gets to victimizes Ryan Wilson a second time.
Malhotra victimizes another defender for his second. This time it's Douglas Murray, who learns the hard way that being the size of a Canyonero has its drawbacks when Malhotra banks a puck off his cuboid body for the goal.
Most of the time, Malhotra is the one doing the dirty work so Kesler can score, but here the script is flipped, with Kesler fighting off a man and muscling a puck to centre and Malhotra burying the puck into an empty net.
I love Malhotra's work on this goal. He gets a nice centring pass from Mike Duco, but the only reason he's available to receive it is the little juke he makes when he engages with Eric Brewer in front of the Lightning goal. He fakes right, then when Brewer goes for it, Malhotra puts his stick down on the opposite side and refuses to be moved. With inside position on Brewer, he's able to direct Duco's pass towards the net, then even fight Brewer off for the rebound.
Here's another instance of Malhotra outmuscling a man in front, as he gets position on Justin Falk and makes himself available for a feed from Kevin Bieksa. Like the goal preceding this one, there's nothing much the defender can do to prevent Malhotra from getting his stick on the puck, but unlike the goal preceding this one, Malhotra only needs one crack at it, redirecting the puck into the net.
Impressive as Malhotra's work on the last two goals may be, they're nothing compared to this beauty. Just as he did versus the Lightning, Malhotra makes like a wide receiver, faking left then going right, streaking to the net as Maxim Lapierre carries the puck in along the far wall. Then, still in football mode, Malhotra dives out to reach Lapierre's saucer pass, tipping it into the Leafs goal with his body fully outstretched.
Malhotra and Lapierre connect once again on Malhotra's seventh and final goal of the season, a sick wrister from the dot that beats Jonathan Quick off the far post. I can't for the life of me understand why Mitchell and Voynov give Malhotra and Lapierre so much room entering the zone. They back off the two like they're goal-scorers, and then it's sort of a self-fulfilling prophecy, isn't it?Tags: Every Goal, every goal 2011-12, Manny Malhotra


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text: Prev | Next Purchase this photo Billy Summers/The Putnam Herald Lady Generals forward Jordan Pauley keeps the ball away from the reach of a Morgantown defender as Winfield hosts the Lady Mohicans on Saturday, Sept. 15, 2012. Gallery: Putnam in Pictures, Friday, Sept. 21 Sep. 21, 2012 @ 12:28 PM 2012/The Herald-Dispatch Did you miss something in Putnam County this week? Chances are, one of our photographers was there. ()


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This weekly course covers the most common questions videographers encounter when shooting and editing with DSLR cameras, from choosing a frame size and frame rate to understanding moiré. Authors Rich Harrington and Robbie Carman will also help you understand the impacts of compression and the difference between cropped (or micro 4/3rds) and full-sized sensors in cameras, and much more. This continual FAQ guide is a handy way to find the answers to the questions that plague you the most.
Robbie Carman: Now, Rich, one of the most tried and true ways to record interviews is by using a Lav, or a Lavalier microphone on your subject. Rich Harrington: Yeah, this is a classic microphone. Originally, this microphone was actually worn around the neck. If you look at early newscasts, they'd have a rope necklace and the microphone would be hanging and you actually see that, but this is actually named after a type of jewelry. So a Lavalier was a pendant that was worn around the neck, often a teardrop shape, and this is really where it comes from. These days, you won't really see people wearing microphone necklaces.
The Lavalier microphone has been adapted and it can be attached several different ways to your subject. Robbie: Yeah, the nice thing about Lavs is that they're nice and small, like this guy right here, and I'm actually wearing one on my shirt, and if I tap it right here or move it around, you can hear it. And the beauty about Lavs is that they're pretty inconspicuous. So if you want to make--you're recording an interview or a scene where you want to make it seem that it's kind of natural, that you don't have a lot of gear on set, they're a good choice. Now, Lavs come in a couple of different setups. The one that you see right here is actually a wired Lav and you can see it runs down a microphone cable, down to a little barrel here, and the end of the barrel there is an XLR adapter.
Now, the other thing about this particular Lav is that it has a compartment here in the middle to put in batteries. Most Lavs are going to need to have power, because they're condenser type microphones, and you can power them either if you have a battery. Or if you're using a mixer or an audio recorder that provides phantom power, you can also power it that way. Rich: Now, one of the things to think about with the Lavalier microphone is where that power is going to come from, either the battery that's inside, or the mixer. I don't recommend that you put both in at the same time. You don't want to overload that mic. Another thing though, too, is realize we're talking about this mic being inconspicuous, and some of you might be thinking that doesn't look that small.
Well, this particular mic you see here, we've already put on a windscreen to cut down on noise and wind blowing or plosives, pops with the mouth, that can come off. And it's a pretty small microphone inside of there. Let's just should slide that off, you see just a little tiny mic, and nothing says you have to use this. This is your sort of standard tie tack, works well on a lapel. We actually can use other types of clips. Like here I have a very small vampire clip, two little fanged teeth, and this is designed to be hooked on the inside of a shirt lapel or maybe on the inside of clothing.
People will sometimes tape this inside of a shirt with a band-aid on the inside of a T-shirt. This is a small inconspicuous mic, and the goal is to just make sure that it gets put close to the subject's mouth. Generally speaking, we say about that far away, and you see there for my mic, that's about the distance. You can go double that distance, but the farther it gets away from the subject, the hollower it's going to sound. Robbie: That's right, and you actually brought up one other really important point and that's sort of placement of the Lav itself, not just in distance, but actual placement on the person's body or clothes.
One of the big problems that you potentially get by using a Lav is clothing rub, on somebody's lapel or their jacket or something, their shirt and they move, you have to be very careful where you place that. Now, typically in an interview setup, I'll have the subject move around a little bit before we actually start rolling, so I can make sure that their natural body movement is not going to disturb the mic and get sort of that ruffling sound, because it's very difficult to sort of remove in postproduction, not impossible, but difficult. Rich: Now, you're not saying like jumping jacks or anything extreme, right? Just move your shoulders, talk with your hands a little bit, listen for that rub.
Another thing that's important about placement that you bring up, which is actually a good idea, see, we're both talking to each other as well as folks at home. I'm typically turning to this shoulder, so if I was wearing a sport coat and I was attaching this to the lapel, I wouldn't want to put it on my outside shoulder, I'd put it on the inside shoulder where I'm looking, since this is center. Even if I turn my head as I'm talking, there's a little variation in the levels, but it's picking up pretty well. But you need to think about where is that mic in relation to the subject's mouth. Getting it nice and center, good idea.
Robbie: Absolutely, now there is one more important thing when it comes to Lavs is that you're going to have sort of two choices in the Lav system that you use. Sort of the old dependable way of doing it is with a wired Lavalier system, which works great. However, new Lav systems can go wireless. Now, you might be thinking that wireless systems are just the way to go, less wires, less problems. You've got to be careful about this. Wireless Lav systems can be prone to interference. So if you have a lot of electronics on set, cell phones, iPads, whatever it may be, they can be interfered with, and that signal from the Lav can have noise in it and distortion and that kind of stuff.
So when you go on set, it's always a great idea if you're going to use Lav mics to have both options available to you, a wireless system, which might be your first choice, but as a backup having a wired system if that wireless version is not going to work out in the particular location that you're in. Rich: Yeah, tied to that location, you can have interference from things like cell phone towers, or radio broadcast towers, lots of wireless microphones. Another important thing is making sure you have plenty of batteries, because wireless mics will burn through them. Typically these are AA. There is one thing, though, that I want to point out, be very careful when buying a wireless mic system, particularly a used one.
If you're in the United States, the FCC, the governing body that oversees communications and electronics, actually switched standards a few years back, and there's a lot of microphones that are old that are not in compliance. So you might find systems available in the market, you need to go to the FCC website, look up wireless microphones and make sure that the frequencies they use are in compliance, otherwise--and believe it or not-- there are actually laws for these things. You could be breaking the law using that microphone system. So you want to make sure that it's a fully compliant system before you drop down some money.
Robbie: Absolutely, I mean, the last thing I'll mention about wireless Lavs is that you often get what you pay for. This is true about a lot of things in production, but it's particularly true if you decide to go with a wireless Lavalier system. Typically the higher end systems are going to give you more flexibility in your frequency choice, have additional features that will reduce the possibility of having interference and noise brought into the system. So just when you're going out there and looking at different Lav systems, be aware that the higher priced wireless systems often generally perform a little bit better than say the $99 special that you found online.
Rich: And to that end, when you're picking out a Lav system, I always recommend get the one that has the wireless Lav and the XLR adapter, this will give you the flexibility to patch into other systems and give you a wireless throw for things like concerts and events. When we come back, we're going to talk about the other type of microphone that's great for dialogue, and that is the Boom mic.
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All eyes on al-Qaeda master of explosives, AKA 'evil genius', who turned his own brother into a bomb
He is Al Qaeda's most valued bombmaker and the creator of explosives so dangerous only an 'evil genius' could have come up with them.
Such is the skill of chemistry student Ibrahim Al-Asiri, who was born into a respectable middle class Saudi family, that his devices can be sewn inside a human body.
And terrifyingly, because they contain no metal elements, they are virtually undetectable and can evade airport security.
The master explosives-maker first tried out his chilling tactics on his willing younger brother, Abdullah.
He implanted a suicide bomb inside the 23-year-old for an assassination attempt on a Saudi Arabian prince.
Although the device went off as planned, Abdullah succeeded in killing only himself and not his target. Al-Asiri's sinister creations have also been used on two high-profile terror attempts in the US, including the underwear bomb carried by Nigerian Umar Farouk Abdulmutallab in his attempt to blow up a plane carrying 300 passengers over America on Christmas Day 2009.
In 2010, his devices were found in printer cartridges on a cargo plane bound for the US. They were intercepted in the UK.
In May 2012, US officials said they believed Al-Asiri had built an improved version of the underwear bomb, which was given to a Saudi-recruited double agent to blow up on a US-bound flight.
After the discovery of the printer cartridge bomb, then US deputy national security adviser John Brennan said analysis of the devices showed they were made by the same person who was behind the underwear bomb.
He said: 'He's a very dangerous individual – clearly somebody who has a fair amount of training and experience. We need to find him and bring him to justice as soon as we can.'
US congressman and former homeland security committee chairman Peter King said Al-Asiri was an 'evil genius', adding: 'He is constantly expanding, he is constantly adjusting.' Intelligence sources believe Al-Asiri, who is known as Abu Saleh, has been passing on his lethal bomb-making expertise from his base in Yemen to Syria, with plans to attack transatlantic flights.


text: Comments by tigerguy24 - MLive.com tag:profile.mlive.com,2015:tigerguy24/9695910 2012-05-24T02:44:02Z Movable Type Enterprise 4.29-advance Comment on We're hypocrites when it comes to schools tag:blog.mlive.com,2015:/flintjournal/aheller//1580.20692138 2012-05-24T02:44:02Z 2012-05-24T02:44:02Z There may be hypocrites among the public...but there are lot of deceptive issues being thrown at the public. The school board announces 227 layoffs. Now they know full well that this an overblown number that will be cut back at tigerguy24 Comment on Michigan budget deal: Republicans plan some tax relief, teacher retirement system changes tag:www.mlive.com,2015:/politics/index.ssf//3203.20691820 2012-05-24T02:20:26Z 2012-05-24T02:20:26Z Someone needs to explain why taxing pensions is so wrong. Take this scenario:One person is working and making $40000 and a retired is sitting home and getting a $40000 pension. The both use the roads...they may even both have kids tigerguy24 Comment on Filling empty Linden storefronts is new City Manager Mark Tallman's first priority tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20658536 2012-05-21T23:06:42Z 2012-05-21T23:06:42Z Attracting tenants to privately owned storefronts is not the business of the city manager. If I had several empty houses in Linden would the city manager help me find tenants? It would be nice to see stores open but it tigerguy24 Comment on Click it or Ticket campaign to have 20 enforcement zones in Genesee County beginning today tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20658497 2012-05-21T23:03:20Z 2012-05-21T23:03:20Z Why is it important to enforce the seat belt law to save lives when it is not important to wear a helmet on a motorcycle to help save lives. Also, why don't motorcycles have seat belts if they are so tigerguy24 Comment on Readers hot over estimated price tag to replace water system at Genesee County Jail tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20644911 2012-05-20T22:39:49Z 2012-05-20T22:39:49Z Agree with ic23b...there will be hot water in the jail. Let's see the sealed competitive bids. Then rebid if not happy. And everyone who is griping about the cost...don't worry about whether it's a local union contractor. tigerguy24 Comment on Genesee County Register of Deeds Rose Bogardus said she didn't expect Clerk Michael Carr to withdraw, would have stayed in the race tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20634667 2012-05-19T17:39:15Z 2012-05-19T17:39:15Z Could it be that Rosie just got scammed by Mike and John? Seems pretty likely that Carr. and Gleason worked this out to get Bogardus out of the picture and to find a job for Gleason who couldn't run for tigerguy24 Comment on Two Flint companies boost employee fitness challenge to new level tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20599701 2012-05-17T00:18:25Z 2012-05-17T00:18:25Z C'mon...they're nodding...right?Minit to Win it is their physical fitness program? I've never seen that machine at the gym. tigerguy24 Comment on Woman arraigned for Mt. Morris Township stabbing death of her boyfriend tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20599649 2012-05-17T00:13:33Z 2012-05-17T00:13:33Z Poor lighting. tigerguy24 Comment on Woman arraigned for Mt. Morris Township stabbing death of her boyfriend tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20599634 2012-05-17T00:12:08Z 2012-05-17T00:12:08Z Now I know why the jailhouse photographer isn't working for Olan Mills. tigerguy24 Comment on Warren Buffett's purchase of 10 million GM shares is no surprise to Grand Blanc investment strategist tag:www.mlive.com,2015:/business/mid-michigan/index.ssf//5048.20599567 2012-05-17T00:06:08Z 2012-05-17T00:06:08Z Yep...I saw this one coming, too. I just didn't tell anyone. Wonder if the Journal would like my picture. tigerguy24 Comment on No surprise with late entry into Genesee County clerk race tag:blog.mlive.com,2015:/flintjournal/aheller//1580.20592915 2012-05-16T16:21:08Z 2012-05-16T16:21:08Z Time magazine's cover picture gives new meaning to "attached parenting". tigerguy24 Comment on No surprise with late entry into Genesee County clerk race tag:blog.mlive.com,2015:/flintjournal/aheller//1580.20591197 2012-05-16T14:45:20Z 2012-05-16T14:45:20Z Oh great...a few years ago we were struggling with the meaning of "it". Now we have to work on how to use 'the". Wonder how long it will take for some cheating politician to graduate to two syllable words..like "admit" tigerguy24 Comment on Lake Fenton Schools may become wireless by fall tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20591045 2012-05-16T14:36:20Z 2012-05-16T14:36:20Z A reasonable expenditure for a technology that is so useful...it seems to me. tigerguy24 Comment on Lake Fenton Schools may become wireless by fall tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20590587 2012-05-16T14:09:06Z 2012-05-16T14:09:06Z A reasonable expenditure for a technology that is so useful...it seems to me. tigerguy24 Comment on Teachers union leaders would no longer be freed from classroom time under bill before Michigan Senate committee tag:www.mlive.com,2015:/education/index.ssf//3940.20585509 2012-05-16T01:07:39Z 2012-05-16T01:07:39Z Get off the GOP's back...the are busy balancing the ledger after years of pro union legislators...the Union's influence will return someday and they will work to reverse the laws and statutes implemented during the Snyder term. The unions have failed tigerguy24 Comment on Fenton Township Trustee Tony Brown is first to file for Genesee County commissioner in District 6 tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20584059 2012-05-15T22:45:18Z 2012-05-15T22:45:18Z daleone....you are one suspicious dude or duress...you couldn't be farther from the truth...even Tony Brown would be shocked to learn my identity. BTW way. wh6 didn't you file...apparently no one filed to oppose Brown. tigerguy24 Comment on Over one hundred gather at Flint City Hall to protest Public Act 4 tag:photos.mlive.com,2015:/flint-journal/4466.20572295 2012-05-15T02:51:06Z 2012-05-15T02:51:06Z This whole demonstration is a big affair to show support for a minister who ought to be ashamed of himself for his public circus with a bullhorn. I think that Rev. Flynn is a good man who has worked tirelessly tigerguy24 Comment on Jesse Jackson, Reverend Reginald Flynn call on residents in Flint, statewide to rally against emergency manager act tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20558897 2012-05-14T03:45:39Z 2012-05-14T03:45:39Z Wow...I just read that Rev. Jesse doesn't think that appointing czar is good. Does he know how many czars that Pres. Obama has appointed? tigerguy24 Comment on Jesse Jackson, Reverend Reginald Flynn call on residents in Flint, statewide to rally against emergency manager act tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20558868 2012-05-14T03:39:47Z 2012-05-14T03:39:47Z I noticed that Mayor Walling and Sheriff Pickell were there at church. Is that where they go to church? Why were TV cameras at God's house? How come TV 12 wasn't at my church? We had a nice Mother's Day tigerguy24 Comment on Student arrested for assaulting teacher at Northwestern High School tag:www.mlive.com,2015:/news/flint/index.ssf//2552.20510196 2012-05-10T03:00:06Z 2012-05-10T03:00:06Z It'll be interesting how the prosecutor handles this case...as a criminal offends or turning it back to the school authorities for inhouse discipline. Prosecuting it would send a message that would help teachers. But then there is the sol's plea tigerguy24