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A system for detecting and correcting impulse noise present on an input data signal includes an impulse detector module receiving an input data signal and producing as output an correction enable signal indicating when an impulse correction is required. An impulse corrector module receives the input data signal and a correction enable signal and produces a corrected data signal, e.g., having the impulse canceled or blanked, as output. A reliability estimator and selector module receives the corrected data signal and the input data signal and selects as output the input signal which is more reliable. In one embodiment, the impulse detector includes first and second complementary impulse detectors, the outputs of which are analyzed by an enable and correction module to produce an impulse detection signal with improved accuracy. Preferably, the enable and correction module also indicates the most appropriate type of impulse correction in accordance with the detection signals from the complementary detectors. A novel system and method of detecting impulses based on Gram Schmidt techniques is also presented. In this method, one or more channels of a multi-channel data signal are kept free of data. When a whitening filter is applied, impulses on these quiet channels are emphasized. The Gram Schmidt technique exploits this fact to provide for improved impulse detection. The system can be modified to detect other types of low dimensionality noise.
1. A system for detecting and correcting non-stationary noise present on an input data signal comprising:
a detector module based on Gram Schmidt orthogonalization, receiving the input data signal and producing as output a correction enable signal indicating when a correction is required;
a corrector module receiving the input data signal and correction enable signal and producing a corrected data signal as output; and
a reliability estimator and selector module receiving the corrected data signal and the input data signal and producing an output signal which is the more reliable of the input data signal and the corrected data signal.
2. The system of
a first reliability estimator receiving the corrected data signal and producing as output a first reliability estimate indicating the reliability of the corrected data signal;
a second reliability estimator receiving the input data signal and producing as output a second reliability estimate indicating the reliability of the input data signal; and
a comparison module receiving the first and second reliability estimates and selecting one of the corrected data signal and the input data signal as output depending on relative values of the first and second reliability estimates.
3. The system of
4. The system of
5. The system of
the first and second reliability estimators each comprise a slicer; and
the first and second reliability estimates each comprise a reliability metric indicating a difference
between the input to the respective slicer and the output from the respective slicer, wherein the lower the reliability metric, the more reliable the signal.
6. The system of
7. The system of
a first impulse detector receiving the input data signal and producing a first impulse detection signal as output;
a second impulse detector receiving the input data signal and producing a second impulse detection signal as output; and
an impulse correction enable module receiving the first and second impulse detection signals and producing the correction enable signal in accordance with the first and second impulse detection signals.
8. The system of
9. The system of
10. The system of
the first impulse detector comprises a Gram Schmidt impulse detector; and
the second impulse detector comprises a moving window threshold detector.
11. The system of
12. The system of
blank an impulse if an impulse is detected by the moving window threshold detector but not the Gram Schmidt impulse detector;
cancel an impulse if an impulse is detected using the Gram Schmidt impulse detector but not the moving window threshold detector;
cancel an impulse if an impulse is detected by the Gram Schmidt impulse detector at a first time of arrival, and an impulse is detected by the moving window threshold detector at a second time of arrival within a predetermined interval from the first time of arrival; and
blank an impulse if an impulse is detected by the Gram Schmidt impulse detector at a first time of arrival, and an impulse is detected by the moving window threshold detector at a second time of arrival which is not within a predetermined interval from the first time of arrival.
13. The system of
14. The system of
15. The system of
16. The system of
17. The system of
18. The system of
19. The system of
20. A method for detecting and correcting non-stationary noise present on an input data signal comprising:
receiving the input data signal at a detector module based on Gram Schmidt orthogonalization which produces as output a correction enable signal indicating when a correction is required;
receiving the input data signal and correction enable signal at a corrector module which produces a corrected data signal as output; and
receiving the corrected data signal and the input data signal at a reliability estimator and selector module which produces an output signal which is the more reliable of the input data signal and the corrected data signal.
21. The method of
receiving the corrected data signal at a first reliability estimator which produces as output a first reliability estimate indicating the reliability of the corrected data signal;
receiving the input data signal at a second reliability estimator which produces as output a second reliability estimate indicating the reliability of the input data signal; and
comparing the first and second reliability estimates using a comparison module which selects one of the corrected data signal and the input data signal as output depending on relative values of the first and second reliability estimates.
22. The method of
23. The method of
24. The method of
utilizing a slicer in each of the first and second reliability estimators; and
the first and second reliability estimates each comprising a reliability metric indicating a difference between the input to the respective slicer and the output from the respective slicer, wherein the lower the reliability metric, the more reliable the signal.
25. The method of
26. The method of
receiving the input data signal at a first impulse detector which produces a first impulse detection signal as output;
receiving the input data signal at a second impulse detector which produces a second impulse detection signal as output; and
receiving the first and second impulse detection signals at an impulse correction enable module which produces the correction enable signal in accordance with the first and second impulse detection signals.
27. The method of
28. The method of
29. The method of
the first impulse detector comprises a Gram Schmidt impulse detector; and
the second impulse detector comprises a moving window threshold detector.
30. The method of
31. The method of
blank an impulse if an impulse is detected by the moving window threshold detector but not the Gram Schmidt impulse detector;
cancel an impulse if an impulse is detected using the Gram Schmidt impulse detector but not the moving window threshold detector;
cancel an impulse if an impulse is detected by the Gram Schmidt impulse detector at a first time of arrival, and an impulse is detected by the moving window threshold detector at a second time of arrival within a predetermined interval from the first time of arrival; and
blank an impulse if an impulse is detected by the Gram Schmidt impulse detector at a first time of arrival, and an impulse is detected by the moving window threshold detector at a second time of arrival which is not within a predetermined interval from the first time of arrival.
32. The method of
33. The method of
34. The method of
35. The method of
36. The method of
37. The method of
38. The method of
This invention is related generally to receiving apparatus for a data communication system. More particularly, this invention is directed to a method and system for detecting, timing, and correcting impulse noise on a data communication channel.
Communications systems are used to transfer data between remote transmitting and receiving locations over one or more physical channels. The integrity and reliability of such data transmissions can be compromised by several factors, such as transmission imperfections, receiving imperfections, and physical channel interference. Examples of interference which affect the quality and rate of data transmission include impulses (or bursts), and other short duration events, and long duration interference, such as ingresses. A relatively large effort has been directed to improving the transmitter and receiver robustness for long duration interference. However, compensating for impulse/burst noise has received little attention. Impulse or burst noise can be caused by many uncontrollable events, such as arcing and electrical transients coupled through a power system, lightning, etc. This type of noise typically occurs at unexpected times and lasts for a relatively short period of time (on the order of several microseconds). Because it is broad band in effect, impulse noise is of particular concern in multi-carrier transmission schemes since the impulse noise may affect many, or even all channels simultaneously.
For example, in a multi-tone modulation transmission scheme, a number of carriers positioned at different frequencies are used and data is transmitted simultaneously in parallel over the carriers. Each band carries a fraction of the total information being transmitted. The discrete bands or sub-channels are independently modulated, and each has a carrier frequency at the center frequency of the particular band. For example, multi-tone modulation schemes include DMT (Discrete Multitone modulation), used for DSL channel communication, and VCMT (Variable Constellation Multi Tone), suggested for use in HFC CATV applications.
In one DMT configuration, a 1.1 MHz channel is broken down into 256 sub-channels or bands, each of which is 4 KHz wide. Each sub-channel has its own carrier frequency. Each of the sub-channels is used to transmit a fixed number of information bits in a single symbol or signal period. The DMT system monitors the signal to noise ratio for each of the sub-channels and uses this information to determine how many bits per signal period (symbol) may be carried in each of the sub-channels. The number of bits per signal in a sub-channel is typically referred to as the loading of the sub-channel. The DMT system dynamically adjusts the loading of each of the sub-channels in accordance with the noise characteristics of the sub-channel. If a sub-channel is particularly noisy, it may not be used at all.
VCMT modulation is a transmission scheme specifically designed to effectively combat the high ingress and impulse/burst impairments present in cable TV channels, and also to maximize the data throughput capacity of such channels. Like DMT, data is transmitted over multiple sub-channels, typically 36. However, in VCMT, data is transmitted using a variable bit loading per tone, along with coding and interleaving. The VCMT system measures the noise present on each channel and independently modulates the tone data transmission scheme from QPSK (quadrature phase shift keying) to 256-QAM (quadrature amplitude modulation) accordingly. During operation, the signal-to-noise ratio across the channels are monitored for each tone and the headend receiver instructs the upstream transmitter in the cable modem to modify the QAM constellation for each tone to maintain a desired bit error rate. VCMT also uses spectral shaping to reduce the frequency sidelobes of the tones to thereby reduce the effect of narrowband interference to only the closest tones.
Multi-tone transmission schemes have relatively good noise immunity. However, there is a tradeoff when resistance to impulse noise is considered. Because data is transmitted on multiple channels, the symbol length can be relatively long while still providing a high overall data transmission rate. Both DMT and VCMT have relatively long symbol periods. Thus, each has fairly good immunity (compared to a single carrier signal) from weak time domain events, such as impulses and bursts, because the effect of a short time domain event will be averaged out over the relatively longer symbol period. However, strong impulses are very damaging to DMT transmission because the impulse may simultaneously corrupt all of the 256 symbols occupying the 256 DMT sub-channels. Similarly, strong impulses are also very damaging to VCMT transmissions because the impulse can corrupt the symbols occupying every VCMT sub-channel at the time the impulse hits. In addition, because VCMT uses spectral shaping, neighboring symbols may also be corrupted by the impulse.
Impulses can be corrected by either canceling or blanking. Impulse canceling is a process where the impulse waveform is estimated and then subtracted from the data signal at the appropriate time. Impulse blanking is a process in which the impulse is located in time and the data input is zeroed (or blanked) for the duration of the impulse. Canceling is superior to banking because it preserves the underlying data. However, it is considerably more complex to implement.
Various techniques for compensating for impulse noise are known. U.S. Pat. No. 5,410,264 to Lechleider, which is incorporated herein by reference, describes very basic techniques for impulse detection, timing, and cancellation. The techniques are based on match filtering with a known impulse shape. An impulse is detected by using a match filter and monitoring when the filter output energy crosses a defined threshold. The location of the impulse is estimated to be the single match filter output sample which has the maximum energy. However, the techniques disclosed in the '264 patent are incapable of handling impulses having more than one degree of freedom (e.g., spanned by a basis of more than one vector).
U.S. Pat. No. 5,479,440 to Esfahani, which is incorporated herein by reference, discloses an impulse cancellation technique which compensates for out-of-band impulse noise by filtering out frequency components suspected as impulses. However, the '440 patent does not adequately address in-band impulse noise. U.S. Pat. No. 5,703,904 to Langberg, which is incorporated herein by reference, discusses temporarily inhibiting (e.g., blanking) modem adaptation circuits when an impulse is detected. However, impulses are detected only by using a simple thresholding input signal. Further, no attempt is made to cancel the impulse. A somewhat more detailed impulse detection scheme, using an adaptive threshold, is disclosed in U.S. Pat. No. 5,119,321, which is incorporated herein by reference.
However, none of these prior art impulse detection and compensation schemes provides a robust and efficient impulse detection system which can adequately detect impulses which have two or more unknown (or varying) degrees of freedom. Further, none discloses an efficient scheme for handling strong impulses in a multi-channel transmission system.
Accordingly, it is an object of the present invention to provide a method for compensating for strong impulse interference in a multi-carrier system, such as DMT and VCMT.
It is a further object of the invention to provide an improved technique for detecting and timing impulses which have attributes that span a number of degrees of freedom.
Yet another object of the invention is to provide a system which will reliably detect an impulse, determine its attributes, and then take appropriate corrective action.
Yet a further object of the invention is to provide an impulse detection and correction system which is suitable for in band impulse noise as well as out-of-band impulses.
A further object of the invention is to detect and correct non-stationary noise, i.e., noise which has statistics which change over time.
This invention is directed to novel methods and apparatus for detecting and correcting impulse noise on a data communication channel. In one embodiment of the invention, a dual-detection scheme is used. The communication signal, which can be a single carrier signal or a multi-carrier signal, is input to two or more separate impulse detectors, each of which uses a different impulse detection scheme. Preferably, complementary detection schemes are used such that the weaknesses in the first detection scheme are countered by the strengths in the second detection scheme, and vice versa.
The outputs of the impulse detectors are provided to an impulse correction enable circuit which uses the impulse detection signals to determine when an impulse is present and produces an output indicating that corrective action should be taken. Preferably, more than one corrective action can be taken and the enable circuit further indicates what corrective action to take. The received signal is also provided to the impulse correction circuit, such as a canceling/blanking circuit. In accordance with the output of the enable circuit, the impulse correction circuit corrects for impulse noise by, e.g., subtracting an estimated impulse waveform from the data signal at the appropriate time or by blanking the data signal for the duration of the impulse. The output of the impulse correction circuit can be sent directly to subsequent components, such as a decoder. Preferably, and according to another aspect of the invention, the output of the pulse corrector is provided to a reliability estimator and selector. The original (uncorrected) data signal is also input to the selector. The selector compares the corrected and uncorrected input signals and determines which is more reliable. The most reliable signal is then selected and provided to subsequent components.
Various impulse detection schemes can be used. One preferred and novel impulse correction scheme is based on utilizing the high intertone impulse correlation generated when an impulse hits a multitone symbol. When a short impulse hits a multitone symbol that is longer than the impulse duration, the noise phasors inflicted on neighboring tones are very similar. This similarity can be quantified by computing the cross correlation among neighboring tones, which would thus be close in absolute value to 1 (the phase depends on the timing of the impulse within the symbol). The high cross correlation is utilized for estimating impulse timing and for estimating the impulse noise waveform.
In particular, the new impulse detection/correction scheme uses quiet tones (sub channels) among the multiple channels in the data link wherein a fraction (typically a few percent) of the sub channels are not used for data transmission. According to this aspect of the invention, the signals on the quiet tone channels are uncorrupted by any transmit signal and therefore can be used to accurately detect the presence of an impulse. Because of high cross correlation of impulse noise across all channels, an impulse detection in a quiet-tone can be used to indicate an impulse on other channels as well. Most preferably, impulses are detected and their timing estimated based on a Gram Schmidt orthogonalization process.
The new Gram Schmidt scheme provides superior impulse timing and shape estimation. However, it is less accurate when multiple impulses are present in a short time period. Accordingly, when used in a dual-detection scheme, a complementary detection scheme which more accurately detects multiple impulses should be used. Preferably, a detection scheme based on a signal energy moving average window is used.
In addition to detection of impulses, new methods of canceling impulses are also presented, including a linear least square scheme, and a decision feed back scheme.
The new technique for detecting and canceling strong impulses can be used in conjunction with multitone transmission schemes, such as DMT and VCMT, to solve their vulnerability to impulse noise. However, the new method is not limited to multitone modulations, but also is suitable for other types of communication schemes, such as CDMA and single carrier modulation, and even non-communication signals. Furthermore, by applying the present method but switching the model time and frequency axes, the invention can be used to acquire the frequency of fast rising or changing ingresses (narrow band interference) and cancel them accordingly. In addition, in some data transmission and reception schemes, received and amplified signals may be subjected to clipping. The effect of clipping on a signal is similar to that produced by impulse noise. The present invention may also be adapted to detect and cancel noise generated by clipping, thus permitting the use of less complex and expensive receiving circuits.
The foregoing and other features of the present invention will be more readily apparent from the following detailed description and drawings of illustrative embodiments of the invention in which:
Turning to
In the preferred embodiment, the outputs of two or more separate impulse detectors are used to determine the timing and possibly shape of an impulse. Thus, the results are generally more accurate than if a single impulse detector is used. Further, the use of multiple detectors permits the use of complementary detection schemes, wherein weaknesses inherent in a first detection scheme are countered by the strengths in a second detection scheme and vice versa. Preferred detection schemes are discussed in detail below.
Impulse correction can be by cancellation or blanking. Preferably, both methods are available. In such a situation, the output of impulse detector 8 indicates whether the impulse should be canceled or blanked. When two or more impulse detectors 12, 14 are used in impulse detector 8, the selection of which correction method to use is made with consideration as to the accuracy of the impulse detection schemes in use and how well the impulse waveform can be predicted in various circumstances. If the impulse correction enable circuit 16 determines that an accurate waveform can be generated, an indication to cancel the impulse is output. Otherwise, an indication to blank the impulse is output.
An impulse corrector module 18 is provided which receives the input signal 11, pre-processed by a match filter 68 if necessary, and the output from the impulse detector 8 (correction enable 16). In accordance with the signal output from the impulse detector, the impulse correction module 18 corrects for the detected impulse noise by, e.g., subtracting an estimated impulse waveform from the data signal at the appropriate time or by blanking (zeroing) the data signal for the duration of the impulse. The output of the impulse correction module 18 can be sent directly to subsequent components, such as a decoder. Preferably, however, the output is provided to a reliability estimator and selector 20, which also receives as input the original (uncorrected) data signal, pre-processed by a match filter 72 if necessary. Selector 20 evaluates the corrected and uncorrected data signals to determine which is more reliable. The most reliable signal is then selected and provided to subsequent components. As can be appreciated, the dual-output path can be implemented using a variety of impulse detectors. Preferably, however, a dual-path impulse detector, such as described below, is used.
Turning to
Also shown, although not technically part of the detector and corrector 10, is an analog and digital front end comprising an A/D converter 22 and a decimator 24. The received analog data signal is sampled by A/D converter 22 at a rate sufficient to prevent aliasing of the data signals. Because of the difficulty of implementing high roll off analog filters, the sampling rate is usually considerably higher than required by the Nyquist Rate. To reduce the sampling rate to a value closer to the Nyquist frequency, the sampled signal is decimated by decimator 24 to produce the input signal 11 which is subsequently processed by the impulse detector and corrector 10. The front end may also contain standard timing and frequency loops. These are well-understood components to those skilled in the art and will, thus, not be described in detail.
The Gram Schmidt impulse detection method produces data which is suitable for estimating the waveform of a detected impulse. The output of detector 12 is used by an impulse estimator 19 which estimates the impulse waveform. This information is used later for impulse cancellation, when appropriate.
To further improve the accuracy of one or both of the impulse detectors, timing information from analogous detectors operating in neighboring signal bands may be shared and merged. Because impulses are typically wide enough to cover many adjacent receiver bands, sharing and merging impulse detection information from multiple detectors operating on adjacent bands can further improve the accuracy of the detection. For example, as shown in FIG. 2, the output of neighboring band impulse detectors analogous to detector 12 is provided via TOA interface 12 to a module 13 which merges the impulse time of arrival (TOA) determined by detector 12 and its neighbors. The weight to be given to the neighboring band impulse detection information when merging this information is dependent on the degree to which impulses are expected to cross multiple bands. Various merging methods will be apparent to those of skill in the art. This feature is discussed further below.
In addressing the operation of the various impulse detectors and other aspects of the invention, it is useful to define various terms and parameters. The signal input to the system is comprised of the Xmit signal (transmitted from remote transmitter), stationary noise sources (e.g. white noise or narrow band noise), and impulses. From the point of view of the impulse detection and correction mechanism, the impulse is the signal of interest while the Xmit signal and stationary noise sources are the unwanted interfering signals. These unwanted signals are referred to herein as the background noise.
It will be assumed that impulses to be detected have an expected length of L. If the detector 10 is used when impulses of indeterminate length are expected, the methods for detecting impulses of a known length L discussed below may be repeated with each possible L. In addition, the following parameters will be used in the following discussion of impulse detection and correcting schemes, as well as in the mathematical appendices:
NTones—Number of tones (sub-channels, carriers) in the multi-carrier communications channel
MGS—Gram Schmidt matrix of size (L*L), time dependent for DMT (see derivation in appendix)
MLS—Least square impulse estimation matrix of size (L*L), time dependent for DMT
THGS—Gram Schmidt window energy threshold.
THMW—Moving window energy threshold.
THERA—Erasure threshold used by the reliability detector
TG—The size of group on which local maximization is performed as part of Multiple Detection Suppression
NN—The number of neighbors used when merging impulse detection TOA information from other bands
Δf—The carrier frequency difference between successive tones
f(n)—The impulse response of the whitener 30 (
GK—gain at center frequency of tone K when viewing f(n) in frequency domain
y(n)—Signal at output of whitener 30 (FIG. 3).
σ—The background noise power after being whitened by whitener 30.
α—The memory of the decision feed back impulse canceler
Turning to
The sub-channel(s) designated as quiet tones can be selected arbitrarily. However, there are performance differences between different quiet tone arrangements, as will be appreciated by one of skill in the art. One way to assess the merits of a certain arrangement of quiet tones is to plot the combined impulse response of the whitener 30 and whitener match filter 32, (i.e., f(n)*f*(−n)). In a preferred quiet tone arrangement, the combined impulse response at the middle of the impulse is maximized while the impulse response at other locations is minimized.
Coefficients of the whitener filter 30, as well as the coefficients of the detection matrix MGS generated for use in the impulse detection routine, and discussed below, are generated in accordance with dynamic measurements of the noise power spectrum of the input signal. The background noise is preferably continuously measured and the relevant matrices and filters updated accordingly. Because changes in background noise are relatively slow, the matrix update rate can be low. Background noise measurement can be done using conventional techniques, such as averaging of the per-tone-energy of slicer errors, where the slicer error is the difference between the slicer input and output.
Data signals are not transmitted on the quiet tone sub-channels. Thus, these sub-channels (in the absence of an impulse) contain only the stationary noise sources. The power spectrum for these channels will therefore be considerably lower than that on the sub-channels used to transmit data (i.e., those with the higher "background noise") and so, during the whitening process, the data carrying sub-channels will be attenuated far more than the quiet tone sub-channels. As a result, when an impulse is present, it will have a much larger effect on the power level in a whitened quiet tone when compared to the power level of the sub-channels which are carrying data tones. This effect is graphically illustrated in the input and output graphs adjacent the whitener filter 30 shown in FIG. 3.
The output of the whitener filter 30 is passed through a whitener match filter 32. This filter has a transfer function which is the complex conjugate of the whitener, i.e., f*(−n) and produces from input y(n) an output equal to y(n)*f*(−n). The whitener match filter 32 functions to collect the energy from an impulse into a short interval having duration similar to the impulse.
The whitener filter 30 and whitener match filter 32 are preferably implemented as frequency-domain multiplications, although time convolution can be used instead. For frequency-domain, a filter bank is used that analyzes the input to the whitener 30, and then applies a per-band gain for the whitener, then a per-band gain for the match filter 32, and finally, combines all bands into one wider signal, e.g., by using a filter bank. The per-band whitener gain and the per-band whitener match filter gain can be combined into one gain (i.e., multiplied) to reduce complexity. Efficient implementation of a filter using filter banks is well-known to those skilled in the art.
Following the whitener and whitener match filters 30, 32, the processed signal is fed to the Gram Schmidt Impulse TOA estimator 34, shown in detail in FIG. 3. First, the processed signal is fed to a FIFO 40 having a length L equal to the estimated length of the impulse. Each time a new sample enters FIFO 40, the oldest sample is discarded. The output of FIFO 40 is a parallel column vector of height L.
Next, the vector output of the FIFO 40 is left multiplied by a Gram Schmidt matrix MGS of size (L*L) in Gram Schmidt module 42. The output of Gram Schmidt multiplication 42 is a column vector of height L, where each component of the vector represents the projection of the impulse on one of the Gram Schmidt (orthogonal) basis vectors. In general, multiplication by matrix MGS transforms values that are the results of correlation with the match filter (i.e., f*(−n)) into projections on the Gram Schmidt basis vectors. The specific form of matrix MGS is dependent on the type of data transmission scheme at issue. Detailed derivations of the Gram Schmidt matrices for VCMT and DMT are presented in Appendixes A-C, below. Similar analyses can be used to derive the appropriate Gram Schmidt matrix for other data transmission schemes, as will be understood by those of skill in the art in view of the present disclosure. In addition, while the appendixes present a derivation of some implementations of various aspects of the present invention, the invention is not limited to an implementation which adopts the precise mathematical relationships discussed in the appendixes and various adjustments to the parameters and mathematical relationships may be made while still falling within the overall scope of the invention.
The column vector output of Gram Schmidt module 42 is processed by Energy Summation module 44. Summation module 44 sums up the square values of the coordinates of the input vector. This value represents the (estimated) net impulse energy after being filtered by the whitener filter for the impulse samples which are contained in FIFO 40. Thus, the value can be used to determine whether an impulse is present and, if so, when it occurred.
As an artifact of this impulse detection scheme, the impulse energy may be smeared across several time points. In particular, a genuine impulse will generate a high-energy sample at the output of energy summation 44 which has a temporal location corresponding to the TOA of the impulse. However, and in addition, the impulse will generate lower energy values at small distances from the actual (correct) TOA of the impulse. This leaked energy is usually significantly lower energy than the energy present at the impulse's TOA. To avoid erroneous multiple detections, a Multiple Detection Suppression module 36 is used.
In a preferred embodiment, Multiple Detection Suppression module 36 comprises three sub-modules as shown in FIG. 3. Group divider 46 divides the vector input into several non-overlapping groups of size TG and identifies the maximum energy point in each group. These group maximums are provided to a Local Maxima Detector 48. Energy values that are higher than a previous group and not lower than a subsequent group are passed to Threshold Local Maxima module 50. (Only immediate neighboring groups are considered. This is the usual Local Maxima Detection). Finally, local maximas that are higher than a predetermined energy threshold, THGS, are identified. The temporal position of those identified maximas corresponds to the TOA of an impulse. It should be noted that the final TOA is not the timing of the local maxima achieving group, but the timing of the maximum sample within that group.
Thus, multiple detection suppression module 36 acts to remove the false alarms and pass on only the true impulse detection using local maximization and assuming that the true detection energy is higher than the surrounding energy. The size TG determines the size of the area in which local maximization is performed. The Local Maxima Detector 48 assures that two impulse detections are at least TG apart. It can be appreciated that increasing TG reduces false alarms but also reduces the probability of genuine impulse detection. (In cases when two genuine impulses occur in an interval shorter than TG samples, one of the impulses would be discarded by this process.) Those of skill in the art will recognize that there are a variety of other techniques for multiple detection suppression, each having various tradeoffs between false alarm rates, probability of impulse detection, and complexity.
This impulse detection scheme can be modified in several ways. One variation is removing the Gram Schmidt multiplication (in module 42). This can easily be accomplished by setting MGS to the identity matrix. As a result, the energy summation will compute the energies in the output vector of FIFO 40 directly. This reduces performance but also reduces complexity since MGS does not need to be computed. An alternative option is available if a good prediction of the impulse power is available in advance. If so, this information can be incorporated into matrix MGS.
As discussed above, and with reference to
In the preferred embodiment, a local TOA estimation is output from detector 12 and which, when a Gram Schmidt detector is used, includes sample energy found by Local maximizer 48 after multiple detection suppression. This data is broadcast to neighboring bands via the TOA interface 12′. At the same time, neighboring band receivers also broadcast their multiple detection suppressed TOA's (including sample energy found by their respective local maximizers). The TOA interface 12′ receives the TOA's of neighboring bands and sends them to the TOA Merge module 13 which combines this data with the local TOA estimation.
In a preferred implementation, the TOA estimates are combined using a weighted average, where weight is related to the TOA sample energy. There are other possible TOA merge algorithms, with tradeoff being between estimation noise and complexity. For example, the merge may be based on a median computation on all the TOA's, where the sample weight is interpreted as a TOA repetition used for the median computation.
When TOA information from multiple bands is merged, it is possible to vary the distribution of quiet tones in ways not possible without this data sharing. In one embodiment, the quiet tones are distributed evenly among different bands, in which case there will be similar TOA estimations of similar reliabilities from all bands. In another embodiment, the quiet tones can be distributed unevenly. In an extreme case, one band may host all of the quiet tones, and all other bands may use its estimation directly.
Turning to
A variety of other ways of implementing a moving window impulse detector can also be used. The particular implementation used is largely dependent on the implementation technology (e.g. DSP, ASIC etc.). For example, a moving window of length L may be implemented using an accumulator. The accumulator is first set to the sum of energies (squares) of L consecutive samples, giving the initial moving window a value. Then, each time the moving window is advanced, one sample (in time), the energy of the oldest sample is subtracted from the accumulator and the energy of the new sample is added, thus the accumulator energy then corresponds to the new set of samples.
A disadvantage of the moving window detection scheme is significantly less accuracy in impulse timing estimation vs. the new Gram Schmidt process, discussed above. The moving window is capable of detecting nearby impulses and estimating their timing only if the impulses are significantly strong compared with the Xmit signal, since the Xmit signal is an interfering noise relative to impulse detection. The Gram Schmidt scheme, by primarily relying on the quiet tones where the Xmit signal does not interfere, achieves superior performance. The background noise, and not the Xmit signal strength, limits the Gram Schmidt performance. In most cases of interest, the background noise is much weaker than the Xmit signal.
However, the moving window impulse detector is good at detecting situations where multiple impulses occur close together while the Gram Schmidt timing detection is not accurate in detecting closely spaced impulses. If the value of TG is small, a high false alarm rate will result. If, on the other hand, TG has a large value, there will be a large number of missed impulse detections because only one impulse is assumed to occur within TG. Because the strengths and weaknesses of these two impulse detection schemes complement each other, they are well matched for implementation in the dual-detector scheme shown in FIG. 1.
As shown in
In contrast, impulse blanking refers to zeroing the match filter input at summer/blanker 6 for the duration of the impulse as determined, e.g., by the output of the moving window threshold detector. Blanking removes the impulse noise but introduces a new impairment because of the Xmit signal zeroing (for the duration of the impulse). Signal zeroing manifests itself by loss of Xmit energy and, more importantly, by inter-symbol interference (ISI) and inter-tone interference for multitone (ITI). This penalty makes blanking advantageous only for those impulses having an instantaneous power which is strong, when compared with Xmit signal carrier power, making recovery of the Xmit signal unlikely. Moreover, a moving window TOA estimation is effective only for strong impulses, making blanking useful with strong impulses only. In general, it is better to use cancellation if possible.
In the preferred embodiment, where the complementary Gram Schmidt and moving window impulse detection schemes are used, the correction enable module 16 is configured to determine whether to use Impulse Cancellation or Impulse Blanking based on the relative strengths and weaknesses of these methods. If an impulse is detected by Moving Window but not Gram Schmidt, then blanking is used. If an impulse is detected using Gram Schmidt but not Moving Window (as when the impulse is too weak for Moving Window detection), then cancellation is used. If an impulse is detected by Gram Schmidt at a first TOA, and an impulse is detected using Moving Window in the vicinity of that TOA, then, if the moving window detections coincide with the first TOA, cancellation is used. Otherwise, if the Moving Window detections do not coincide with the first TOA, blanking in the detected impulse interval is used. Logic circuits or programs to implement this decision process can be easily generated by those of skill in the art. If other types of impulse detection modules are used, the operation of the enable module 16 may need to be adjusted accordingly, as is well-known in the art. In addition, the enable module 16 can also be configured to combine impulse detection data from more than two different detection schemes and act accordingly based on the relative strengths and weaknesses of the implemented schemes.
Impulse blanking is performed according to the TOA of the impulse as detected by, e.g., the Moving Window detector. The number of samples blanked corresponds to the length L of the moving window on which the impulse was detected. More precisely, the L consecutive samples output from decimator 24 (
In a Least Square cancellation scheme, impulse LS Estimation 19 is configured to estimate impulse coefficients in the time domain using data gathered by examining the quiet tones. The estimated impulse waveform is then subtracted by the summer/blanker 66 from the received signal. The impulse LS estimation is performed on the L consecutive samples output of whitener match filter 32 that were grouped by FIFO 40 and then identified by Gram Schmidt module 42. The estimation is performed by multiplying the L long sample vector from FIFO 103 with matrix MLS (which is an L*L matrix). For reference, one derivation of this impulse Least Square estimation is provided in Appendix B. Other methods known to those of skill in the art can also be used.
Decision Feed Back (DFB) impulse cancellation is an iterative process that uses a slicer output for Tones 1 . . . K−1 to predict impulse inflicted noise on a Tone K. The technique is somewhat similar to using Decision Feedback for ingress (narrow band interference) cancellation in single carrier systems (but swapping time and frequency domains) because once the impulse timing is available from the Gram Schmidt process, the problems of multitone impulse cancellation and single carrier ingress cancellation become similar. Despite its relative complexity, the advantages of DFB over least square cancellation are numerous.
Far fewer quiet tones are needed for DFB impulse cancellation versus LS cancellation. In Least Square Cancellation, the accuracy of the estimation degrades as the quiet tones frequency separation is increased since the cross-correlation of impulse inflicted noise between tones decays as tones are separated in frequency. Thus, the wider the Xmit signal bandwidth as compared with the reciprocal of impulse duration, the more quiet tones are needed. In contrast, a DFB impulse canceler refines the impulse estimation, going from Tone K to Tone K+1, and therefore has no such limitation. In fact, if the background noise is ignored, even a single quiet tone for DFB cancellation can be suitable for accurate results. A further advantage is that there is lower leftover impulse estimation noise after cancellation. The impulse estimate is refined from one tone to the next. Thus, the final estimate is based on many more sample tones than are examined in Least Square cancellation.
When DFB impulse cancellation is implemented, the impulse TOA stimation, e.g., as output from the merge module 13 is provided directly to DFB module 70 (FIG. 2). In one embodiment, the summer/canceler 66 does not need to subtract an impulse estimation (such as from LS estimation) or blank. Rather, it just passes the signal on to match filter 68. The output of match filter 68 is fed to the DFB module 70 which does the actual impulse cancellation. Other arrangements are also possible.
Adder 73 subtracts a current impulse prediction (which is output of rotator 88) from the complex value of the input 69, thus removing its impulse noise component. The cleaned complex value output of the adder 73 is then provided to slicer 74 which finds the nearest valid constellation point (i.e., slices). The output 76 of slicer 74 is then fed to a reliability estimator 94 (
Assuming that the slicer 74 had made no error, the true Xmit signal is provided to adder 78 which subtracts the true Xmit signal from the complex value input at 69 (and transferred to adder 78 input along signal 80), where the input at 69 is composed of Xmit signal plus impulse noise plus background noise. This leaves only the impulse noise plus background noise at the output of adder 78. This background noise corrupted impulse estimation is input to Predictor 82.
The Predictor 82 multiplies its input by (1−α) at 84. The adder 86 sums the previous predictor output from delay buffer 90 multiplied by α at 92 with the multiplied output at 84. The coefficient α is the memory of the predictor, e.g. α=1 means ignore current sample (use only memory), while α=0 means ignore the past samples (no memory). When the rotator 88 is included, the result is essentially a single pole passband filter. The properties of rotator 88 determine the center frequency of the passband filter. The rotator frequency ω (in radians) corresponds to the impulse timing τ from 50 multiplied by frequency difference Δf between successive tones, i.e., ω=2πΔfτ.
The impulse estimation needs to be rotated from Tone K to Tone K+1 because the tones have different carriers. Since the tones have different carriers, the same is true for their match filters in match filter 68, and the match filters directly rotate the impulse (a part of the filtering operation). Also note that for the quiet tone itself, the output of the slicer 74 is set to zero since nothing was transmitted on that tone.
In the event that there is only one quiet tone, but it is the tone at the highest frequency, the same process can be used, but starting from the highest frequency tone and going down to the lowest frequency tone. In this case, the rotator frequency ω=−2πΔfτ. In case there is a quiet tone that is not located in one of the extreme tones, but is somewhere in the middle, the DFB cancellation can be divided into two parts. First, the DFB can propagate from Quiet tone up and handle all higher frequency tones, and then can propagate down from Quiet tone to all lower tones. If there is more than one quiet tone, each tone can be used to cleanup its neighboring tones.
There are many ways known to those of skill in the art to construct the predictor 82 of DFB canceler 70, trading off complexity and accuracy. For the sake of simplicity, a rather simple first order predictor is preferred. Alternatively, for example, an N th order FIR predictor may be calculated directly from impulse noise cross-correlation among different tones. If the impulse is modeled as the gating on of a white gaussian noise source for the duration of the impulse, the random signal consisting of impulse samples on different tones is a stationary process having a sink shaped cross-correlation (among tones). The use of stationary random signal cross-correlation to build predictors is known to those of skill in the art. Also, using the equality (1−α)X+αY=X+α(Y−X), the one pole predictor 82 may be constructed using one multiplier and two adders instead of two multipliers and one adder. This transformation may reduce complexity for some implementations.
While the system and method of the preferred embodiment selects whether to blank or cancel a detected impulse, alternately the system can be simplified so that impulses are always blanked or always canceled. It is also possible to combine blanking with canceling using decision feedback (DFB canceling). For very strong impulses, some benefit can be achieved by first blanking the signal and then performing DFB canceling. When the impulse is blanked, so is the Xmit signal. This introduces an interference similar to an impulse having instantaneous power identical to Xmit signal power. If the impulse power is significantly higher than the Xmit signal, then blanking it would reduce the burden on the Decision Feedback impulse canceler. Because Decision Feed Back canceling uses a prediction based on earlier tones to clean the current tone, it is limited by the impulse process innovation from earlier tones to the current tone. If the innovation is too large, slicer errors will occur. Blanking, by reducing this innovation for large impulses, extends the impulse canceler operating range.
Referring back to
In this architecture, the corrected and the uncorrected signal paths are input to reliability estimator and selector 20. Selector 20 selects the best signal among these two. As will be appreciated by one of skill in the art, by using the double path architecture, even when a false alarm or timing error is present on the "corrected" path, the output to the decoder will be from the uncorrected data path and therefore there is no harm due to the false alarm. The strength of the two path architecture is based on the accuracy of the Reliability Estimators 94, 96 (
The reliability estimators 94, 96 operate by slicing the respective input signal and comparing the input of the slicer to its output. The closer the input signal is to the interpreted output, the more likely the input signal is to be reliable. More specifically, each one of the NTones input tones is sliced, thus producing a vector of NTones Decisions. For tones where the Xmit signal is known, i.e., quiet tones (where the Xmit Signal is 0) and preamble tones (where the Xmit signal taken from a known preamble sequence), the known value is used in the slicer's decision vector. Then, the per tone Decision is subtracted from the per tone Slicer input to produce a difference vector. (If the various tones do not have the same margin vs. background noise, it is preferred to scale them according to their individual margins.) Then, the sum of squares of the difference vector is computed to produce the reliability metric. The reliability metric has units of energy, wherein the higher the metric the less reliable the data.
Path Selection module 98 uses the generated Reliability Metric for two purposes. First the reliability metrics for the corrected and uncorrected data are compared and the input having the lower metric (i.e., the more reliable) is selected. Then, preferably, the reliability of the selected path is compared to a threshold value, THERA. If the reliability metric exceeds THERA, then even the most reliable path is deemed too unreliable to use and the entire column is erased so that the decoder gets erasures instead of channel symbols for the column.
While dual architectures have been described, both for impulse detection (Gram Schmidt and Moving window detectors), and for impulse correction (corrected and uncorrected path). It is also possible to use only a single impulse detector and/or a single path architecture to reduce complexity (at the price of a possible reduction in performance).
In the impulse detection and correction techniques discussed above, it was assumed that the impulse/burst duration L is given. In cases where this duration is not known, the processes described herein may be repeated with each possible L. Because the computations for different impulse durations are highly overlapping, a great deal of complexity may be saved by combining certain elements and steps. For example, the whitener and whitener match filter need not be duplicated because the same processing is performed for all durations. The suppression and merge with other bands can also be combined for all durations.
It can also be appreciated that there may be cases were the impulses are weak enough such that it is possible to modulate on some tones with a reduced bit loading even without canceler/blanking (i.e., using a loading lower/worse than that obtained after impulse canceling). In this case we may modulate on these tones using low loading. These tones can be considered blank tones, as opposed to quiet tones, since they will be used by blanking/canceling. The rest of the tones (none of which are blank tones) will use the loading obtained after applying the impulse canceler/blanker. These tones can be considered pure data tones. In this embodiment, the reception process will first demodulate the blanker tones, slice them, and then subtract the slicer output from these tones. Assuming the slicing was successful, the subtraction turns the blanker tones into quiet tones that may be used with the impulse canceler/blanker. After applying impulse cancellation or blanking, the pure data tones are demodulated. The benefit to this embodiment is that it achieves the maximal loading possible for the pure data tones (i.e., the loading obtained after applying the impulse canceler/blanker) while not entirely sacrificing bandwidth to quiet tones.
Those of skill in the art will also recognize that the present invention is not tied to the particular communication scheme described, but instead may be used in addition to point-to-point communication schemes, with multipoint-to-point, point-to-multipoint, and multipoint-to-multipoint schemes. In addition to multitone modulation, the invention can also be used with single carrier, CDMA and other modulation schemes. In non-multitone schemes, the transmitter should be configured to notch a few bands for use by the canceler/blanker as the quiet tones. Standard mechanisms can be used in the transmitter/receiver to correct for these notches.
This invention can be used in non-communication cases as well. For example, any signal that is corrupted with impulses and has one or more quiet sub bands may be cleaned using the above techniques by considering the quiet sub bands as quiet tones.
Yet another set of applications for this invention is to cancel low dimension noise contained in at most a few dimensions (i.e., noise exists in a low dimension linear subspace) from a high dimension signal where a few signal dimensions may be sacrificed to locate noise. A low dimensionality noise is a random signal which is a linear combination of a small number N of deterministic waveforms or basis functions. The waveforms are generally fixed and the particular coefficients for the linear combination are randomly distributed scalar variables. For this type of noise, most of the signal energy is contained in this low dimensional space. In other words, a large portion of the noise energy is contained within a small number of basis functions. For example in the impulse case, most signal energy is contained in a few successive (in discrete time) delta functions. In the ingress (narrow band noise) most signal energy is contained in a few neighboring frequencies. In contrast, white noise is not a low dimensionality noise because it has the same dimension as the useful signal. Given M samples of a target signal which is contaminated by white noise, the dimension N of the white noise component is also M. Further, the white noise power is evenly split among all of its N=M dimensions and, therefore, the present invention is not well suited for detecting and canceling this type of high-dimensionality noise.
Low dimensionality noise can be detected and canceled by projecting the noise on an orthogonal basis in a manner similar to the treatment of an impulse, discussed above. An example is a single carrier modulation corrupted by fast popping narrow ingresses wherein the frequency of the ingress is not known in advance and this frequency may change from time to time. In such a case, a quiet symbol is transmitted periodically (with the period getting longer as the ingress becomes narrower). The quiet symbol acts as a quiet tone for use in the detection/cancellation process. The ingress is highly correlated between successive symbols similar to impulse correlation between successive tones for an impulse canceler. By using the above techniques but swapping the frequency and time axes, the ingress frequency and an estimate of its waveform can be determined. It will be appreciated that the ingress frequency in this embodiment is the same as the impulse timing for the impulse canceler.
The dimension N of the matrices used in the noise detection and cancellation scheme of the invention is determined by the dimensionality N of the noise signal. Thus, the computational complexity of this method increases directly with the noise dimension. Furthermore, when the noise is detected through the use of quiet samples, such as the quiet tones used for impulse detection, the number of quiet samples used is preferably at least N. Thus, the larger the dimensionality of the noise, the more of the available bandwidth which must be reserved to carry quiet samples instead of a data signal. In general, noise having a dimensionality of no more than about three to five is well suited for detection and cancellation in accordance with the present invention, although use with higher dimensionality noise signals may be suitable in certain circumstances, such as when it is acceptable to cancel only a portion of a detected noise signal.
While the invention has been particularly shown and described with reference to preferred embodiments thereof, it will be understood by those skilled in the art that various other changes in form and details may be made therein without departing from the spirit and scope of the invention. For example, the present invention can be implemented using time-domain techniques or frequency-domain techniques.
This section presents the derivation of the impulse timing estimation for VCMT.
We model the input to impulse blanker/canceler (input to Noise whitener filter 30) as a combination of impulse noise and background noise. The impulse noise is modeled as the gating on and off (for the impulse duration) of a white noise source. A simplified discrete version of this model is
Noise whitener filter 30 (
To decide for a specific timing (t), whether that time was hit by an impulse (H1) or not (H0), we may use the log likelihood ratio below. According to Neyman-Pearson, to minimize False Alarm rate for a given Detection Rate, the LLR should be compared to a threshold THGS. In general H1 should be declared for LLR's above the threshold THGS and H0 for LLR's below threshold THGS (The higher the THGS threshold the lower the False Alarm rate). Note that the LLR is maximized with respect to h, which is the impulse waveform (time domain), thus performing maximum likelihood for impulse coefficients.
With, y, Signal input to whitener match filter
However we cannot declare H1 for all threshold exceeding LLRDETECT'S. Typically since around the true timing of the impulse there would be a neighborhood of high LLRDETECT's, we would like to suppress the additional false detections. One intuitive way to suppress false detections is to look for local neighborhood maximas (i.e., mountain peaks). We will now give a detailed explanation showing this is at least approximately correct.
To choose among the two candidate times (t1 & t2) the more likely candidate we can use the LLRTIME
With, y, Signal input to whitener match filter
Moreover LLRTIME — SELECT may be used to find the genuine impulse among a neighborhood of high LLRDETECT. This may be accomplished by computing the LLRTIME — SELECT for each pair of times, and selecting the time topt having positive LLRTIME — SELECT vs. all neighbors. Note we only have to suppress close neighbors, since as we depart in time from the impulse, the LLRDETECT drops and will not pass the detection threshold THGS.
Assuming the support (s) of y on which the LLR computation is performed, is big enough vs. neighborhood of false alarms (i.e., t1-t2), we have
This (approximate) equality shows a time t having LLRDETECT higher than its neighbors would be preferred by LLRTIME — SELECT and selected as topt. Thus, instead of directly computing LLRTIME
The background noise is whitened by Noise Whitener 30, which outputs a σ power white Gaussian noise. However, the impulse is also affected by noise whitener 30. We have modeled an impulse of length L starting at time instant t,
It is known from linear algebra that the projection of {yn} on a subspace is the best "approximation" existing in the subspace to {yn}. Thus, assuming ak opt are the coefficients of hopt, we would like to compute the following score for time t (Impulse time would be selected as the time having highest score)
Then applying Parsaval's theorem, the norm ∥hopt∥2 is equal to the sum of squares of projections of hopt on any orthonormal basis (which hopt is a member of its span), since FA columns constitute such a basis we have:
However (F′y) are L consecutive samples of the whitener match filter output 32 (FIG. 3). So we only need to additionally apply A′ and than square and sum up. The grouping into L sample size groups is performed by FIFO 40, the multiplication by A′ is performed by Gram Schmidt module 42 and energy summation is performed by energy summation module 44. Local neighborhood maxima is found by Group Divider 46 and Local Maxima detector 48. And finally comparison to threshold THGS is performed by Threshold Local Maxima module 50. Note the fact A is triangular reduces matrix application (multiplication) complexity further.
The description above does not refer directly to matrix A, instead it refers to matrix MGS=A′, which is applied by Gram Schmidt module 42 in FIG. 3. The following are the steps for computing MGS. Although the matrix MGS is applied (matrix multiplication) for each t, it need not be recomputed (Cholesky factorization) for each t. Matrix MGS depends only on GK and L that change when channel characteristics change (background noise or Impulse duration) and thus change slowly. Thus, the matrix MGS may be computed periodically by a low rate process.
This periodic Gram Schmidt matrix computation task is comprised of the following steps: The system assesses its input noise spectrum, including both stationary noise sources and the Xmit signal itself. Using the measured noise spectrum, it adapts the coefficients GK so that the whitener filter 30, having impulse response f(n), will whiten the input noise spectrum. Then using f(n) we build the matrix F=[V0 V1 . . . VL−1] with VK defined above (definition of basis B). Then using, for example, Cholesky factorization, we find MGS such that MGSF′FMGS′=I (since MGSF′FMGS′=(FMGS′)′(FMGS′)=I). Note that the whitener filter f(n) and the whitener match filter f*(−n) and matrixes MGS and MLS should be updated at the same time.
In this section we will derive impulse timing estimation for DMT. We are using the same impulse and background noise modeling as for VCMT.
Noise whitener 30 (
The blocks after the whitener need to detect impulse existence using whitener output Y(K). As before, the log likelihood ratio LLRDETECT is used for detecting impulses. The LLR is maximized with respect to H(K), which is the impulse waveform (in the frequency domain), thus performing maximum likelihood estimation for impulse coefficients. The support s parameter is not needed, since for DMT the LLR is based exactly on one DMT symbol length.
With, Y(K) Signal input to whitener match filter in frequency domain
The background noise is whitened by Noise Whitener 30, which outputs σ power white Gaussian noise. However, the impulse is also affected by noise whitener 30. We have modeled the impulse as
K, being the tone number, 0<=K<N
GK, being tone K frequency noise equalizer gain
t, the sample index, within a DMT symbol (0<=t<NFFT), that the impulse started
L, being the modeled impulse length
an, being the impulse coefficients prior to DFT
As with the VCMT case, Hopt(K) (i.e., the H(K) that maximizes the LLR) needs to get as close to Y(K) as possible. Assuming an are free numbers we get that Hopt is the projection of {Y(K)} on the subspace spanned by basis Bt below. As it is known from linear algebra that the projection of {Y(K)} on a subspace is the best "approximation" existing in the subspace to {Y(K)}, this yields:
With NFFT, size of FFT, Also equal to NTones (Number of DMT tones)
As with the VCMT case, applying Parsaval's theorem we get:
The multiplication (F′Y) may be implemented efficiently using IFFT. Computation for all ranges t . . . t+L−1 (0<=t<NFFT) within a DMT symbol may be performed all at once. First we need to compute the vector W such that W(K)=Y(K)GK (note no complex conjugate is needed for GK since it is real) and then compute U=NFFT*IFFT(W). As a result U(t . . . t+L−1) corresponds to ((Ft)′Y).
To summarize the processing performed for each Hypothesis test at time t: the whitener 30 (
The previous description does not refer directly to matrix At, instead it refers to matrix MGS−t=At′, which is applied by Gram Schmidt module 42 in FIG. 3. We will now point out the steps for computing MGS. As in the VCMT case, the matrices At may be computed periodically by a low rate process.
This periodic Gram Schmidt matrix computation task is comprised of the following steps: The system assesses its input noise spectrum, including both stationary noise sources and the Xmit signal itself. Using the measured noise spectrum, it adapts the coefficients GK so that the whitener filter 30, having impulse response f(n), will whiten the input noise spectrum. Then using G1, G2, . . . GNFFT−1 we build the matrixes F1, F2, . . . FNFFT−1, with Ft=[Vt Vt+1 . . . Vt+L−1] and VK defined above (definition of basis Bt). Subsequently, we need to find for each t a matrix MGS
The impulse waveform least square estimation is used for the linear canceling (as opposed to decision feed back canceling). It uses primarily the quiet tones in order to determine the impulse coefficients. It is similar to an over determined solution of set of equations (Generalized Least Square solution). The derivation is straightforward and may be applied to VCMT and DMT as well. Here we explain the VCMT case.
Given the output of whitener 30 (
The above description refers to impulse estimation matrix MLS which should be computed as follows: The system assesses its input noise spectrum, including both stationary noise sources and the Xmit signal itself. Using the measured noise spectrum, it adapts the coefficients GK so that the whitener filter 30, having impulse response f(n), will whiten the input noise spectrum. Then, using f(n) we construct matrix F=[V0 V1 . . . VL−1] with VK as defined for basis B in Appendix A, i.e., the VCMT case. Finally we use F to compute MLS=(F′F)−1.
In this section we will derive impulse timing estimation for VCMT assuming we have an apriori knowledge of impulse power.
We model the input to impulse blanker/canceler (input to Noise whitener filter 30) as a combination of impulse noise and background noise. The impulse noise is modeled as the gating on and off (for the impulse duration) of a white Gaussian noise source. A simplified discrete version of this model is
Noise whitener 30 (
With, y, Signal input to whitener match filter
However, we cannot declare H1 for all thresholds exceeding LLRDETECT's. Typically, since around the true timing of the impulse there would be a neighborhood of high LLRDETECT'S, we would like to suppress the additional false detections. As with previous cases, we can suppress false alarms by looking for local neighborhood maximas (i.e., mountain peaks) of LLRDETECT'S.
To re-formulate the maximization we first have to define vectors {VK}K=1 . . . L. Vector VK is a column vector composed of two parts. The upper part has dimension N and the lower part has dimension L. The upper part is constructed by shifting f(n) down K locations and padding with zeroes. The lower part is constructed by putting σ/σI in location K and zero in all other L−1 locations. The following is an illustration of VK.
The re-formulated maximization is identical to the original one. The difference is that the ak related components are generated by the vector extensions. Using this vector formulation it is obvious we need to minimize the second addend. The second addend is simply the error of approximating y using VK'S. Moreover it is known from linear algebra that the projection of y on a subspace spanned by VK is the best "approximation" existing in the subspace to y. Thus, to find the maxima we should project the extended y on the subspace spanned by VK. This is identical to cases of impulse detection without apriori knowledge (appendix A) but in the extended space.
Continuing similarly to previous derivations we obtain Score(t)
L, The modeled impulse duration in samples
s, the support of f(n) (i.e., length of f(n) is 2*s+1)
L, The modeled impulse duration in samples
However (F′y) are L consecutive samples of the whitener match filter output 32 (FIG. 3). So we only need to additionally apply A′ and then square and sum up. Then we can continue as before (Appendix A). The only difference vs. appendix A is a different computation for matrix A, i.e., Cholesky factorization on V′V instead of F′F.
The description above does not refer directly to matrix A, instead it refers to matrix MGS=A′, which is applied by Gram Schmidt module 42 in FIG. 3. To summarize, the steps for computing MGS for this apriori impulse power case are as follows. As in the VCMT case, the matrix A may be computed periodically by a low rate process.
This periodic Gram Schmidt matrix computation task is comprised of the following steps: The system assesses its input noise spectrum, including both stationary noise sources and the Xmit signal itself. Using the measured noise spectrum, it adapts the coefficients GK so that the whitener filter 30, having impulse response f(n), will whiten the input noise spectrum. Then using f(n) we build the matrix F=[V0 V1 . . . VL−1] with VK defined above. Then using, for example, Cholesky factorization, we find MGS such that MGSF′FMGS′=I (since MGSF′FMGS′=(FMGS′)′(FMGS′)=I). Note that the whitener filter f(n) and the whitener match filter f*(−n) and matrixes MGS and MLS should be updated at the same time.
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A Hooters in Queens, N.Y., is being sued by a Korean-American who claims he and his girlfriend were identified as "CHINX" on their receipt. The public relations dance is in full swing by the holding company that owns that particular Hooters. Contrite-ish declarations of outrage and disgust were issued, and the waitress who wrote the […] [Read More]
Don't search for this person
McAfee's 2012 "Most Dangerous Celebrities" list has named the talented and beautiful Emma Watson as the No. 1 most dangerous online search for this year. McAfee reports there is a 12 percent chance, or one in eight, that you will land on an attack site when clicking on pages that spit out when searching for […] [Read More]
What is 'Humaneering' technology?
"Humaneering" technology sounds like something out of an awful British science fiction tale. But for those of you wanting to get the low down on the meaning of the the new techno-business term there is a professional development meeting of the Association for Operations Management at 7 p.m., tonight at Anne Marie's Catering, 12475 Starcrest […] [Read More]
Gain access to capital financing
The U.S. Small Business Administration is having a seminar from 11 a.m. to noon, today at the SBA's San Antonio District Office, 615 E. Houston St., Suite 298. Loan programs available to small businesses though various SBA programs will be covered. The seminar is free. Contact 210-403-5900. -Chris Quinn [Read More]
Catch the 'Lunch Connection'
The local chapter of the National Association of Women Business Owners will have its monthly Lunch Connection from 11:30 a.m. to noon, today at the The Egg & I, 830 NW Loop. Cost is free, but Lunch is at attendee's expense. Contact 210-408-1220Ö or firstname.lastname@example.comÖ. Tuesday Sept. 11 Seminar — U.S. Small Business Administration, 11 […] [Read More]
GoDaddy goes down and takes millions with it
From about 1 to 5:30 p.m. today, website host company GoDaddy.com went down to an alleged hacker attack. And as big daddy went dark it took millions of small business websites, which are hosted through GoDaddy.com, with it. The Associated Press reports that many of GoDaddy.com customers took to social media to grip about their […] [Read More]
UPDATED: Bank's foreclosure crew secures wrong house
Apparently banks sometimes foreclose just for the hell of it. California couple Alvin and Pat Tjosaas recently lost all of their possessions after contractors hired Wells Fargo attempted to foreclose on their home even though there was no note on it. CBS Los Angeles reports that the bank mistakenly sent a foreclosure crew to the wrong […] [Read More]
Going orange for hunger
This month the smokestacks at the Alamo Quarry Market will light up the night with orange as part of the "SA Goes Orange Campaign." The going orange campaign is in partnership with Whataburger and is in support of Hunger Action Month and the San Antonio Food Bank. The lights will remain orange for all of […] [Read More]
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April 25, 2014
Top Stories
Seder helps community persevereOn April 14 students and
faculty were able to participate
in Susquehanna's Passover
Seder. The Seder was organized
and hosted by students
and faculty involved with Hillel,
the campus Jewish life organization.
Rabbi Palley, director
of Jewish life, provided more
information about the Seder.
"Passover is the most celebrated
Jewish holiday in America,"
she said. "It is a ritual dinner
where we retell the story of
the Exodus from Egypt and we
involve our family and friends
in celebrating being free."
Palley said that normally the
Seder can run two and a half to
three hours. This year's Seder
started at around 7:30 p.m. and
ended at 10:15 p.m. During
that time Palley said that they
try and recreate what it's like to
celebrate the Seder in Jewish
homes around the world. She
said that at the start of the Seder
the people participating were
organized into "family tables,"
where each table consisted of
a person's family and small
group to talk to for the night.
Palley said that there are
many different rituals performed
at the Seder throughout
the night, some of which they
put their own spin to. One of
the rituals is the hand washing
at the beginning of the Seder.
"We go around the table and
we wash someone else's hands,
and as someone is washing our
hands we say something we're
looking forward to cleansing
ourselves of and leaving behind,"
Palley said.
She added that one of the
themes of the Seder is the idea
of living like free people. One
of the ways that this idea can be
exemplified is by having others
do things for you. Rituals like
the washing of the hands and
the pouring of the grape juice
during the Seder are two ways
it is practiced, she said.
Palley and the students involved
in Hillel helped organize
the Seder. Palley said that
there were two different parts
to the planning. Being a main
university event, she said, there
had to be a lot of logistical
planning, such as catering the
food, setting up the layout of
the tables and planning the actual
"We decided what to keep,
what to cut out, who says what,
and we had meetings to prepare
and practice," Palley said.
Another aspect of the planning
process, Palley said, was
the invitation of the community,
which was a large part of
the Hillel students' job. Palley
added that though this was a
Jewish ceremony, everyone
was welcome to attend.
Palley added that an event
that happened recently the day
before the Seder was a shooting
in Overland Park, Kan.,
aimed at Jewish people outside
two Jewish facilties, which included
a Jewish nursing home
next door.
"It really tainted everything
about Passover," Palley said.
She added that President L. Jay
Lemons, who comes to every
Seder, spoke to the students and
faculty about this event.
Overall, Palley said that she
thinks the Seder was wonderful.
Because of the smooth
planning, she said she could be
more in the moment during the
Palley said: "Every family
has different customs of what
the Seder looks like, so coming
to a new Seder, it always feels
a little weird. But for the most
part they like it. For non-Jewish
students, it's fun and not at all
what they expect, which is also
very interesting because I never
know what they expect."
First-year Pamela Harvey
said that she enjoyed the Seder.
She said: "The Passover
dinner was a great event that
brought the community of
Susquehanna together to experience
Passover. I think it was
really great showing the Jewish
tradition to the campus and
having so many come and support
the small group of Jewish
students on this campus. On
top of being educational, it was
also fun to meet new people."
NEWS HEADLINESCampus service shifts from quantity to quality Student panel offers open discussion on bigotry Seder helps community persevere Campus continues fifty year laundry relationship Student raises thousands for crucial blindness research Campus celebrates longtime bus driver Summer sessions offer course variety, intensity
Top Stories | News | Living & Arts | Forum | Sports


text:
Don't worry, we'll go there someday. – Abby (Busterthecat)
Missy Frederick says Jasper and Cash "stand at the door to greet us when we come home and watch us leave when we go to work." Aww! We hope their dreams of going out with Mom come true soon. Thanks to Missy for the photo and cheers to Abby on her winning caption!
Want one of your pictures featured in our caption contest or in our weekly feature Animal D'Oh!? Submit a photo to our #cutepic contest on Twitter or stock up your profile with the funniest pet pictures you've got – we'll be looking!
Want more funny captions? Check out our recent winners here.
Congrats, Abby! You Win This Week's Caption Contest


text:
Services & Initiatives
Increasingly, instructors find themselves moving back and forth between teaching in online environments and on-campus learning spaces. And, in the current technological environment, they face an abundance of software options and cloud-based services, making it difficult to identify the "best" solution to meet their needs and challenges or try out new ideas. The Center for Scholarly Technology helps faculty navigate these choices.
Our services range from consultation and skill development to enterprise-level applications and evaluation for USC faculty who want to use technology to advance their teaching, collaboration, and research efforts. We offer:
- Instructional Design and Technology Consultation
- Customized Training
- Blackboard Learning Management System
- Evaluation of Educational Technology Projects and Programs
- Statistical Software
Contact us at firstname.lastname@example.com to schedule an appointment or find out more about our services.


text:
Showtek & Bassjackers – Hey! (Music Video) : Heavy Electro House AnthemPosted in Bangin, Video by nick | Tags: Bassjackers, Dutch House, Electro, Electro House, Hardstyle, LIVE, Music Video, Showtek
Fresh after dropping us "Let's Get Weird" the Bassjackers team up with Hardstyle legend Showtek for a massive track. "Hey!" is a straight bass infused anthem that would techically get classified as Electro House, but both Bassjackers and Showtek's roots shine through strongly. This is the track for shutting down the biggest festival, or any set, or on your next playlist. Can't get over how intense this is, and the video shows exactly how it does destroy crowds live. No download yet, just a video for now. Turn this up, enjoy!
Showtek & Bassjackers – Hey!
The Mowgli's – San Francisco (Little Daylight Remix) : Chill Sunny Indie / Electronic RemixPosted in Chill by nick | Tags: Electronic, indie, Little daylight, Remix, The Mowgli's
Say hello to The Mowgli's, a new Southern California indie / folk group that in their words are Rock N' Roll with California soul. Well here is a smooth remix from Little Daylight of their single "San Francisco". The feel good sunny indie track gets a chilled out remix accenting it perfectly. Free download which we always love. Enjoy!
The Mowgli's – San Francisco (Little Daylight Remix) | Direct Download
Follow The Mowgli's through Twitter
Benny Benassi – Satisfaction (RL Grime Remix) (Preview) : Must Hear Trap RemixPosted in Bangin by nick | Tags: Anthem, Benny Benassi, Remix, RL Grime, Trap, Trap Music
Benny Benassi's classic rave anthem "Satisfaction" has become one of the most popular electronic songs of all time since getting released in 2002. Well now RL Grime has done a proper trap remix for the iconic track, and he destroyed it. He carries over the energy of the original, with a 2012 blast of freshness. It made me feel like I was hearing "Satisfaciton" for the first time. This might even appeal to those who aren't quite feeling trap quite yet. This is stream only for now, and will be getting an offiicial release on December 17th, turn it up, enjoy! Update: this is a preview, RL Grime is going to be uploading the full version a week before it drops. Listen on repeat until then. Enjoy!
Benny Benassi – Satisfaction (RL Grime Remix)
Viceroy – While We're In Love ft. Ghost Beach (Oliver Nelson Remix) : Must Hear Indie Disco Electro Remix [TSIS PREMIERE]Posted in Bangin, Premieres by nick | Tags: Dance, disco, Ghost Beach, indie, Indie Electro, Oliver Nelson, Remix, Viceroy
Viceroy's recent "While We're In Love" featuring the vocals from Ghost Beach was an incredible beach / indie anthem, and was just calling for a more energetic remix. Now here is the premiere on Swedish based Oliver Nelson's smooth indie electro / disco take on the song, and I dare to say may have actually made the song better. It captures the feel good spirit of the original with some extra bass, and and even fresher edge. Turn this up, and you can purchase through iTunes. Enjoy!
Viceroy – While We're In Love ft. Ghost Beach (Oliver Nelson Remix) | iTunes
Follow Oliver Nelson and Viceroy
Tayyib Ali – Like Dat (Music Video) : Must Hear Fresh Chill Hip-Hop [TSIS PREMIERE]Posted in Chill, Video by nick | Tags: Chill, Hip-Hop, Keystone State of Mind 2, Laid Back, Rap, Tayyib Ali
Here is the latest from one of This Song Is Sick's favorite rappers Tayyib Ali. It's the first song off his new mixtape Keystone State of Mind 2 called "Like Dat" with an incredibly fresh beat produced by 52 Kings. Tay crushing the chorus and vereses, showcasing his distinct sound, with a new more aged tone. The video captures the vibe of the song with shots of him rapping and friends skating. Don't miss his previously released TSIS sponsored Keystone State of Mind mixtape that dropped last year. Look out for more from Tayyib Ali. Enjoy!
Tayyib Ali – Like Dat (Music Video
Ultra Music Festival Europe : Ultra Breaks into Europe with 5 Year Residency in CroatiaPosted in Events by nick | Tags: Croatia, Ultra Europe, Ultra Music Festival, Ultra Music Festival Europe
The legendary North American electronic music festival Ultra Music Festival that has been taking place in Mimi for 15 years, in past alongside the Winter Music Conference. Now this massive festival, after hitting South America and Asia last year is finally embarking on their European takeover. They have chosen Croatia to be the first European location, and have commited to the 5 year residency, and will be the only place in Europe for the next 5 years that Ultra will be descending upon.
The festival will be "Taking place in the city of SPLIT (12th & 13th July) and the island of HVAR (14th July)"
We might just be packing our bags, as this looks like an international event not too miss. You know since it's Ultra they are going to bring top notch production, amazing talent, and lots of surprises. Early bird tickets for extra cheap go on sale December 5th for 40 Euros.
Action Bronson & Alchemist – Rare Chandeliers (Mixtape) : Fresh Laid Back Hip-Hop MixtapePosted in Chill, Mixtapes / Albums by nick | Tags: Action Bronson, Alchemist, Chill, Hip-Hop, Laid Back, Mellow, Mixtape, Shcoolboy Q
Here's a talented face we have featured enough of on TSIS, Action Bronson. Here is the latest mixtape from Queens based rapper, Rare Chandliers. This 13 track project features so many solid songs it could be an album. He captures a old school raw hip-hop vibe with a new school twist that I can't get enough of. The whole project was produced by the legendary hip-hop producer Alchemist and he delivers nothing but smooth, insanely dope productions. We tried to pick out a few of our favorites, but it was so hard. Download the whole project, write below what your favorite track is. Enjoy!
Follow Actions Bronson and Alchemist
Action Bronson & Alchemist – Rare Chandeliers (Mixtape) | Direct Download
Action Bronson - Bitch I Deserve You feat Evidence (Produced by Alchemist)
Action Bronson – The Symbol (Produced by Alchemist)
Action Bronson – Demolition Man feat Schoolboy Q (Produced by Alchemist)
Action Bronson - Sylvester Lundgren feat Meyhem Lauren & Ag Da Coroner (Produced by Alchemist)
Jay-Z – Public Service Announcement (gLAdiator Remix) : Massive Trap / Hip-Hop Remix [Free Download]Posted in Bangin by nick | Tags: gLAdiator, Jay-Z, Remix, Trap, Trap Music
Jay-Z's iconic "Public Service Announcement" just got a proper trap fix from LA based duo gLAdiator.. and they crushed it. The bass drops so hard right from the beginning, and never lets up. Jay-Z's legenadary vocals go so well with the bass infused trap freshness. This should be played loud, and on some massive speakers or good headphones. He was kind enough to toss us out the free download. Turn this up, enjoy!
Jay-Z – Public Service Announcement (gLAdiator Remix) | Direct Download
Follow glAdiator through Twitter
Grizmatik – Digital Liberation Is Mad Freedom #DLIMF : Must Hear Song from GRiZ + Gramatik [Free Download]Posted in Bangin by nick | Tags: Dubstep, Electro Soul, Free Download, Funk, Gramatik, Griz, Grizmatik, Groove
A few weeks back we premiered the video to "Digital Liberation Is Mad Freedom", the massive collaboration between Grizmatik, GRiZ and Gramatik's new side project that has been crushing festivals and secret after parties since the debut at the Thissongissick Secret Set at Electric Forest last summer. Today we get the full high quality download of the massive collaboration.. and it is epic. The track that packs bass thumping energy with groove like never heard before. The video, also featured below showed them crushing crowds all over, and now you can crush your speakers or headphones for your personal enjoyment. Turn this up, enjoy!
Grizmatik – Digital Liberation Is Mad Freedom | Direct Download
Follow Gramatik | Facebook
Follow GRiZ | Facebook
Follow Grizmatik | Facebook
Grizmatik – Digital Liberation Is Mad Freedom (Music Video)
Electro Beach 2013 Tickets Go On Sale : 30 Day Electronic Spring Break Festival in Mexico ft. Tiesto, Zedd, & More!Posted in Bangin, Events by nick | Tags: Electro Beach, Prime Social Group
The incredible Electro Beach presented by Prime Social Group is back again with another year of 30 days filled with some of the biggest and best DJ"s in the world. We are happy to announce that we will be teaming up with them to provide in depth before and after coverage, on top of some incredible contests, and down at the festival we will have some exclusive thing going on that we will be posting more details on later.
For the first phase of their lineup they have announced Tiesto, Zedd, Nicky Romero, Krewella. Tommy Trash, Sander Van Doorn, 3LAU, The Knocks, Pierce Fulton, Danny Avila, and Manfucated Superstars. This is only the first phase.. Look below at the official trailer.. This is the ultimate spring break for any electronic fan. You can not get more for your money. For every trip you get 6 nights filled with DJ's at epic clubs, and then day parties and after parties every single night as well, on top of not stop raging and relaxing in Mexico. You get to party with you favorite DJ's, and be apart of a historic event.
Tickets are now on sale!
Tickets go on sale for the insane event today at 4pm EST / 2pm MST. They will start at the cheapest early bird price and go up. Each week is sure to be selling out, and even with the huge list of other aritsts also getting announced. Do not miss out. Hope to see you all their!
Check out travel options here
Buy Party Packages including tickets to all the events to each week here, see the video from last year below!
week1 | • 3/3 – 3/9
week 2 | • 3/10 – 3/16
week 3 | • 3/17 – 3/23
week 4 | • 3/24 – 3/30
Electro Beach 2013 Official Promo Video
Seven Lions – Days To Come (Coyote Kisses Cover) : Must Hear Live Electronic CoverPosted in Bangin, Chill by nick | Tags: Cover, Coyote Kisses, Dubstep, Live Instrum, Remix, Seven Lions
Seven Lions recently announce a contest to remix his "Days to Come" song, and Coyote Kisses to a stab at it.. and created something incredible. As the description states "Decided to take a break from finishing up all our originals and try something we've never done before, incorporating more "live" instrumentation. The result is something more rock & roll/different. Enjoy :]" Listen and you will understand. They fuse live instrumentation with electronic elements like I never thought possible. The result is really something ground breaking, and I really hope to hear more songs in this fashion from Coyote Kisses. Besides incorporating live instruments the song maintains a great blend of the sweet melodies and just the right amount of smooth bass. You can vote for this song here. Enjoy!
Seven Lions – Days To Come (Coyote Kisses Cover) | Vote for this Song
Follow Coyote Kisses through Facebook
Viceroy – While We're In Love ft. Ghost Beach : Must Hear Chill Indie / Electronic / Beach SinglePosted in Chill by nick | Tags: Beach, Ghost Beach, indie, Summertime, Viceroy
There are some indie tracks that you instantly fall in love with, here is just that. "While We're In Love" by Viceroy featuring Ghost Beach. Viceroy is the chilled out beach loving producer from San Franciso who brought us the Jet Life remixes to "Going Back to Cali" and "This Plane". Well he takes his feel good Beach vibes and teams up with the duo Ghost Beach to create an instant indie beach classic. It is getting colder and colder by the day in most parts of the US, but this song will warm you up. You can support by purchasing through iTunes. Enjoy!
Viceroy – While We're In Love ft. Ghost Beach | iTunes
Follow Viceroy through Twitter
Follow Ghost Beach through Twitter
Waka Flocka Flame – Grove St. Party (BUSTED by heRobust) : Huge Trap / Rap / Glitch-Hop RemixPosted in Bangin by nick | Tags: glitch-hop, heRobust, Hip-Hop, Remix, Trap, Trap Music, Waka Flocka Flame
Waka Flocka Flame's "Grove St. Party" is easily one of the best real trap rap anthems to come out before the recent new trap movement. It was just waiting for a proper bass heavy reworking, and heRobust took the track and busted it into a glitched out trap BANGER. This track has some massive synths and some insane vocal sampling flipping the vocals into a brutal robotic vibe. It is gritty, grimey, and breathes new light to a classic, what more could you ask? Free download as always from heRobust. Turn this up, enjoy1
Waka Flocka Flame – Grove St. Party (BUSTED by heRobust) | Facebook to Download | Direct Download
Follow heRobust through Twitter
Zedd – Clarity (Jay Cosmic Remix) : Heavy Drumstep Remix [Free Download] [TSIS PREMIERE]Posted in Bangin, Premieres by nick | Tags: BANGER, Drumstep, Heavy, Jay Cosmic, Remix, Zedd
Zedd's recent Clarity album has become one of the biggest electronic albums of the the year, and has spurred countless remixes. Today we get a massive drumstep remix done by newcomer Jay Cosmic to the title track "Clarity". This remix packs a very heavy brutal edge, yet maintains the melodic feel of the original complete with the sweet vocals to tie everything together. Excited to premiere this beastly remix, complete with free download. Jay Cosmic is asking that you facebook like to download his track. Enjoy!
Zedd – Clarity (Jay Cosmic Remix) | Facebook to Download | Direct Download
Follow Jay Cosmic through Facebook
My story has changed quite a lot since moving to Boulder, Colorado and starting Thissongissick back in 2010. My name is Nick Guarino and this is Thissongissick.com. We've grown a lot since, but the original goal has always stayed the same: making it easier for you to discover sick new music that you've never heard before. In high school I would make mix cd's for my friends to show them all the new music I was discovering. Now, through TSIS, we work with musicians and record labels from all over the world to showcase a variety of the freshest electronic, hip-hop, indie, and alternative music to a global following that is comprised of millions of music lovers in over 110 countries - every single month. So, make yourself at home while enjoying countless amazing musicians from a variety of genres and let the sick sounds fill your ears! - Nick