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Choral and Instrumental Festival
02 May 2015
This Choral event at St Flannan's Cathedral will be a most memorable one with children's choirs performing during the afternoon. Adult choirs will feature in the early evening and a Gala Concert will take place at 8.30pm
Gospel Rising Music Festival
08 May 2015 - 10 May 2015
Energetic and inclusive event which calls on all music lovers who are interested in this growing genre of music in Ireland. There are gospel choirs popping up all around us, and this festival is the chance to get that inside look and feel on what happens when you are 'in the choir'. The festival consists of a series of workshops with big and small groups, these cover choir harmony singing in gospel styles, different solo singing styles and levels, choreography and big group singing. Th...
Burren Béilíní and all that Jazz
18 May 2015
15:28 - 16:28
Kilshanny House, Kilshanny, Co Clare
To start the Burren Slow Food Week Festival, Kilshanny House presents a relaxing evening of music with the Paul O'Driscol Jazz Trio accompanied by our local light bites from land and sea. We will be showcasing Oonagh's (The Wild Kitchen) winning Masterchef Burren Béilíní from last Autumn's Burren Food Fayre. This event is also part of the Burren Food Trail Mondays.
Feile Chnoc na Gaoithe
26 June 2015 - 28 June 2015
A weekend of Traditional Irish music, song and dance with a particular emphasis on Fiddle music. The event includes workshops, competitions, a ceili each night and sessions in all the pubs.
Ennis Trad 22
05 November 2015 - 09 November 2015
Ennis Trad 22 guarantees an amazing line up of talented musicians, a session trail and master classes for the fiddle, flute, accordian, concertina and uilleann pipes. Ennis Trad 22 has something for everyone.


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The Greatest Empire That Never Was
This is the first of Argentinean writer Angélica Gorodischer's nineteen award-winning books to be translated into English. In eleven chapters, Kalpa Imperial's multiple storytellers relate the story of a fabled nameless empire which has risen and fallen innumerable times. Fairy tales, oral histories and political commentaries are all woven tapestry-style into Kalpa Imperial: beggars becomeTwo Short Novels of Love and Cooking in New Orleans
hese two short novels bookend Poppy Z. Brite's cheerfully chaotic series starring two chefs in New Orleans. The Value of X introduces G-man and Rickey, who grew up in New Orleans' Lower Ninth Ward and who are slowly realizing there are only two important things in life: cooking and each other. Rickey's parents aren't quite so taken with the boy's plans and get him an impossible-to-resist place atThe Unreal and the Real: Selected Stories Volume One
Praise for Ursula K. Le Guin's short story collections: "It is the author's more serious work that displays her talents best. . . . [A] classy and valuable collection."—Publishers Weekly "A master of the craft."—Neil Gaiman The Unreal and the Real is a two-volume selection of Ursula K. Le Guin's best stories. It is a much-anticipated event and there is no doubt it will delight, amuse, and provoke.

subset: commoncrawl


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Bereavement, depression, and our growing geriatric population.
The population of the United States is in great flux. In the 1970s and 1980s, as the baby boomer generation grew up, the majority of citizens were young, healthy, and often acted in the role of care provider to their loved ones. Today, as that generation ages, the populace is becoming more elderly, more medically unstable, and more likely to require care from family and social institutions. This cohort is now beginning to experience other difficulties associated with aging as well. The loss of a spouse or companion can be devastating, and this can be a major turning point in these patients' lives. In fact, it is estimated that 51% of women and 14% of men will be widowed at least once after age 65. (1) When bereavement is experienced in an appropriate manner, the patient can grieve their loss, fondly reminisce about shared experiences, and eventually move on through their developmental journey. They may spend time concentrating on their grandchildren, they may become involved in a cause they believe in, or they may mentor a young person with similar interests. However, when grief is complicated, it may become sufficiently severe as to induce any number of poor outcomes. These can include delayed or prolonged grief, suicidal ideations, new onset of psychotic symptoms, or the development of a major depressive episode. (1)In this issue, Williams (2) reviews the literature regarding the effects of bereavement and depression on recently widowed spouses. It is very obvious that bereavement often leads to depression and that both are associated with increased morbidity. In fact, patients with depression have been found to have an increased incidence of death from cardiovascular illness. (2,3) It is not clearly understood how this happens, but there are multiple theories. These theories range from depression affecting health behaviors leading to the development of heart disease to depression promoting the development of atherosclerosis. (3) Regardless of the association between cardiac illness and depression, the diagnosis and treatment of depression in the elderly will become of increasing importance as the population ages. Therefore, there must be an increase in the vigilance in which we screen for this disease.
One of the first points to consider is whether the patient's clinical presentation is a major depressive episode or simply bereavement. In those patients with a major depression, any mood symptoms are usually pervasive and unremitting. (1) Mood fluctuations are common in patients who are experiencing grief, as they often describe grief as coming at them "in waves." (1) Other symptoms more common in major depression rather than grief include excessive guilt, suicidal ideations, preoccupations with worthlessness, unremitting functional impairment, and hallucinatory experiences (other than transiently seeing or hearing the decreased). (4) This underlies the primary problem that there is often some difficulty in diagnosing depression in the geriatric population. In a recent study by Unutzer et al, (5) it was noted that late life depression is common in the primary care setting but that it was not frequently diagnosed or treated. There are many reasons for this, including the fact that the elderly themselves minimize or deny their symptoms. (6) They may become preoccupied with somatic symptoms, which may further decrease the chance of detection in the primary care setting. These may be cases of "masked" depression in which a patient focuses on physical rather than mood symptoms. (6) Symptoms of depression may also overlap with dementia or may be assumed to be a part of "normal aging." (6) All of the above are reasons that all physicians will need to have a high index of suspicion for geriatric depression, especially in cases in which there is a greatly increased risk, such as a recent loss of a loved one.
Unfortunately, the old mnemonic "SIG E CAPS" (Sleep, Interest, Guilt, Energy, Concentration, Appetite, Psychomotor, and Suicide) is probably not a great choice to screen for geriatric depression, although it is better than no screen at all. However, there are a number of different scales that can be used. These include the Beck Depression Inventory, the Hamilton Depression Rating Scale, the Symptom Check List 90-Revision, and the Zung Depression Scale, among others. (4) However, these can take anywhere from 5 minutes to 20 minutes to administer and may not be viable choices in a busy primary care practice. In that case, consideration can be given to using the Beck Depression Inventory (which has a primary care and brief screen version) or the Geriatric Depression Scale, both of which are very brief and are patient self-report instruments. (3)
In summary, as physicians, we are looking at a significant increase in the number of geriatric patients seen in our practices in the very near future. As America ages, we need to be prepared so we can continue to provide the best medical care to our patients. That care includes being able to diagnose and treat depression in the geriatric population. This is especially important in those patients who are vulnerable. As our patients age, they will experience losses, such as widowhood, that will make them more likely to have depression. As noted in Williams' article, there is a significant connection between grief, depression, and cardiovascular disease. By aggressively diagnosing and treating depression, we can help decrease our patients' overall morbidity.
Accepted June 15, 2004.
Please see "Depression as Mediator Between Spousal Bereavement and Mortality from Cardiovascular Disease: Appreciating and Managing the Adverse Health Consequences of Depression in an Elderly Surviving Spouse" on page 90 of this issue.
1. Sadock BJ, Sadock VA: Kaplan and Sadock's Synopsis of Psychiatry: Behavioral Sciences Clinical Psychiatry. Philadelphia, PA, Lippincott Williams & Wilkins, 2003.
2. Williams JR. Depression as a mediator between spousal bereavement and mortality from cardiovascular disease: appreciating and managing the adverse health consequences of depression in an elderly surviving spouse. South Med J 2005;98:90-95.
3. Sayers SL. Depression and heart disease. Psychiat Ann 2004;34:282-288.
4. McDaniel JS, Brown FW, Cole SA. Assessment of depression and grief reactions in the medically ill. In Stoudemire A, Fogel BS, Greenberg DB (eds). Psychiatric Care of the Medical Patient. New York, NY, Oxford University Press, 2000, ed 2, pp 149-164.
5. Unutzer J, Simon G, Belin TR, et al. Care for depression in HMO patients aged 65 and older. J Am Geriatr Soc 2000;48:871-878.
6. Unutzer J, Small GW, Gunay I. Geriatric Medicine. In Wise MG, Rundell JR (eds). The American Psychiatric Publishing Textbook of Consultation Liaison Psychiatry: Psychiatry in the Medically Ill. Washington, D.C. American Psychiatric Publishing, Inc, ed 2, pp 853-869.
Glenn Catalano, MD
From the Department of Psychiatry and Behavioral Medicine, University of South Florida College of Medicine, Tampa, FL.
Reprint requests to Glenn Catalano, MD, University of South Florida Psychiatry Center, 3515 East Fletcher Avenue, Tampa, FL 33613. Email: email@example.com
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Author: | Catalano, Glenn |
Publication: | Southern Medical Journal |
Article Type: | Editorial |
Geographic Code: | 1USA |
Date: | Jan 1, 2005 |
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The Fast Show (Windows)
Genre Perspective Theme Misc |
100 point score based on reviews from various critics. 4.0
5 point score based on user ratings. |
This is a set of desktop/screensaver tools and film clips, mixed with short games based on episodes of The Fast Show comedy TV series from BBC. Colin Hunt's Office Trolley offers desktop customization and screensavers, Jesse's Thought for the Day is a desktop clock and calendar, and Rowley Birkin's Video Chestnuts contains clips from the show.The three included games are the Chanel 9 Ton Big Show Quizzico Bonanzo trivia game for one or two players, Appeaze the Squeezy Cheezy Peaz! as a Space Invaders clone where food falling from the sky needs to be shot with a pea-pod, and Ken and Kenneth ... Well Suited! as a memory game where a mannequin needs to be dressed identically to how the clerks did it at the start.
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I no longer work at Microsoft, so please don't bother leaving a comment here or trying to contact me through my MSDN blog.
You can find my new blog at http://www.technologytoolbox.com/blog/jjameson. My new site also provides copies of all posts from my MSDN blog.
It occurred to me this morning that while I previously shared some details on how I manage my MSDN blog, I've never shared my method for formatting code for the Web.
Actually, calling it "my method" is definitely a bit of a stretch. I certainly didn't come up with the approach but rather refined someone else's approach (and code) to suit my needs. The original credit goes to David Anson.
Prior to adopting David's approach, I previously copied code from Visual Studio, pasted it into Microsoft Word, then copied it again in Microsoft Word, and finally pasted into Expression Web. While this achieved the desired end result -- meaning, formatted code with color syntax highlighting -- it definitely was a little kludgey. First, the four-step process -- while not excessively tedious -- was definitely less than desirable, because it often meant I had to fire up Word for the sole purpose of formatting code (note that copy/paste from Visual Studio into Expression Web does not preserve the formatting). Second -- and more importantly -- the resulting HTML markup was just "crap" (sorry, I can't think of a more eloquent way to put that right now).
When I started looking at approaches for improving the formatting of code for my blog, I found that there were numerous "solutions" out there. However, I knew what I really wanted was something that would produce a minimal amount of HTML markup (or at least a lot less HTML than Microsoft Word) and, preferably, something that generated semantic markup as well -- or at least reasonably semantic markup.
What I mean by semantic markup is that code should be wrapped in a  tag -- as well as a
 tag (in order to correctly display line breaks, indenting, etc.). To understand what I mean by semantic markup for code, consider the following example:
using System; public class Class1 { public Class1() { string foo = "foo"; } }
In HTML markup, this is expressed as:

using System; public class Class1 { public Class1() { string foo = "foo"; } }

The
 element is used to constrain lengthy code blocks (i.e. show a vertical scrollbar when necessary) and also format code with a background color and border.

Note that in the stricted sense, this isn't 100% semantic markup because the  tags are used to apply presentational styles, namely the various font colors. Truly semantic markup for code would specify something more like this:

using System; public class Class1 { public Class1() { string foo = "foo"; } }

CSS rules could then be used to achieve the color syntax highlighting:
code .keyword { color: #0000ff; } code .string { color: #a31515; } code .userType { color: #2b91af; }
Anyway, getting back to the real topic for this post...
I really liked David's approach since a) it was simple (meaning I didn't need to spend much time understanding his code sample), and b) it leveraged Visual Studio to handle the bulk of the formatting work.
However, there were a couple of "fixes" that I found I needed:

I also wanted to eliminate extraneous  tags for the default color (i.e. black).
Note that -- at least to this point -- I haven't made any attempt to generate 100% semantic markup (by converting the style attributes to corresponding CSS class names), because I think it would be somewhat brittle (i.e. dependent on the default color options in Visual Studio) and, honestly, not worth the effort.
Update (2010-04-27) After upgrading to Visual Studio 2010, I discovered that "\par" tags in the RTF were not being converted to new lines in David's original code (because Visual Studio 2008 didn't emit "\par" tags in the RTF, but rather "\r\n"). Consequently I updated the code below to work with Visual Studio 2010 (similar to the changes described in David's updated post from last December).
Here's the updated code that I now use for my Rtf2Html.exe utility:
// Original source: // http://blogs.msdn.com/delay/archive/2008/03/13/ // blogging-code-samples-should-be-easy-free-convertclipboardrtftohtmltext-tool-and-source-code.aspx using System; using System.Collections.Generic; using System.Drawing; using System.Text; using System.Windows.Forms; // Convert Visual Studio 2008 RTF clipboard format into HTML by replacing the // clipboard contents with its HTML representation in text format suitable for // pasting into a web page or blog. // USE: Copy to clipboard in VS, run this app (no UI), paste converted text // NOTE: This is NOT a general-purpose RTF-to-HTML converter! It works well // enough on the simple input I've tried, but may break for other input. // TODO: Convert into a real application with a notify icon and hotkey. namespace ConvertClipboardRtfToHtmlText { static class ConvertClipboardRtfToHtmlText { private const string colorTbl = "\\colortbl;"; private const string colorFieldTag = "cf"; private const string tabExpansion = " "; [System.Diagnostics.CodeAnalysis.SuppressMessage( "Microsoft.Maintainability", "CA1502:AvoidExcessiveComplexity")] [STAThread] static void Main() { if (Clipboard.ContainsText(TextDataFormat.Rtf)) { // Create color table, populate with default color List<Color> colors = new List<Color>(); Color defaultColor = Color.FromArgb(0, 0, 0); colors.Add(defaultColor); bool insideSpan = false; // Get RTF string rtf = Clipboard.GetText(TextDataFormat.Rtf); // Parse color table int i = rtf.IndexOf( colorTbl, StringComparison.OrdinalIgnoreCase); if (-1 != i) { i += colorTbl.Length; // When copying from Visual Studio, we expect // "\\colortbl;\r\n". However when copying from SQL Server // Management Studio, we expect just "\\colortbl;". SkipOptionalText(rtf, ref i, "\r\n"); while ((i < rtf.Length) && ('}' != rtf[i])) { // Add color to color table SkipOptionalText(rtf, ref i, "\r\n"); SkipExpectedText(rtf, ref i, "\\red"); byte red = (byte)ParseNumericField(rtf, ref i); SkipExpectedText(rtf, ref i, "\\green"); byte green = (byte)ParseNumericField(rtf, ref i); SkipExpectedText(rtf, ref i, "\\blue"); byte blue = (byte)ParseNumericField(rtf, ref i); colors.Add(Color.FromArgb(red, green, blue)); SkipOptionalText(rtf, ref i, "\r\n"); SkipExpectedText(rtf, ref i, ";"); } } else { throw new NotSupportedException( "Missing/unknown colorTbl."); } // Find start of text and parse i = rtf.IndexOf("\\fs", StringComparison.OrdinalIgnoreCase); if (-1 != i) { // Skip font size tag while ((i < rtf.Length) && (' ' != rtf[i])) { i++; } i++; // Begin building HTML text StringBuilder sb = new StringBuilder(); sb.Append("

"); while (i < rtf.Length) { if ('\\' == rtf[i]) { // Parse escape code i++; if ((i < rtf.Length) && (('{' == rtf[i]) || ('}' == rtf[i]) || ('\\' == rtf[i]))) { // Escaped '{' or '}' or '\' sb.Append(rtf[i]); } else { // Parse tag int tagEnd = rtf.IndexOf(' ', i); if (-1 != tagEnd) { if (rtf.Substring( i, tagEnd - i).StartsWith( colorFieldTag, StringComparison.OrdinalIgnoreCase)) { // Parse color field tag i += colorFieldTag.Length; int colorIndex = ParseNumericField(rtf, ref i); if ((colorIndex < 0) || (colors.Count <= colorIndex)) { throw new NotSupportedException( "Bad color index."); } if (insideSpan == true) { sb.Append(""); insideSpan = false; } // Change to new color if (colors[colorIndex] != defaultColor) { sb.AppendFormat( "", colors[colorIndex].R, colors[colorIndex].G, colors[colorIndex].B); insideSpan = true; } } else if ("par" == rtf.Substring(i, tagEnd - i)) { sb.Append(Environment.NewLine); } else if ("tab" == rtf.Substring(i, tagEnd - i)) { sb.Append(tabExpansion); } // Skip tag i = tagEnd; } else { throw new NotSupportedException( "Malformed tag."); } } } else if ('}' == rtf[i]) { // Terminal curly; done break; } else { // Normal character; HTML-escape '<', '>', and '&' switch (rtf[i]) { case '<': sb.Append("<"); break; case '>': sb.Append(">"); break; case '&': sb.Append("&"); break; default: sb.Append(rtf[i]); break; } } i++; } // Trim any trailing empty lines while ((2 <= sb.Length) && ('\r' == sb[sb.Length - 2]) && ('\n' == sb[sb.Length - 1])) { sb.Length -= 2; } // Finish building HTML text if (insideSpan == true) { sb.Append(""); insideSpan = false; } sb.Append("

"); // Update the clipboard text Clipboard.SetText(sb.ToString()); } else { throw new NotSupportedException( "Missing text section."); } } } // Skip the specified text private static void SkipExpectedText(string s, ref int i, string text) { foreach (char c in text) { if ((s.Length <= i) || (c != s[i])) { throw new NotSupportedException("Expected text missing."); } i++; } } private static void SkipOptionalText( string s, ref int i, string text) { string substring = s.Substring(i, text.Length); if (substring == text) { i += text.Length; } } // Parse a numeric field private static int ParseNumericField(string s, ref int i) { int value = 0; while ((i < s.Length) && char.IsDigit(s[i])) { value *= 10; value += s[i] - '0'; i++; } return value; } } }
I suppose I could have kept the ConvertClipboardRtfToHtmlText moniker that David originally had, but for some reason I decided to abbreviate it. In hindsight, I'm really not sure why I didn't keep the name, but oh well...
Whenever I need a code sample in a blog post, I simply copy the code in Visual Studio, double-click Rtf2Html.exe in my Toolbox, and then paste into Expression Web. It's still a three-step process, but not one that takes more than three or four seconds, and more importantly, it now produces much better HTML markup than the hack I used to use with Microsoft Word.


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US 4334185 A Abstract A circuit for automatic gain control of a feedback system in a time that is essentially constant regardless of the signal level includes a device for producing a signal that is representative of the output of the circuit. The signal is compared with a fixed reference to determine an error signal. The error signal is multiplied by its own time integral to obtain a control signal for a weighter that is cascaded with an amplifier to provide a controlled forward path. By this means, gain of the controlled forward path is controlled within a time that is substantially independent of signal strength.
Claims(5) 1. A circuit for automatic control of gain between an input terminal and an output terminal of a system having a continuous a-c signal at the input terminal, the circuit comprising:
a weighter connected to the input terminal and receiving the continuous a-c signal therefrom, the weighter attenuating the continuous a-c input signal by a controlled amount; an amplifier connected to the weighter and to the output terminal and receiving from the weighter a signal that is amplified and delivered as an output signal to the output terminal; a detector connected to the output terminal and responsive to a measure of amplitude of the output signal to generate therefrom a detected signal; a controllable source of a predetermined reference electrical quantity; a comparator connected to the detector and the controllable source to produce an output that is the difference between the reference electrical quantity and the detected signal; a multiplier connected to the comparator and receiving as a first input the comparator difference output; and an integrator connected to the multiplier and the weighter, the integrator receiving as an input an output signal from the multiplier, the integrator producing an integrated output signal that is taken as a second input to the multiplier and as a control signal to the weighter to determine the controlled amount of attenuation of the weighter. 2. The circuit of claim 1 wherein the continuous a-c signal is an amplitude-modulated carrier.
3. The circuit of claim 1 wherein the continuous a-c signal is a frequency-modulated carrier.
4. The circuit of claim 1 wherein the continuous a-c signal is single sideband with a vestigal carrier.
5. The circuit of claim 1 wherein the weighter is a PIN-diode attenuator.
Description This invention relates to automatic gain control (AGC) in systems using feedback. In particular, it is a method and means of achieving AGC with a substantially constant response time over a relatively wide dynamic range. This is of especial importance in radio receivers in which a signal must typically be controlled over a wide dynamic range, and it has applications in other control systems. The normal operation of radio receivers calls for the development of an output signal that is constant in level despite variations in the level of the carrier of a received signal. A properly designed receiver will leave the listener unaware of most of the fading or other variations that may occur in a signal to which he is tuned, and it will also leave him unaware of differences in the average received signal strengths of the carriers of different stations to which he may tune. To accomplish these objectives, it is customary to apply AGC to a receiver. This is a feedback system that adjusts the gain of one or more elements in a circuit in response to the level of the carrier in the system. In most such systems, gain is essentially an exponential function of the amplitude of the feedback signal. If the controlled amplifier is a bipolar transistor, the gain is essentially an exponential function of the average value of the base-emitter voltage. However, there are disadvantages that can arise from applying ACG to transistors. When AGC is applied to an amplifier, the input and output impedances of the amplifier are normally changed from their values without AGC. The introduction of AGC may also lead to instability in a transistor stage. A further disadvantage is the fact that changing the operating point of a transistor amplifier may increase the distortion produced by intermodulation in the amplifier. All of the effects listed above are disadvantages that must be overcome. One way of overcoming these disadvantages is to connect a controlled variable attenuator in cascade with an amplifier having fixed gain, and applying feedback control to the variable attenuator. However, this creates the corresponding disadvantage of making the response time of the controller a strong function of the input signal level. This is the case with a PIN diode attenuator in which attenuation is a linear function of signal strength. It would be advantageous to keep the response time independent of signal strength. It is an object of the present invention to provide a system of automatic gain control that has a substantially constant bandwidth. It is a further object of the present invention to provide a system of automatic gain control that adjusts to a change in input in a time that is essentially independent of the size of the change. Other objects will become apparent in the course of a detailed description of the invention. A system for automatic gain control with a substantially constant bandwidth is achieved by placing a controllable weighter in cascade with an amplifier having a fixed gain. The carrier level or some other measure of the signal strength of the output of the amplifier is detected, and a signal proportional to the signal level is applied to a summer where it is compared to a reference voltage. A signal that is the difference between the reference voltage and the detected voltage is applied to a multiplier, and the output of the multiplier is integrated and taken as both a second input to the multiplier and a control signal to the weighter. The multiplier creates a non-linear response in a feedback network that causes the network to respond faster to large changes in carrier levels than it does to smaller changes, thus tending to produce a constant bandwidth for the system. FIG. 1 is a functional block diagram of a circuit for the practice of the present invention. FIG. 2 is a diagram of a circuit for the practice of the present invention. FIG. 1 is a functional block diagram of a circuit for the practice of the present invention. In FIG. 1 a weighter 10 receives an input signal from an input line 12. The weighter is connected to an amplifier 14 which receives and amplifies the output signal from weighter 10. The output of amplifier 14 is taken on line 16 as the controlled output from the circuit and is also conducted to detector 18 which produces an output proportional to the signal level on line 16. The output of detector 18 is applied to comparator 20 in which a reference voltage from source 22 is subtracted from the output from detector 18. The difference signal is taken from comparator 20 to multiplier 24, and the multiplied signal is integrated in integrator 26. Multiplier 24 receives as a second multiplying input the output of integrator 26. That output is also taken to control the setting of weighter 10. When the level of the signal at the output of amplifier 14 is not changing, the output of comparator 20 is zero, as is the output of multiplier 24. The output of integrator 26 is thus a constant, so that weighter 10 holds whatever setting it has had. if the level of the signal on line 12 increases, the signal on line 16 increases, increasing the output from detector 18. Comparator 20 will then produce a positive output which is multiplied in multiplier 24 by the integrated output of multiplier 24 to produce a signal as an input to weighter 10 that will attenuate the signal on line 12, reducing the input to amplifier 14 and hence its output. This change will continue until the output of comparator 20 drops to zero, when the circuit is again at its steady state. Operation of the circuit with a decrease in signal is similar, tending to restore the constant output level on line 16. The presence of multiplier 24 in the circuit of FIG. 1 increases the input to integrator 26 disproportionately for larger changes in signal level, thus driving the weighter 10 to restore equilibrium in the feedback network. The multiplier 24 introduces a nonlinearity that causes the network to return to equilibrium following a disturbance at a rate that is a function of the magnitude of the disturbance. FIG. 2 is a circuit diagram of an apparatus for the practice of the present invention. In FIG. 2, a PIN diode bridge attenuator 32 receives an incoming signal Vin and attenuates that signal according to a setting of the attenuator 32. Signal Vin is typically a carrier that may be modulated with AM, FM or single sideband with at least a vestigial carrier, although it may equally as well be any continuous a-c signal. The output of attenuator 32 is amplified in amplifier 34 to become the output voltage Vout of the circuit. That voltage is also applied to detector 36 which responds to DC or slowly varying portions of the output signal. The detected output of detector 36 is compared in summer 38 with an adjustable voltage from a reference source 40. The voltage of reference source 40 sets the overall gain of the circuit. This is the value to which the gain is controlled. The difference between the voltage from reference source 40 and that from detector 36 is applied to quad multiplier 42. The multiplied output of quad multiplier 42 is integrated by the combination of high-gain amplifier 44 and integrating capacitor 46 to generate an output that is taken as a second input to quad multiplier 42. Thus, the input to quad multiplier 42 from summer 38 is multiplied by its integral to produce an output. The integrated output of high-gain amplifier 44 is taken to voltage-to current converter 48 which generates a current proportional to the output of high-gain amplifier 42 to control the setting of PIN diode attenuator 32. The circuit of FIG. 2 was built and operated at a frequency of 11.7 MHz. In that circuit the amplifier 34 was an FET amplifier having a gain of 23 dB. Detector 36 was a diode detector, and the summer 38 was an operational amplifier with differential inputs. Quad multiplier 42 was a linear four-quadrant multiplier that is a catalog item, and amplifier 44 and voltage-to-current amplifier 48 were operational amplifiers. With this circuit, over a variation of approximately 50 dB of attenuation, the weighter followed a characteristic that was close to linear. Specifically, the gain W of the weighter over that range was given by W=KI.sup.(0.95) where K is a static weighting constant. Using that weighter, the response of the circuit was obtained by measuring the 3-dB bandwidth as a function of the input power. The bandwidth was obtained by applying an RF signal with essentially 100% amplitude modulation by a pure sinusoid of varying frequency. For each level of input power the output of the integrator was monitored with a modulating signal well within the passband, and then the frequency of a modulating signal was increased until the measured value of the output of the integrator decreased by 3 dB. This provided a measure of the half-power bandwidth of the control circuit. The results of this measurement are shown in Table 1. TABLE I______________________________________Bandwidth as a function of input power for the circuit ofFIG. 2Input Power 3 dB Bandwidth(dBm) (Hz)______________________________________-100 10.5-90 9.4-80 8.8-70 8.0-60 8.0-50 8.0-40 8.0-30 7.9-20 7.9-10 7.8______________________________________ An inspection of Table 1 shows that the bandwidth was constant to within 2% of its value over a range of input powers from -70 dBm to -10 dBm. For input power levels below -70 dBm, the bandwidth begins to increase at a moderate rate. In the absence of the circuit of the present invention, that bandwidth would have varied by a factor of about one thousand with a variation of the input signal from -10 dBm to -70 dBm. Patent Citations
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The PLHRQD7B is a unique, 7-inch quad-view TFT monitor from Pyle designed for in-vehicle applications & home security. Connect up to four video inputs to this monitor and then view them in a variety of modes: single view, split dual video, and quad four source view. The reverse function allows you to flip a monitor's contents, such as a rear back up camera. A wireless, fully functional remote control is included to change sources and adjust video settings. This monitor is universal stand compatible for a variety of mounting options - or mount these monitors to the back of a headrest. The included headrest shroud allows you to mount these monitors flush into most surfaces. PAL and NTSC compatible. Color: black.
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Additional Info
Manufacturer | Pyle |
Model Number | PLHRQD7B |
Length | 14.70 |
Width | 9.50 |
Height | 2.90 |
UPC Code | N/A |
Condition | New |
Color | No |
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'Disturbing' cruelty halts live exports to Egypt
PUBLISHED: 06 May 2013 00:05:54 | UPDATED: 06 May 2013 00:31:39PUBLISHED: 06 May 2013 PRINT EDITION: 06 May 2013The latest suspension of live cattle exports to Egypt will come at a cost of more than $50 million to Australia.
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Does your plugin accomodate SSL for admin or the whole site?
Does your plugin accomodate SSL for admin or the whole site?
Can you be more specific? If you are using SSL and have a valid SSL certificate then BPS Pro works fine on websites using SSL.
I'm thinking more like Better WP Secure which has the ability to SSL the Admin area, a single page, or the whole site as part of the plugin.
This is a security feature lacking in WP.
Encrypting the admin area is a great addition to any security plan for WP. Encrypting the whole site, whether commerce or not, is a great idea however I understand not all plugins would function well in that environment.
Uh yeah i think you better take a look at that plugin's "What others are saying" area before you decide to try that plugin. ;) You are forewarned that you should perform a backup and they are serious - so do not skip that part or you will be sorry if something goes horribly wrong. I have assisted several people in recovering their websites after using that plugin and it is a royal pain to fix everything so do the backup.
I'm not saying that it is a bad plugin. I would be very apprehensive to use it on a Live Production website unless i had thoroughly tested it first because if you make a mistake it WILL destroy your website. I think what has happened with the development of that plugin is that they have tried to develop the plugin in too many directions at once and it appears they are spread a little too thin. Several versions in a row broke ALL websites, which usually indicates either rushing, carelessness or biting off more then you should be chewing at one time.
True SSL requires a valid SSL certificate.
Forced or Pseudo-SSL is not really as secure as true SSL because it is not really valid SSL. I can easily get around / hack Pseudo-SSL, where real SSL is not beatable.
And i agree that, that is an interesting security approach using encryption, but not a website security direction i would ever choose because of the direction Zend is going with Zend Guard and the Encryption that they use and more importantly what is coming in the future of Zend. This is an inevitable train wreck that has not happened quite yet, but it will eventually.
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US 3798560 A Abstract A second-order digital filter arrangement having output taps from each of two first-order subsections and a pair of adjustable gain devices connected at each tap is modified by providing reentrant connections around the entire filter and also its first-order subsections to perform the function of a nonrecursive multitap transversal equalizer. One of each pair of gain devices serves as a forward-feeding tap signal multiplier. The remaining one of each pair of gain devices serves as a correlator for tap and error signals to adjust the gain of a tap signal multiplier. Memories for storing output signals and updated tap gain coefficients are programmed on a time-division basis while message signals are being circulated through the digital filter subsections. The capability of reconversion to the recursive digital-filter form under program control is at all times preserved.
Claims available in Description (OCR text may contain errors) Patent [1 1 Mar. 19, 1974 ADAPTIVE TRANSVERSAL EQUALIZER USING A TIME-MULTIPLEXED SECOND-ORDER DIGITAL FILTER [75] Inventor: Michael Gordon Taylor, Holmdel, Assignee: Bell Telephone Laboratories, Incorporated, Murray Hill, NJ. Filed: Jan. 29, Appl. No.: 327,622 References Cited UNITED STATES PATENTS Schu Elliott 328/167 ...'333/18 X Esterban 328/167 X Primary ExaminerPau1 L. Gensler Attorney, Agent, or Firm-J. P. Kearns ABSTRACT A second-order digital filter arrangement having output taps from each of two first-order subsections and a pair of adjustable gain devices connected at each tap is modified by providing reentrant connections around the entire filter and also its first-order subsections to perform the function of a nonrecursive multitap transversal equalizer. One of each pair of gain devices serves as a forward-feeding tap signal multiplier. The remaining one of each pair of gain devices serves as a correlator for tap and error signals to adjust the gain of a tap signal multiplier. Memories for storing output signals and updated tap gain coefficients are programmed on a time-division basis while message signals are being circulated through the digital filter subsections. The capability of reconversion to the recursive digital-filter form under program control is at all times preserved. TATENTED MAR l 9 I974 SHEEI 2 OF 4 FIG. 2 PRIOR ART ADDERS DIGITAL DELAY UNITS ADJUSTABLE GAIN DEVICES DIGITAL Z DELAY UNITS Z n N ADJUSTABLE l l GAIN DEVICES 2; FIG. 3 V f52n 2ND ORDER SECTION 2ND ORDER SECTION 2ND ORDER sEcTIoN PATENTEUHAR 19 I974 SHEET 3 OF 4 FIG. 4 DELAY DELAY PATENTEMR 19 m4 1 3798560 saw u or 4 2 REGISTER ADAPTIVE TRANSVERSAL EQUALIZER USING A TIME-MULTIPLEXED SECOND-ORDER DIGITAL FILTERv FIELD OF THE INVENTION This invention relates generally to digital electricwave filters and more specifically to the adaptation of a second-order digital filter to serve as an automatic transversal equalizer. BACKGROUND OF THE INVENTION In a paper by L. B. Jackson, J. F. Kaiser and H. S. McDonald published in the September 1968 issue of IEEE Transactions on Audio and Electroacoustics (Vol. AU-l 6, No. 3) and entitled An Approach to the Implementation of Digital Filters" the general characteristics of digital filters are outlined and the principlal canonical forms are described. Digital filters accomplish the frequency shaping of continuous waveforms by operating on discrete signal samples of these waveforms with digital components, such as adders, subtractors, multipliers and shift registers. Digital filters avoid the use of reactive circuit components and piezoelectric crystals which must generally be tailored to the specific circuit application under conventional analog design techniques. Digital filters are adaptable to the building block concept. The increasing availability of integrated circuits makes digital filters more attractive from the standpoints of cost, size and reliability than conventional analog filters in many applications. The basic direct-form digital filter comprises a plurality of delay units readily implemented by shift registers connected in series, input and output combining circuits,and a plurality of multipliers placed in feedback and feedforward relationships between evenly spaced taps at the delay units and the respective input and output combining circuits. For compatibility with continuous analog circuits the digital filter is preceded and followed by respective analog-to-digital and digital-toanalog converters. The number of stages in each shiftregister delay unit is determined by the number of serial bits in each word encoding an analog input sample. The total number of delay units is determined by the order of the algebraic equation (a ratio of polynomials) defining the filter transfer function desired to be implemented. The delay amount provided by each delay unit is typically the symbol interval of the data being processed. As explained by Jackson et al, the ratio of polynomials of arbitrary order defining a direct-form digital filter can be transformed into continuing products of secondorder polynomial quotients. The hardware required to implement this cascade form of the digital filter becomes simplified into a sequence of second-order building blocks. In this cascade form of the digital filter each second-order stage compreises two delay units and two pairs of feedforward and feedback multipliers whose operating coefficients are the only variables from stage to stage. Such a cascade of identical delay units can be implemented with a single second-order section whose feedforward and feedback coefficients are time multiplexed to form a read-only memory while the samples being operated on are recirculated from output to input until all coefficients have been applied to each sequential sample. The time-multiplexing principle for operation of a cascade-form digital filter using only one second-order section cannot readily be applied to the nonrecursive transversal equalizer function because complete pro cessing of each sample of the input signal cannot be accomplished within a single sampling interval. In addition, processing is often required on a per symbol basis rather than on a per sample basis. Furthermore, the coefficients applied to the several selected signal samples are a function of an error signal determined from a summation of a plurality of products of prior signal samples and a plurality of independently variable tapgain coefficients. SUMMARY OF THE INVENTION It is accordingly an object of this invention to realize a nonrecursive transversal equalizer for a synchronous digital data transmission system from a single timemultiplexed second-order digital filter section. It is another object of this invention to realize both nonrecursive and recursive filters compatibly from a common single second-order digital filter section. It is still another object of this invention to realize an adaptive transversal equalizer interchangeably with an nth order recursive digital filter from a single timemultiplexed second-order digital filter. In accordance with this invention these and other objects are achieved by modifying a second-order digital filter to permit recirculating digital signals internally around the individual delay units therein as well as around two such delay units in tandem, to permit recirculating combined feedforward tap signals and obtain a cumulative sum extending over a plurality of sampling intervals, to incorporate an error detection circuit to operate on cumulative tap-signal sums and to convert the normal feedback multipliers into tap incrementation control devices. With the removal of the feedback multipliers from the normal input combining circuit of the digital filter and the addition of circuitry to permit both internal and external recirculation of digital signals, the network becomes nonrecursive and capable of realizing the multitap transversal equalizer. The purpose for internally circulating signal samples around individual delay units is to restrict operation to once during each symbol interval where more than one sample of a signal wave is taken during each symbol interval. The purpose for externally circulating signal samples around pairs of delay units is to simulate a multitap direct-form delay system. A feature of this invention is the compatibility of hardware with both recursive and nonrecursive digital filter forms so that a straightforward change in control words effects the transformation between forms. Another feature of the invention is that the stored coefficients for feedforward multiplication are made adaptive to minimizing the error component of the accumulated outputs of the second-order section when it is used to realize a nonrecursive filter. DESCRIPTION OF THE DRAWING A more complete understanding and appreciation of this invention will be attained from a consideration of the following detailed description and the drawing in which: FIG. 1 is a block diagram of a recursive time-division multiplexed digital filter known to the prior art; modulated signals. FIG. 2 is a block diagram of the cascade form of the recursive digital filter known to the prior art; FIG. 3 is a block diagram of a nonrecursive digital filter realizable from two-tap second-order digital sections; FIG. 4 is a simplified block diagram showing a second-order digital filter section capable of arrangement in either the recursive cascade form or the nonrecursive direct form according to this invention; and FIG. 5 is a block diagram showing the modifications according to this invention for converting a timemultiplexed second-order digital filter into an adaptive nonrecursive, direct-form transversal equalizer. DETAIbED oEsc uPTroN A receiver for a digital data transmission system employing a time-multiplexed digital filter of low-order is illustratd in FIG. 1. The prototype for this arrangement is found in FIG. 4 of U.S. Pat. No. 3,522,546 issued on Aug. 4, 1970 to L. B. Jackson and H. S. McDonald. A data signal wave received from a data transmission channel on input line 11 is first converted to multibit digital word form in analog-to-digital converter 12 at a sampling rate much higher than the highest frequency present in the channel signal, e.g., 9,600 samples per second to yield four samples per symbol of a 2,400-bitper-second data wave. Each sample taken is converted into a multidigital word of 12 bits, for example. Once the sample traverses input switch 13, it is entered in the first shift register storage subsection of digital filter 15. Assuming filter is of second-order, two shift registers are provided in tandem and each register includes a large number of stages or time slots of the order of 40 or 50. Thus, for each data sample taken a large number of different operations, such as filtering, demodulation, demultiplexing and equalization, can be performed in successive time slots. Output switch 16 permits the samples to be recirculated by way of path 14 through filter 15 during the successive time slots. The final output of filter 15 is applied by way of output switch 16 to digital-to-analog converter and data sink 21. The array of coefficients to be applied over leads 17 to filter 15 according to a predetermined program during the several time slots is stored in memory 18. Timing and program control 19 controls the sampling rates at converters 12 and 20, the openings and closings of switches 13 and 16, and the transfer of the correct 00-- efficients to filter 15. It is within the skill of the art to devise programs for handling different types of data signals, such as baseband and passband amplitude modulated signals as well as frequency-modulated and phase- A digital filter realizes a transfer function of the form n order of the filter (this is constrained to be less than or equal to twice the maximum number of time slots per sampling period), a, feedforward gain coefficient for the ith delay element, b, feedback gain coefi'icient for the ith delay ele ment, N numerator, and D denominator. Equation 1 defines the direct form of the digital filter as illustrated, for example, in FIG. 2 of the cited Jackson et al patent. If at least one b, coefficient is nonzero, the filter is said to be recursive, i.e., previous outputs are combined with present inputs. If all b, coefficients are zero, the filter is said to be nonrecursive, i.e., only previous inputs are used to form new outputs and no previous outputs are so used. Although the direct form of the digital filter has the capability of realizing either recursive or nonrecursive transfer functions, it is not generally used to realize the recursive function because the latter function is sensitive to small changes in the location of the poles, i.e., frequencies at which the denominator of equation (1 goes to zero. The pole locations are thus sensitive to small changes in the b, coefficients. Accordingly, the b, coefficients must be precisely determined in the directform digital filter. Equation l can be factored by using standard techniques into a continued product of second-order rational functions, namely, where m the maximum number of time slots per sampling period. Equation (2) can be realized as a cascade of secondorder digital filter sections as shown in H6. 2. Each second-order section, comprising a tandem connection of two delay units 36 and 40 separated by a tap 38 and having an input tap 34 and an output tap 42, an input adder 33, an output adder 35, adjustable feedback gain devices 37 and 41 and adjustable feedforward gain devices 39 and 43, realizes one pair of zeros and one pair of poles in the overall transfer function. Input gain device 32 connected between input line 31 and input adder 33 realizes the scale factor n in equation (2). The left-hand second-order section uses subscripts 1, while the right-hand section uses the subscript n. Broken line 44 suggests the presence of as many additional second-order sections as are required to realize a given transfer function. Inasmuch as each section is physically the same and differs functionally from any other only in the a, and b; gain coefficients, a single section can be time multiplexed by looping output to input and changing the coefficients on each recirculation until a given program is implemented. For each recirculation a set of four gain coefficients plus a control word are stored. The control word effectively directs the signal flow through the second-order section. A control word can illustratively include on the order of twelve bits with certain bits dedicated to magnitude scaling by powers of two, to multiplexing, i.e., whether a new input is to be accepted or the old output recirculated, and to storing an output for later reuse. The adaptive transversal equalizer is an important example of .a nonrecursive transfer function employed in high-speed digital data systems which is not susceptible of realization in a straightforward manner as a cascade ing input buffer storage is required for each group. A new group of input samples is formed for each sampling interval by discarding the oldest element of the prior group and adding one new element from the input of second-order digital filter sections. The reason for 5 buffer store. A recirculation path between output and this is that the gain coefficients applied at each tap are adaptive to an error signal which can only be determined from the summation of the products of a plurality of simultaneously available tap signals each of which in turn is multipled by a different gain coefficient. FIG. 3 illustrates the generalized nonrecursive form of the digital filter with the delay units compartmentalized into pairs. It will be observed that there are no feedback gain devices. Each broken-line box 52 encompasses two delay units 56 and 60, input taps 54, intermediate taps 58, output taps 62, and an adjustable gain device 59 at each intermediate and output tap. The overall input is applied at lead 51 and the overall output is obtained as the combination of all the signals operated on by gain devices 59 on lead 75 at the output of summation circuit 65. Similar elements in the several blocks have the same basic designator, but are distinguished by the subscripts. The subscripts n and n-l suggest that there may be an indefinite number of these blocks in a practical system. The coefficients for gain devices 59 are indicated in the drawing as A1 through A5. Final block 52, has no functioning output tap and delay unit 60,, is shown for symmetry only. The operation of the arrangement of FIG. 3 as a nonrecursive digital filter can be understood if it is regarded for purposes of discussion as a five-tap structure in which each block is occupied by signals obtained from five consecutive samples available at the time i when input x(i) is received on input lead 51. At this time sample X1 is available in delay unit 56,; sample X2, in unit 60- and so forth. In second-order section 52, the single product X1 times Al is obtained and applied to adder 65. In second-order section 52( n-1) the two products 'A2X2 and A3X3 are obtained and applied to adder 65. In second-order section 52, the two products A4X4 and A5X5 are similarly obtained and also applied to adder 65. The resultant is an n-bit number representing the application of the desired transfer function to the digitally encoded input at one particular sampling time. Immediately after the above-described products are taken all values stored in delay units 56 and 60 are shifted one sample time to the right so that input x(i) X6 is stored in unit 56 sample X5 in unit 60,; sample 1 X4 in unit 56(n-1); and so forth. A new input x(i+1) X7 can now be present on input lead 51. The same gain coefficients Al through A5 are applied to the shifted samples to form the products A1X2, A2X3, input of the secondorder section can include storage for the old elements of the prior group which are to be part of the new group. Selectively controlled input and output switches determine which elements of each 10 group are discarded, recirculated or augmented from time slot. The summation of all three products constisequence A1, A2, A3, A4, and A5 in Table I. TABLE I Sample Sampling Time Gain Coef. period slot lst 2nd 1st 2nd Output 1 1 Al Xl AlXl 1 2 A3 A2 x3 x2 A2X2+A3X3 l 3 A5 A4 X5 X4 A4X4+A5X5 2 1 A1 X2 A1X2 2 2 A3 A2 X4 X3 A2X3+A3X4 2 3 A5 A4 X6 x5 A4X5+A5X6 3 1 Al X3 AlX3 It is apparent from TABLE I that each sampling period is divided into three time slots. The designations 4O first" and second applied to gain co'efficients and samples refer to the respective intermediate and output taps of a second-order section. In the first time slot of the sampling period a signal sample is operated on by the first coefficient to form the product AlXl and cor- A3X4, A4X5 and A5X6. The sum of these products, taken in adder 65, provides a second n-bit number defining the filtered signal at a second sampling time. The multiplications, additions and shifts described above are repeated until all input samples have been operated on. The continuing output can be converted to analog form in a straightforward manner. The above operations can be performed by applying consecutive inputs to a single second-order section and processing these inputs in groups having as many elements as there are delay units in the direct-form digital filter being simulated and at a speed which permits the operation of all gain coefficients on each element within a signal sampling interval. Because of the speeded-up processtutes the solution of the transfer equation for one sampling interval. The above operation can be summarized for an assumed input sequence X1, X2, X3, and coefficient responds to that of block 52,, in FIG. 3. The second time slot covers the operation on two intermediate samples of a group of two further coefficie'nts to form theproducts A2X2 and A3X3 and corresponds to that of block 52 in FIG. 3. Finally in the last time slot of a sampling period the fourth and fifth samples of a group are operated on by the last two coefficients to form the products A4X4 and A5X5. These operations correspond to those effected in block 52, of FIG. 3. These same operations are repeated in subsequent sampling periods as indicated in the remainder of TABLE I. The last column of the table lists the samplecoefficient products obtained in the several time slots. The combination of the three sets of products yields the transformed input signal sample for that interval. changing channel transmission characteristics which can only be determined after many consecutive impulse response samples have been observed. The possibility of feeding the output of the rightmost tap of a second-order section to the leftmost tap has already been discussed in connection with FIG. 3. There is a further requirement in the transversal equalizer that operations performed in both consecutive and non consecutive sampling periods, and not merely those performed in time slots within the same sampling period, be accumulated and made available for operations in subsequent sampling periods. Moreover, provision must be made for recirculating delayed signals over a plurality of sampling periods. FIG. 4 is a simplified block diagram illustrating certain modifications according to this invention in a second-order digital section to implement a multitap transversal equalizer, while preserving the capability of realizing a recursive transfer function. The structure of FIG. 4 comprises input adder 84, output adder 85, delay units 86 and 90, feedforward gain devices 89 and 93, feedback gain devices 87 and 91, single-pole switches 82 and 83 single-pole triple-throw switch 88, sing|e-pole double-throw switches 92 and 96 and auxiliary delay unit 94. Input signals are accepted on lead 81 and final outputs appear on lead 101. The recursive form of the digital filter is realized when switches 82, 83, 88, 92 and 96 in FIG. 4 are in the B position. In this condition gain devices 89 and 93 act as feedforward elements and devices 87 and 91, as feedback elements. Recirculation is accomplished externally by means not shown but within the principles discussed in connection with FIG. 1. The nonrecursive form of the filter is realized when single-pole switches 82, 83 and 92 are in the A position. Switch 88 is movable to either the A, B or C position as required and switch 96 is movable to either B or C position as required. The operation of switches 82 and 83 to positions A removes gain devices 87 and 91 and adder 84 from the circuit. The operation of switch 88 to position A provides an internal recirculation path through conductor 99 independent of output accumulator 85 to transfer unmodified signal samples from the output tap of one two-tap section to the input tap of another in effecting a multitap equalizer. The operation of switches 88 and 96 to the C position provides for recirculation through conductors 97 and 98 of unmodified signal samples around the individual delay units to preserve their contents over a plurality of sampling intervals where nonrecursive filter processing is performed at the rate of only one sample per symbol. The operation of switch 92 to the A position provides the capability of accumulating the sum of the outputs of a plurality of feedforward gain devices over an extended period. Switch 92 is moved to the A position selectively whenever it is necessary to augment the sum accumulated in adder 85. The overall operation of the nonrecursive form of the digital filter is apparent from the previous discussion of FIG. 3. Although the several switches are shown on FIG. 4 in mechanical analog form, they are susceptible of implementation in any suitable form including the use of semiconductors. The position of these switches is preferably under program control, thus allowing the second-order filter section to realize both fixed recursive cascade-form filters and adaptive nonrecursive filters. The operations associated with one recursive secondorder digital filter section include four multiplications, only two of which are required for the direct form of a nonrecursive filter. The two unused multiplications can be turned to account in implementing an adaptive nonrecursive filter by using them as error signal correlations. This change can be accomplished by means of the control word bit which effects the transformation between recursive and nonrecursive formats. A frequently implemented adaptive tap-updating algorithm for transversal equalizers is embodied in the following equation: a, gain coefficient applied to the jth equalizer tap, i time index, j tap index, k incrementation factor, x input signal sample value, and = error difference between the actual filter output and the desired output a quantized value for example. Equation (3) states that the next gain coefficient value a,(i+1) is the present value a,(i) decremented by the product of the ith input sample delayed to the jth tap location and the present error amount e(i). The incrementation factor k is realized as a power of two and in a binary shift register is effected by shifting the contents the appropriate number of stages left or right depending on whether k is lesser or greater than one. FIG. 5 shows an expansion of FIG. 4 to include the error detector and the conversion of the feedback gain devices to error correlation service. The elements that are common to FIGS. 4 and 5 carry the same designators. It is to be observed that the principal delay units are shortened by 2D amounts, where D is the width of a time slot, in order to allow time for processing and to avoid any race conditions. The auxiliary delay units and 106 in series with the output of principal delay unit 86 and units 107 and 108 in series with the output of principal delay unit 90 are each of one time-slot duration to preserve the overall delay for each first-order component at z units. Further auxiliary delay units 102, 103, 104 and 111 are provided for similar purposes. The principal differences between FIGS. 4 and 5 lie in the conversion of normal feedback gain devices 87 and 91 to correlation use by disconnecting their normal outputs on leads 114 and 115 through transferring switches 82 and 83 from B to A positions and thus connecting these outputs instead to storage registers 116 and 124. The overall output of the second-order section while in the nonrecursive equalizer mode is connected at output lead 101 to an error detector 110, which operates on accumulated outputs to take the difference between the actual output and an allowed quantized digital signal level and to deliver a binary error output by way of leads and 126 to further inputs of gain devices 87 and 91. Each such polarized error output is correlated with the signal temporarily stored in auxiliary delay unit 105 or 107 to determine an increment for the tap gain coefficient of the corresponding feedforward gain device 89 or 93. The incrementation signal from gain device 87 is applied by way of auxiliary delay device 11 1 to scaling device 112, an attenuator whose setting controls the size of the incrementation step effective on the tap gain device 93. Because of the dynamic nature of the continual shifting process the gain coefficients are not calculated and stored in register 116 until after the circulating signal from which it was derived has been shifted into principal delay unit 90. Accordingly, the register 116 stores gain coefficients a to be applied to forward tap gain device 93 over conductor 128 as shown in FIG. 5. For the same general reason of timing coordination auxiliary delay unit 111 is required between the output of gain device 87 and scaling unit 112. In a similar fashion the incrementation signal from gain device 91 is applied to scaling device 121, whose setting controls the magnitude of the incrementation step effective on gain device 89. Register 124 accumulates the tap gain coefficient values a, to be effective on forward tap gain device 89, because the circulating signal from which these values were derived has now been shifted into principlal delay unit 86. Tap gain coefficients a, are applied to forward tap gain device 89 over conductor 127 as shown in FIG. 5. Registers 116 and 124 store as many gain-coefficient words as there are taps in the equivalent direct-form equalizer. Registers 116 and 124 are-indicated as having a delay of z. units to correspond with the effective lengths of principal delay units 86 and 90. If there are fewer equalizer taps than stages in registers 116 or 124, the surplus stages are unused for equalizer purposes, but serve to keep the occupied stages in the proper time relationship with the delay units. The contents of registers 116 and 124 are continuously recirculating through adders 113 or 122, by means of which any incrementation of the contents during a particular time slot is effected from the output of gain device 87 or 91. AND-gates 117 and 123 are placed in circuit with the recirculation loops in order to zero the stored coefficients initially from a signal source (not shown) connected to zeroing input 119. It is convenient to have one coefficient corresponding to a center reference tap initially set to a value of one. This is provided for in an additional input at lead 118 through OR-gate 120 to register 116 only. The center tap is typically an oddnumbered tap and occurs at the first tap of a secondorder section. The adaptively controlled gain levels of gain devices 89 and 93 are applied to output adder 85 whose contents are also recirculated through time-slot delay unit 94 when switch 92 is in the A position. As in FIG. 4 the A position of switch 88 provides for transfer of the contents of principal delay unit 90 to the delay unit 86 at the proper sampling instant. The B position of switches 88 and 96 provide for entry of new samples into the second-order section. The C position of switches 88 and 96 provide for recirculation of the contents of principal delay units 86 and 90 over one or more sampling intervals, particularly where there is more than one sampling interval in each symbol interval. The overall operation of the second-order section of FIG. 5 is essentially that of a multitap adaptive transversal equalizer, as disclosed in U.S. Pat. No. Re 27,047 issued Feb. 2, 1971 to R. W. Lucky. On the assumption that 50 time slots of storage are available in each principal delay unit of a second-order filter, it is possible to realize an adaptive equalizer having as many as 99 taps. This number of taps is rarely necessary in voiceband data service. Typically, a suitable equalizer can be constructed using nine, 13, 17, 21 or 25 taps on a nonrecursive transversal structure. This means that only that not more than half this number of time slots need be assigned to equalizer realization and the remaining taps up to the assumed maximum of can be assigned to recursive filtering or demodulation service. Time slots in the tap-gain coefficient registers are coordinated with the signal storage cells in the principal delay units according to well known time-division multiplex principles. While this invention has been described in terms of a specific illustrative embodiment, its principles are to be understood by those skilled in the art to which it relates to be susceptible of a wide range of modification within the scope of the following claims. What is claimed is: 1. A digital filter for producing an equalized output from a distorted input signal comprising first and second delay storage units in tandem, a first and second pair of adjustable gain devices respectively connected to each of said delay storage units, an accumulating adder for combining signals operated on by one of each pair of said gain devices, means for connecting the other of each pair of said gain devices to control said one of each pair of said gain devices, an error detection circuit connected to said adder, means for applying error signals from said error detection circuit to the others of each of said pairs of gain devices for correlation with the delayed input signal thereat, first means for selectively looping the output of each said delay unit to its own input, and second means for selectively looping the output of said second delay unit to the input of said first delay unit. 2. The digital filter defined in claim 1 in which each of said delay storage units is a multistage shift register having at least as many stages as there are bits in each digitally encoded sample of said input signal. 3. The digital filter defined in claim 1 further comprising a recirculating storage register for tap-gain control signals to be applied to each of said first pair of gain devices, and means of scaling said error signals used in determining the magnitude of incrementation of said storage register. 4. The digital filter defined in claim 1 in which a switchable recirculation loop is connected between output and input of said adder to permit augmentation of prior stored sums of tap-gain controlled signals with additional sums of tap-gain controlled signals. 5. The digital filter defined in claim 1 in combination with control means for predetermining which of said first and second looping means is operative at any given time. 6. A second-order digital filter including two delay storage units in tandem, first and second pairs of gaincontrol devices connected to said delay units and input and output adder circuits to each of which are normally connected one each of said first and second pairs of gain devices: further comprising a first selectable recirculation loop around said output adder, second and third selectable recirculation loops around each of said delay storage units, a fourth selectable recirculation loop around both of said delay storage units in tandem, an error detector connected to said output adder for determining from a comparison with a quantized level the direction of the output signal error, means for applying signals from said error detector to one gain device of each of said first and second pairs of gain devices for correlation with input signal samples stored in said delay units, storage registers for gain coefficients controlling the other of each of said first and second pairs of gain devices, and means for transferring the outputs of the ones of each of said first and second pairs of gain devices between said input adder circuit and said storage registers. 7. A digital filter section adapted to interchangeable connection as either a recursive filter or a nonrecursive adaptive equalizer comprising not fewer than first and second delay storage units in tandem, first and second pairs of adjustable gain devices connected to the outputs of each of said delay storage units, first and second adders respectively connectable to the input of said first delay storage unit only and to the outputs of all of said delay storage units, means for connecting one of each of said pairs of gain devices to said second adders, means for selectively connecting the other of each of said pairs of gain devices in the alternative to said first adder whereby said filter section is in recursive form or to the one of each of said pairs of gain devices as gain control means whereby said filter section is in nonrecursive equalizer form, an error detection circuit connected to said second adder, means for selectively applying error signals from said error detection circuit to the other of each of said pairs of gain devices for correlation with the delayed input signal thereat, first means for selectively looping the output of each delay storage unit to its own input during operation as an equalizer, second means for selectively looping the output of the last said delay storage unit to the input of said first delay storage unit during operation as an equalizer, and control means for determining the selective operation of said digital filter section in both recursive and nonrecursive forms. Patent Citations
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Definition of wall rocket in English:
A yellow-flowered European plant that resembles mustard and emits a foul smell when crushed.
- Diplotaxis muralis, family Brassicaceae
Example sentences
- The perennial wall rocket can be easily mistaken for the Wild Turnip at first glance because the yellow flowers and slender fruit pods are very similar.
- There were some interesting flowers here, including the yellow, rather wallflower-like wall rocket - of which I failed to get a decent photo.
- Wild arugula (also called wall rocket; botanically Diplotaxis muralis) has small, fleshy leaves and tastes peppery, clean, and sharp.
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Pronunciation: fôrˈtisəˌmō
(especially as a direction) very loud or loudly


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My mother has enjoyed the Sun sets over the Susquehanna for so many years. Tonight was the first time I was actually to catch both her enjoying a sunset, and the sunset it'self. Both of them reflecting.
Both beauties in reflection
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Medicare Secondary Payer Provisions
AARP health insurance plans (PDF download)
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medicare part d (PDF download)
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Medicare Secondary Payer Provisions
Medicare Secondary Payer (MSP) Manual Chapter 1
first of a series of provisions that made Medicare the secondary payer to certain … Payer (MSP) provisions and are found at section 1862(b) of the Social Security …
Medicare Secondary Payer (MSP) Manual Chapter 2 – Centers for …
Mar 20, 2009 … 10 – Medicare Secondary Payer Provisions for Working Aged Individuals … 30 – Medicare Secondary Payer Provision for Disabled Beneficiaries.
Medicare Secondary Payer (MSP) Fact Sheet – Centers for Medicare …
This fact sheet provides a general overview of the MSP provisions and … The MSP provisions apply to situations when Medicare is not the beneficiary's.
Medicare Secondary Payer (MSP) Manual Chapter 7 – Centers for …
Medicare Secondary Payer (MSP) Manual. Chapter 7 – Contractor MSP Recovery Rules. Table of Contents. (Rev. 59, 02-22-08). Transmittals for Chapter 7.
Your Guide to Who Pays First – Medicare.gov
Check your insurance policy—it may include the rules about who pays first. You can … When is Medicare a secondary payer for domestic partners with group.
Medicare Secondary Payer – NHIC, Corp.
a series of provisions that made Medicare the secondary payer to certain … provisions are known as the Medicare Secondary Payer (MSP) provisions and are …
Learn more about MSP (PDF).
is to provide a general overview of the MSP provisions for individuals involved in … Since 1980, the Medicare Secondary Payer (MSP) provisions have protected.
Medicare Secondary Payer Resources – National Government …
Chapter 2 – MSP Provisions. • Chapter 3 – MSP Provider Billing Requirements ( Section 20 for identifying primary payers). • Chapter 4 – Coordination of Benefits …
Strengthening Medicare and Repaying Taxpayers
tration of intravenous immune globulin (IVIG) and to amend title XVIII of the. Social Security Act with respect to the application of Medicare secondary payer rules …
Medicare Secondary Payer – U.S. Senate Special Committee on Aging
insurance may fill in all or some of Medicare's gaps. However, in some situations the Medicare. Secondary Payer (MSP) rules prohibit Medicare from making …
medicare as a secondary payer and coordination of benefits – Health …
Medicare is the secondary payer where the law requires other insurers … Medicare rules treat the services that the federal Black Lung Program to coal miners. ○.
TEFRA MEDICARE SECONDARY PAYER – AGC Health Plans NW
The Medicare Secondary Payer (MSP) rules determine whether Medicare is the … In general, the MSP rules prohibit certain actions by a group health plan that.
MEDICARE Secondary Payer Resource Guide – DON SELF …
The formula for calculating Medicare secondary payment is: …… Security Act ( relating to Medicare Secondary Payer provisions) in the case of reference.
MEDICARE SECONDARY PAYER GUIDELINES – Tufts Health Plan
… Medicare Part A and Part. B. Part B enrollment has rules and time frames that … Medicare Secondary Payer (MSP) refers to situations where another entity or …
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to the Medicare Secondary Payer (MSP) provisions. The purpose … overview of the MSP provisions for individuals … (MSP) provisions have protected Medicare.
mmsea section 111 medicare secondary payer … – Tucker Ellis
May 11, 2009 … A recent amendment to the Medicare Secondary Payer statute …. Guide provides rules for the roles and responsibility of such approved Agents.
Billing Medicare Secondary Payer (MSP) Claims Electronically
Before an MSP claim can be submitted to Medicare, some information from the … They are only able to state what fields are needed to process an MSP claim …. for this service line under the provisions of the contract prior to the determination.
Information – Medicare Secondary Payer Rules
ow edicere Secondary eyer rules apply to edicare BlueCmssBlueShield beneficiaries covered under Erie Cross and lue Shield of iiiineis (CSlL) "Elmo's.
Understanding MSP for Employer Groups – Premera Blue Cross
Special rules apply to multiple employer group health plans concerning coordination of benefits under the Medicare Secondary Payer (MSP) statute and …
Medicare Secondary Payer ("MSP") Overview – American Health …
Jan 26, 2011 … Under the MSP laws, Medicare is the secondary payer in designated instances of dual ….. to provide deference to MSP manual provision.


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I am very passionate about civil rights for lazy people.
i see him :0
How long did it take you to set that up?
Not long what so ever.
Yeah I've seen that before. Monty Python is classic. :)
This is a very well placed screenshot, well done :)
Thanks :)
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Unseen killer...


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Material Type: | Government publication, National government publication |
Document Type: | Book |
All Authors / Contributors: |
J Frasier; Institute for defense analyses alexandria va. |
OCLC Number: | 45281696 |
Notes: | Final rept. Mar-Sep 98. |
Description: | 88 pages. |
Series Title: | AD-a365 339. |
This briefing maps the U.S. industrial base for development and production of fuzes for bombs, missiles, and large caliber projectiles. The strengths and weaknesses of the firms are assessed. The current and future business base is compiled. Development trends are identified. Potential problems in maintaining competition among willing, competent contractors and suppliers are discussed.
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© 2015 Local Corporation - US Patent 7,231,405
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Kid Cudi
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