FIELD OF THE INVENTION 
     The present invention relates to optical systems for scanning or deflecting light beams, and in particularly to MEMS/MOEMS devices which comprise moving reflective elements, such as oscillating mirrors. 
     BACKGROUND OF THE INVENTION 
     Certain devices such as wafer defect scanners, laser printers, document scanners, projectors and the like make use of a narrow collimated laser beam that usually scan across a flat surface along a straight line path. A typical optical scanning system for this purpose employs a tilting flat mirror to deflect the beam. The tilting micro-mirror serves as a central element in many Micro Electro Mechanical Systems (“MEMS”) devices and/or Micro Opto Electro Mechanical Systems (“MOEMS”) devices. For the convenience of the reader, these devices (i.e. MEMS and/or MOEMS) will be referred to hereinafter throughout the specification and claims as “MEMS” devices. Many of these MEMS devices comprise two types of electro-statically mirrors:
         In-plane mirrors—this type of mirrors is usually driven at its resonance frequency, the stator and the rotor of these mirrors are at the same layer and the mirrors&#39; driving pulse is usually of a rectangular type signal (these mirrors are also known as resonance mirrors).   Staggered mirrors—this type of mirrors is typically comprised of two different layers, one that comprises the stator while the other comprises the rotor. In some cases, where the stator or the rotor is tilted permanently after manufacturing, only one layer may be used for the stator and the rotor. The staggered mirrors may operate at their resonance frequency or at lower frequencies down to and including DC (these mirrors are also known as linear mirrors).       

     In most MEMS devices, data that relate to the mirror&#39;s position must be very accurate. Unfortunately, the knowledge of the actuation voltage timing is usually insufficient to enable determining the accurate position. Temperature changes, laser power change and other factors contribute to an overall unacceptable error in many cases, e.g. where a MEMS mirror is used for projecting applications that require accuracy of much less than a pixel. Video standards, especially high resolution use hundreds of bits per scan line, hence the significance in the accuracy of the mirror&#39;s position. 
     There are several methods known in the art for monitoring the mirror&#39;s position, some of them rely on the electrostatic fingers to derive therefrom an indicator of the mirror position. Each position of the mirror is characterized by having different capacitance induced between the electrostatic fingers, thus, if the capacitance can be measured accurately, it may provide information regarding the mirror&#39;s position. The following attempts were made to harness the system capacitance for monitoring the mirror position: 
     US 2003174376 discloses a control system for controlling the position of the mirrors in a MEMS device. This disclosure uses the absolute capacitance of the mirror to detect the position of the mirror. According to the solution described in this publication, the MEMS mirror device is mounted on a substrate that includes a micro mirror that is movable pivotally about an axis, a first conductive layer on the mirror, a second conductive layer on the substrate, where the first and second conductive layers form a capacitor for determining the position of the mirror. The control according to this disclosure is of the absolute phase by means of measuring the absolute phase of the mirror. Unfortunately measuring this parameter in order to overcome the problem at hand has been found quite unsatisfactory for a number of reasons among which is the parasitic capacitance involved. 
     US 2008180516 discloses a MEMS mirror device that includes a CMOS substrate, a pair of electrodes, and a reflecting mirror moveable over the substrate and the electrodes. The voltages applied to the electrodes create an electrostatic force causing the edge of the mirror to be attracted to the substrate. According to this publication the position of the mirror can be detected and controlled by sensing a change in capacitance between the mirror edges, by detecting the differential capacitance between the two antipodal electrodes. 
     The above methods measure the absolute capacitance but still fail to provide reliable and accurate information regarding to the mirror position because of parasitic capacitance that is inherent to the system. In addition due to the nature of the electric circle that drives the mirrors, none of the above methods can measure the capacitance throughout the whole scanning cycle. 
     SUMMARY OF THE INVENTION 
     It is object of the present invention to provide a device and method for accurately monitoring the position of mirrors in a MEMS device. 
     It is another object of the present invention to provide a device and method for measuring the changes in capacitance over time for a MEMS device. 
     It is yet another object of the present invention to provide a device and method for measuring continuously the changes in capacitance in a MEMS device throughout the whole scanning cycle. 
     It is still another object of the present invention to provide a method for measuring the maximum deflection angle of in-plain mirrors in MEMS devices. 
     It is yet another object of the present invention to provide an adequate solution for the 180° ambiguity problem associated with in-plain mirrors of MEMS devices. 
     It is still another object of the present invention to provide a method for monitoring the movement of at least one moving mirror in a staggered configuration, based on identified plurality of ripples in the mirror resonance frequency. 
     Other objects of the invention will become apparent as the description of the invention proceeds. 
     According to a first embodiment of the present invention there is provided a method for monitoring movement of at least one moving mirror in a MEMS device which comprises one or more moving mirrors, wherein the monitoring is based upon capacitance changes in the MEMS device over time, and wherein the method comprises the steps of: 
     if the at least one moving mirror is an in-plain mirror:
         a. providing DC voltage to the MEMS device in addition to a driving voltage required for the movement of the at least one moving mirror;   b. measuring current that is proportional to capacitance changes associated with the movement of the at least one moving mirror; and   c. monitoring the at least one moving mirror movement based on the measured current; and       

     if the at least one moving mirror is a staggered mirror:
         a. measuring a current associated with the movement of the at least one moving mirror;   b. identifying a plurality of ripples associated with capacitance changes in the MEMS device over time, in the measured current; and   c. monitoring the at least one moving mirror movement based on the identified plurality of ripples.       

     According to another preferred embodiment of the invention, the driving voltage of the at least one in-plain mirror comprises a series of periodical signals and wherein at least one signal of that series of signals is missed in order to enable establishing a complete cycle of the capacitance change. 
     According to yet another embodiment of the present invention, in case where the at least one moving mirror is a staggered mirror, the method further comprising the step of:
         d. establishing at least one counter signal (i.e. counter acting signal) required to offset at least one of the plurality of identified ripples to prevent unwanted oscillations in the movement of the at least one moving mirror.       

     The term “establishing at least one counter signal” as used herein should be understood to encompass also application of minimizing algorithms in order to establish the quantities of current/voltage required to offset (eradicate) the measured ripples. 
     In accordance with another embodiment of the present invention, the method further comprises a step of determining the at least one mirror position based on the at least one mirror monitored movement. 
     By still another preferred embodiment, the at least one moving mirror is an in-plane mirror, and the method further comprising a step of calculating the maximum deflection angle of the at least one moving mirror. 
     According to another preferred embodiment, the at least one moving mirror is an in-plane mirror, and the method further comprises a step of determining the direction at which the in-plain mirror rotates. 
     In accordance with another preferred embodiment, for the at least one moveable mirror that is a staggered mirror, the method further comprises preventing the mirror from rotating at its natural frequency. 
     According to another aspect of the present invention there is provided a MEMS device comprising at least one moveable mirror and adapted to monitor movement of the at least one moveable mirror based upon capacitance changes in the MEMS device over time, and wherein the MEMS device further comprises: 
     voltage supply means operative to provide driving voltage required for the movement of the at least one moving mirror; 
     current measuring means operative to measure current associated with a capacitance change involved with the movement of the at least one moveable mirror; 
     a processor operative to monitor the movement of the at least one moveable mirror based on the current measurement; and
         wherein if the at least one moveable mirror is an in-plain mirror, the voltage supply means is operative to provide DC voltage to the MEMS device in addition to the driving voltage, the current measuring means is adapted to measure current proportional to capacitance changes and associated with the DC voltage; and   wherein if the at least one moving mirror is a staggered mirror, the MEMS device further comprises means to identify in the measured current a plurality of ripples associated with capacitance changes in the MEMS device over time, and the processor is adapted to monitor the movement of the at least one moveable mirror based on the plurality of identified ripples.       

     According to another preferred embodiment of this aspect of the invention, in the case that the at least one mirror is an in-plain mirror, the driving voltage provided comprises a series of periodical signals and wherein at least one signal of that series is missed to enable establishing a complete cycle of the capacitance change. 
     In accordance with another preferred embodiment, processor is further adapted to determine the at least one mirror position based upon the movement of the at least one mirror monitored. 
     By yet another preferred embodiment, the processor is further operative to establish when the movement direction of the at least one mirror is changed based on the monitored movement of the at least one mirror. 
     According to still another preferred embodiment, the processor is further operative to calculate maximum deflection angle of the at least one moving mirror being an in-plain mirror. 
     In accordance with yet another preferred embodiment, wherein the at least one moving mirror is a staggered mirror, the processor is further adapted to prevent that mirror from rotating at its natural frequency. (e.g. referred to hereinbefore as “ripples”). 
     Preferably, for a case where the at least one moving mirror is a staggered mirror, the processor is further adapted to establish at least one counter signal required to offset at least one of the plurality of identified ripples. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       FIG.  1 —displays a schematic example of MEMS mirrors apparatus; and 
       FIG.  2 —presents a graph describing the voltage applied to in-plane mirrors dependence in time; 
         FIGS. 3A and 3   b —provide an example of a circuitry that enables measuring the current associated with the capacitance changes: 
       FIG.  3 A—demonstrates prior art hardware; 
       FIG.  3 B—demonstrates one possible option for hardware modification which enables the current measurement; and 
       FIGS.  4 A and  4 B—illustrate an embodiment of the present invention enabling capacitance measurements in a full cycle: 
       FIG.  4 A—demonstrates measurements results when all actuation pulses exist. The repetitive high voltage pulses may blank relatively high percentage of the measurements; 
       FIG.  4 B—demonstrates the measurement&#39;s results according to the present invention when occasionally one actuation pulse is omitted to enable a clean full cycle of measurement; and 
       FIG.  5 —presents a graph describing the voltage applied to the in-plain mirrors according to the embodiment illustrated in  FIG. 4B ; and 
       FIG.  6 —demonstrates a way to measure the maximum deflection angle of the mirror; and 
         FIGS. 7A ,  7 B, and  7 C—illustrate an embodiment of the present invention for solving the “180° ambiguity” problem in in-plain mirrors: 
       FIG.  7 A—presents a side view of a typical prior-art in-plane mirror; 
       FIG.  7 B—demonstrates a solution for the “180° ambiguity” problem; 
       FIG.  7 C—demonstrates another solution for the “180° ambiguity” problem; 
         FIGS. 8A ,  8 B and  8 C—provide simulated and practical results associated with some of the embodiments which relate to in-plain mirrors: 
       FIG.  8 A—presents a simulated detector signal according to one embodiment of the invention; 
       FIG.  8 B—illustrates practical results according to the same embodiment of the invention simulated in  FIG. 8A ; 
       FIG.  8 C—displays the capacitance calculation of the new conductive layer as suggested in  FIG. 7B ; 
       FIGS.  9 A and  9 B—demonstrate two views of a schematic example of a staggered mirror device; 
       FIG.  10 —presents a typical case of staggered mirror having resonance “ripples”; and 
       FIG.  11 —presents a flow chart demonstrating one option of implementing the method proposed by the present invention. 
     
    
    
     DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS 
     A better understanding of the present invention may be obtained when the following non-limiting detailed examples are considered in conjunction with the accompanying drawings. 
     In order to better understand the various aspects of the present invention, let us consider the following: Equation (1) is derived simply by using the basic definitions of the parameters used: 
                     I   ⁡     (   t   )       =         ⅆ   Q       ⅆ   t       =         ⅆ     (   CV   )         ⅆ   t       =       C   ⁢       ⅆ   V       ⅆ   t         +     V   ⁢       ⅆ   C       ⅆ   t                       (   1   )               
Where:
 
     I—is the current; 
     Q—is the electric charge; 
     C—is the capacitance; and 
     V—is the voltage. 
     In the classic case, the capacitance would remain constant over time, therefore the above equation may be reduced to the following: 
     
       
         
           
             
               
                 
                   I 
                   = 
                   
                     C 
                     ⁢ 
                     
                       
                         ⅆ 
                         V 
                       
                       
                         ⅆ 
                         t 
                       
                     
                   
                 
               
               
                 
                   ( 
                   2 
                   ) 
                 
               
             
           
         
       
     
     However, according to a preferred embodiment of the present invention, we are interested in the capacitance change when fixed in time voltage is applied to the system. In this case, equation (1) may be reduced to the following: 
     
       
         
           
             
               
                 
                   I 
                   = 
                   
                     
                       
                         ⅆ 
                         
                           ( 
                           CV 
                           ) 
                         
                       
                       
                         ⅆ 
                         t 
                       
                     
                     = 
                     
                       V 
                       ⁢ 
                       
                         
                           ⅆ 
                           C 
                         
                         
                           ⅆ 
                           t 
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   3 
                   ) 
                 
               
             
           
         
       
     
     In this case the current will indicate the change in the capacitance with time. Now, let us assume that the capacitance is composed of fixed and variable components:
 
 C=C   f   +C   v   (4)
 
     The parasitic capacitance associated with the fixed capacitance will not be detected when we measure only the change in capacitance, hence: 
     
       
         
           
             
               
                 
                   I 
                   = 
                   
                     V 
                     ⁢ 
                     
                       
                         ⅆ 
                         
                           C 
                           v 
                         
                       
                       
                         ⅆ 
                         t 
                       
                     
                   
                 
               
               
                 
                   ( 
                   5 
                   ) 
                 
               
             
           
         
       
     
     As aforesaid, many MEMS devices comprise in-plane mirrors and/or staggered mirrors. The following description relates to these two types of mirrors outlining the difference in implementing the method of the present invention for each type of these mirrors. 
     In-Plane Mirrors 
       FIG. 1  illustrates a schematic example of an in-plain mirror according to the present invention. Device  100  comprises two types of “fingers”, the rotor fingers ( 110 ) that are connected to the tilting mirror and the stator fingers ( 120 ) that are connected to MEMS structure (where both types of fingers reside at the same plane), and a torsional spring ( 130 ) that enables the movable MEMS part to move. 
     A fixed voltage is applied to the device.  FIG. 2  illustrates the voltage profile over time that is applied to the in-plane mirrors.  210  shows the base level of constant voltage applied to a typical prior art device, whereas  220 ,  220 ′ and  220 ″ are the rectangular signals that form the driving pulse. According to the present invention, a relatively small fixed DC voltage  230  is further applied to the device, in order to enable measuring capacitance changes in accordance with the present invention. The small fixed DC voltage may be either positive or negative, and is selected such that it will preferably have a negligible effect on the mirror operation. Still, it will be such that will enable the measurement of the current evolving due to the change in the capacitance. 
       FIGS. 3A and 3B  demonstrate examples of a circuitry that enables measuring the current (the “rotor” and the “stator” are interchangeable).  FIG. 3A  demonstrates the original hardware, and  FIG. 3B  demonstrates one possible option for hardware modification which enables measuring the capacitance change in time windows were the high driving signal does not exist. 
     The movement of the in-plain mirror is driven by a driving pulse which is usually a periodically rectangular signal. The high voltage signal drives the operational amplifier to a saturation level and only afterwards the capacitance measurements will take place. Therefore only part of the capacitance change can be measured, this situation is demonstrated in  FIG. 4A  where  410 ,  410 ′ and  410 ″ represent blank time segments during which capacitance and particularly capacitance changes, cannot be measured.  FIG. 4B  demonstrates a solution of the present invention to cover the capacitance changes within a complete cycle. According to one embodiment of the present invention one driving pulse is omitted from time to time, thus enabling to measure the complete capacitance change curve cycle.  420  and  420 ″ represent blank time segments during which the capacitance changes are not measured, while  420 ′ represents a time segment where the pulse is omitted and the capacitance changes are measured. It is particularly convenient to omit a pulse during a period at which the scan accuracy is not critical, for instance during a vertical retrace time of a 2×1D of the scanning mirror, in projecting applications. 
       FIG. 5  demonstrates the resulting voltage profile applied to the device. Here again,  510  is the base voltage that is applied to the device whereas  520  is the additional constant voltage applied to the device according to the present invention for the capacitance changes measurements. The driving pulses (rectangle signals)  530  and  530 ″ are examples of driving pulses that are responsible for the mirror movement, but as opposed to the similar profile presented mutatis mutandis in  FIG. 2 , this time, there is no driving pulse  530 ′ between pulses  530  and  530 ″. Still, in order to achieve a better signal to noise ratio, it is possible to apply during the dilution period a high DC voltage (i.e. the dilution period being a period extending from the pulse that preceded the time at which the missing pulse should have been applied to the pulse that proceeds that time of the missing pulse). If the duration of the applied high DC voltage is essentially equal to one period, its effect would be negligible due to the energy conservation law. However, the current I in Eq. (5) will be much higher since it is proportional to the applied voltage, V. 
     The data describing the capacitance changes may be applied for a variety of uses. For example, to determine if the mirror is actually rotating (this may be important for safety reasons, to avoid eye injuries when the laser beam is reflected from a non-moving mirror), to measure the exact crossover time, i.e. the time when the mirror is parallel to the plane, etc. At that point, the capacitance is at its maximum value and apart from a small timing offset that could be compensated, the capacitance change at this point is equal to zero. According to another embodiment of the invention the capacitance changes enable to determine the maximum deflection angle of the mirror. It is possible to measure it either according to the produced current (the higher 
                 ⅆ     C   v         ⅆ   t       ,         
the higher is the deflection) as exemplified in  FIG. 6  or, according to the distance of the driving pulse and the crossover time.
 
     Due to the full symmetry existing typically in in-plain mirrors, it is usually impossible to determine whether the mirror moves upward or downward. This problem is usually referred to as the “180° ambiguity”. At a certain occasion, the mirror may start moving in one direction, while, at another occasion it may start moving in the opposite direction.  FIG. 7A  is a side view of a typical in-plane mirror, where  710  is the holding frame that constitutes the base for the in-plain mirrors,  720  is an insulation layer,  730  is the rotor,  750  is the stator, and  740  is the overlapping area between the rotor ( 730 ) and the stator ( 750 ). Several solutions to this “180° ambiguity” problem are known in the art. A typical (but costly) solution is to add an optical detector to solve the ambiguity question. Another solution that could solve the ambiguity is to add a microphone as described in the Applicant&#39;s WO 2010/001388. The present invention provides several symmetry breaking options that when applied to a MEMS device, they enable the determination of change in the direction movement of the mirror based on the capacitance change. The following examples provide non limiting forms of solving the 180° ambiguity, but any other solution that is based on measuring the capacitance changes in a MEMS/MOEMS device, should be consider as being encompassed within the scope of the present invention. 
       FIG. 7B  illustrates breaking the inherent symmetry of the resonator mirror by adding a conductor plating. In this Fig.,  760  is insulation plating whereas  770  is conductor plating placed on top of the insulation planting.  FIG. 7C  demonstrates breaking the inherent symmetry of the resonator mirror by reducing one side of the holding frame,  780  in this Fig. In both cases, using an additional capacitance sensing detector enables the detection of the mirror movement direction. It should be noted that instead of passive capacitance detection, it is possible to introduce active actuation voltage thereby ensuring that the mirror always starts at the correct direction. 
       FIGS. 8A ,  8 B, and  8 C provide simulated and practical results associated with some of the embodiments of the present invention that relate to the in-plain mirrors discussed above.  FIG. 8A  is a simulated detector signal (detector&#39;s current). In this simulation one can observe the complete capacitance change curve cycle where  810  and  820  are two reference points that are easily identifiable (further explanation on measuring the complete capacitance change curve cycle were provided hereinabove while discussing  FIGS. 4A and 4B ). The practical results are illustrated in  FIG. 8B  where the dilution method was applied in order to receive the full capacitance change curve. Blank time segments  830 ,  832 ,  834 ,  836  and  838  are associated with the voltage pulses where no measurements are made, and  810 ′ and  820 ′ are the points that correspond to the points of  FIG. 8A , and were measured when a driving pulse was omitted.  FIG. 8C  presents the capacitance calculation of the new conductive layer of  FIG. 7B  using finite elements method (in pF). 
     Staggered Mirrors 
       FIG. 9A  demonstrates a schematic example of a staggered mirror device according to the present invention. The device comprises two types of “fingers”, stator fingers ( 940 ) that are connected to MEMS handle ( 910 ), and rotor fingers ( 930 ) that are connected to the tilting mirror ( 950 ) and to ankle ( 920 ).  FIG. 9B  presents the same device in a side view for better demonstrating the fact that the “fingers” are staggered, i.e. are not at the same plain. 
     Staggered mirrors are used for applications that require non-sinusoidal operation, such as vertical scan in projection systems, where a saw tooth movement is desirable. For this purpose, the driving voltage is usually continuous with the required characteristics that will cause the mirror to move according to a pre-defined path. However a dynamic control is required to prevent the mirror from (slightly) rotating at its natural frequency. As may be recalled from Equation (1), the measured current depends on the voltage change in time and the capacitance change in time: 
     
       
         
           
             
               
                 
                   
                     I 
                     ⁡ 
                     
                       ( 
                       t 
                       ) 
                     
                   
                   = 
                   
                     
                       
                         ⅆ 
                         Q 
                       
                       
                         ⅆ 
                         t 
                       
                     
                     = 
                     
                       
                         
                           ⅆ 
                           
                             ( 
                             CV 
                             ) 
                           
                         
                         
                           ⅆ 
                           t 
                         
                       
                       = 
                       
                         
                           C 
                           ⁢ 
                           
                             
                               ⅆ 
                               V 
                             
                             
                               ⅆ 
                               t 
                             
                           
                         
                         + 
                         
                           V 
                           ⁢ 
                           
                             
                               ⅆ 
                               C 
                             
                             
                               ⅆ 
                               t 
                             
                           
                         
                       
                     
                   
                 
               
               
                 
                   ( 
                   1 
                   ) 
                 
               
             
           
         
       
     
     But in the staggered mirror case, the driving voltage is typically continuous and cannot be replaced by a constant voltage as in the case of the in-plane mirror. However, the driving voltage is known and theoretically does not include “ripples” in the mirror resonance frequency, therefore, any “ripples” in the mirror resonance frequency may be attributed to capacitance change oscillations, i.e. the ripples in the capacitance measurements are created due to the high Q (low damping factor) of the mirror. 
     A dynamic control is therefore needed to prevent the mirror from (slightly) rotating at its natural frequency. 
     As demonstrated hereinbefore, the current that can be measured will be: 
     
       
         
           
             I 
             = 
             
               
                 ⅆ 
                 
                   ( 
                   CV 
                   ) 
                 
               
               
                 ⅆ 
                 t 
               
             
           
         
       
     
     But in this case, the applied voltage is continuous and cannot be replaced by a constant voltage as in the case of in-plane resonance mirror. However, the applied voltage is known and typically does not include “ripples” with the mirror resonance frequency. Therefore, any current “ripples” in the mirror resonance frequency is attributed to capacitance change oscillations, that is, to the mirror mechanical oscillations. 
       FIG. 10  shows a typical case of staggered mirror having resonance “ripples” as measured by a circuitry similar to the one described in connection with  FIG. 3B . The oscillations are clearly measured ( 1000  indicates the trace start) and it is possible to observe the oscillations decay in time due to mechanical losses. According to a preferred embodiment of the present invention the oscillations are dynamically controlled (i.e. eradicated) by introducing a measurement metrics (such as p-p values or DFT value) and then eradicating the ripples by applying counter signals during the fly-back period. Other cancelling signals and/or minimizing algorithm such as early-late gate algorithm or any other control methods can be applied to achieve full eradication. 
       FIG. 11  provides a flow chart that demonstrates one option for implementing the method proposed by the present invention. The current measurement provides 
                 ⅆ     (   CV   )         ⅆ   t       ,         
the measurement metrics are processed using a Discrete Fourier Transform ( 1110 ), and an early-late gate algorithm ( 1120 ) is used to identify the ripples. Next, counter signals are applied to the driving circular ( 1130 ), preferably during the fly-back period to cancel the mirror ripples.
 
     In order to minimize the ripples, a counter-acting signal is introduced. Two measurements are done. The first measurement is done with the current value of the counter-acting signal, while the second measurement is carried out with a slightly modified value. The metrics result of the first measurement is compared with the metrics result of the second measurement. If the second result shows a lower value (less ripples), the second counter-acting signal is considered to be better. The system will then adopt the second signal to be the reference signal and will continue the iterations while using the same trend for modification. 
     However in case the second measurement yields a higher value result (i.e. more ripples), the selected modification would be considered to worsen the situation, so that the system would stay in this case with the same original state and will apply a reverse modification trend. 
     It should be mentioned that the algorithm that is used to achieve the required results may be comprised of two or more modification dimensions such as amplitude and phase of the counter-acting signal.
A method for monitoring movement of at least one moving mirror in a MEMS device comprising one or more moving mirrors, and wherein the monitoring is based upon capacitance changes over time in the MEMS device. The method comprises the steps of: if the at least one moving mirror is an in-plain mirror, then: a. Providing DC voltage to the MEMS device in addition to a driving voltage required for the movement of that at least one moving mirror; b. Measuring current proportional to capacitance changes associated with the movement of the at least one moving mirror; and c. Monitoring the movement of the at least one moving mirror based on the measured current. If the at least one moving mirror is a staggered mirror, then: d. Measuring a current associated with the movement of the at least one moving mirror; e. Identifying a plurality of ripples associated with capacitance changes in the MEMS device over time, in the measured current; and f. Monitoring the movement of the at least one moving mirror based on the identified plurality of ripples.