CROSS-REFERENCE TO RELATED APPLICATIONS 
     This application claims the benefit of U.S. Provisional Application Ser. No. 60/260,132, filed on Jan. 2, 2001 and entitled “A Simple Approach to Non-Linear Cancellation of Line Driver Errors and Non-Linearities,” which is incorporated by reference herein in its entirety. 
    
    
     FIELD OF THE INVENTION 
     The present invention generally relates to telecommunication and, more particularly, relates to a system and method for removing the linear and non-linear echo signal. 
     BACKGROUND OF THE INVENTION 
     With advancements in technology, the transmission of voice and data at faster rates and in larger volumes is always in demand. One solution to fulfilling these demands is digital subscriber line (DSL) technology. DSL technology has been introduced into the field of broadband networking, among other reasons, to overcome issues faced by traditional voice band technology. Such issues include, but are not limited to, bandwidth limitations. Multiple DSL technologies exist including, but not limited to, rate adaptive DSL (RADSL), symmetric DSL (SDSL), multi-rate SDSL (M/SDSL), high bit-rate DSL (HDSL), very high bit-rate DSL (VDSL), and asymmetric DSL (ADSL). 
     ADSL technology utilizes the infrastructure already in place in a public switched telephone network (PSTN), including copper loops constructed of copper wires, between a customer premise and a central office. Advantageously, ADSL technology does not require replacement of network equipment such as routers, switches, firewalls and Web servers, which are commonly used in today&#39;s paradigm for broadband access. 
     The transmitting and receiving of information on a common wire creates coupling and interference between the transmitted and received signal. This interference is referred to as echo. One of the characteristics of echo is that a transmit waveform that is transmitted within a local transmit path, is coupled to a local receive path, thereby interfering with received signals. The result of this reflection is a differently shaped waveform than was originally intended to be received, which introduces data degradation. 
     Echo cancellation is the elimination of the transmit signal from the received signal. Numerous methods have been used for removing transmit echo. One such method, for example, comprises use of a least mean squared adaptation. Least mean squared adaptation finds a correlation between a received signal and error caused by echo. Specifically, an echo canceler is utilized to cancel transmit echo, thereby leaving a clean incoming signal. 
     The echo is generated by two types of error, linear error as well as non-linear error. Many of today&#39;s current applications can correct for the linear error. Digital Signal Processors (DSP) can easily detect the differences between the receive signal and the transmit signal it sent as long as the differences are linear. If the differences can be detected, an echo canceler can easily eliminate the error. However, DSPs can not easily recognize non-linear error. 
     Non-linear errors are caused by non-linearities present in components that process the transmit and receive signals. In particular, a line driver generates much of the non-linear error on the transmit signal. A line driver drives the transmit signal through a two-wire pair in accordance with a required power particular to the application considered and the type of line driven. Most established DSL applications have a required standard power spectral density template that they are required to meet. As an example, for the most common DSL service currently deployed (2B1Q HDSL), the required transmit power is approximately 13.5 dBm. This yields a maximum peak power of 18.6 dBm, for a peak current of 48.2 mA (assuming 6Vpp differential output voltage, 3 dB loss in back matching resistors, and a peak-to-average ratio (PAR) of 1.8 for 2B1Q). 
     At the other extreme, the required transmit power for a Discrete Multi Tone-Asymmetric Digital Subscriber Line-Central Office (DMT-ADSL-CO), assuming 3 dB loss in the back matching resistors and a PAR of 5.3 for DMT, is approximately 20.5 dBm. This yields a maximum peak power of 37.98 dBm, for a peak current of 2095 mA (assuming a 6Vpp differential output voltage). It should be noted that there is a multitude of other applications at various power levels between these two extremes. Also, due to line impairment caused by a variety of different factors, particularly bridge taps, the actual line impedance might be significantly less then expected, and the load current can thus be significantly higher then expected. 
     For DSL systems, the line driver is typically the most significant source of distortion in the data transmit path, due to the high speed and large load current requirement, combined with the variety of line configurations encountered. For most high-speed ADSL applications the trend is currently to avoid transmitting and receiving in the same frequency bands. From the customer premise side, typically there is transmission at the low frequency end of the band and reception at the upper frequency end of the band. Thus, distortion products, which fall at multiples of the transmit signal, fall in the receive spectrum. Typically, distortion in the transmit path couples into the receive path through a hybrid, which makes the receiver implementation significantly more challenging. The receiver recovers the echoed portion of the transmit signal, which falls in the receive band, as well as the receive signal itself. Therefore, limitation of distortion in the transmit path is important to both the transmission and reception of information. 
     It should also be noted, that distortion introduced in the receive band by any element in the transmit path, up to the line driver, can be filtered out with a passive external LC filter before it is fed to the line driver. However, if the line driver introduces the distortion, it is not practical to filter the distortion out due to the low impedance level. Thus, the distortion introduced by the line driver is the final limiting factor for the distortion of the transmit path, which typically is the most critical factor in terms of achievable reach of the system. 
     Generally, line drivers are implemented with high input impedance amplifiers. This makes it easy to interface to the line driver. However, it implies that there is significant signal swing across the input terminals of the line driver. This changes the common mode input to the line driver, which inherently changes the gain, in turn, yielding distortion and degradation of both transmitted and received data. 
     A system and method is desirable to not only eliminate the linear errors that crossover from the transmit path to the receive path, but to also eliminate non-linear errors generated by components that process the transmit signal. In particular, the errors caused by the line driver. 
     SUMMARY OF THE INVENTION 
     In light of the foregoing, a transceiver interface circuit is disclosed. The transceiver interface circuit cancels echo caused by non-linearities in the transmission and reception process. 
     Generally, the structure of the transceiver interface circuit contains a digital signal processor (DSP). The DSP processes a transmit, receive, and transmit error signal. Mathematical operations are performed on the receive and transmit error signal to eliminate non-linear error on the receive signal by error compensation. An analog front end (AFE) is used to modify the transmit, receive, and transmit error signals from either analog to digital or vice-versa. A line driver is used to amplify the transmit signal for transmission. The line driver also outputs the transmit error signal that is generated by the amplification of the transmit signal. A hybrid network is used to isolate the amplified transmit signal from the receive signal. The hybrid network sends the transmit signal and receives the receive signal to and from a transmission line, respectively. The receive signal and error signal are sent to the DSP for error compensation. 
     The present invention can also be viewed as a method for performing echo-cancellation. In this regard, the method can be broadly summarized by the following steps: amplifying a transmit signal to a certain power level for transmission; sensing a transmit error signal generated by the amplification of the transmit signal; error compensating a receive signal with the transmit error signal. The receive signal contains error that is introduced from the transmit signal. Once error compensated, transmit error is removed from the receive signal. 
     Other systems and methods of the present invention will be or become apparent to one with skill in the art upon examination of the following drawings and detailed description. It is intended that all such additional systems, methods, features, and advantages be included within this description, be within the scope of the present invention, and be protected by the accompanying claims. 
    
    
     
       BRIEF DESCRIPTION OF THE DRAWINGS 
       The invention can be better understood with reference to the following drawings. The components of the drawings are not necessarily to scale, emphasis instead being placed upon clearly illustrating the principles of the present invention. Moreover, in the drawings, like referenced numerals designate corresponding parts throughout the several views. 
         FIG. 1  shows the spectrum allocation for both POTS and xDSL signals. 
         FIG. 2  shows the spectrum allocation for the transmit and receive signals of xDSL. 
         FIG. 3  is a block diagram of a communication system in which the present echo canceling system may be provided. 
         FIG. 4  is a block diagram further illustrating a connection between the central office ADSL interface card of  FIG. 3  and the customer premise ADSL interface card of  FIG. 3 . 
         FIG. 5  is a block diagram further illustrating the ADSL customer premise interface card of  FIG. 4 . 
         FIG. 6  is a circuit diagram of an amplifier contained within the line driver of  FIG. 5 . 
         FIG. 7  is a flowchart illustrating functionality performed by the present echo canceling system. 
     
    
    
     DETAILED DESCRIPTION OF THE INVENTION 
     Turning now to the drawings, wherein like referenced numerals designate corresponding parts throughout the drawings,  FIG. 1  shows the spectrum allocation for both POTS and xDSL signals. Specifically, the graph is a plot of frequency on the horizontal axis and power on the vertical axis. As is known, the POTS frequency band  10  generally extends from approximately DC, or 0 hertz, to approximately 3.4 kilohertz. The xDSL frequency band  11  generally extends from approximately 30 kilohertz up to an upper boundary  12 , which varies depending upon the particular digital subscriber line technology utilized. A separation or guard band  13  provides a margin of signal separation between the POTS frequency band and the xDSL frequency band, thereby allowing both POTS and xDSL to co-exist on the same wire. 
       FIG. 2  shows in more detail the spectrum allocation of the xDSL frequency band  11 . Again, the graph is a plot of frequency on the horizontal axis and power on the vertical axis. For customer premise applications the transmit signal frequency band  15  is the lower of the two  15  and  16 . The transmit signal frequency band for ADSL is roughly 35 kHz to 135 kHz. The receive signal frequency band is roughly 138 kHz to 1.1 MHz. The upper and lower bounds of each frequency band may vary based upon the particular DSL technology utilized. On the central office side, the frequency bands are flipped. Therefore the transmit signal is in the higher frequency band and the receive signal is on the lower frequency band. 
     Of importance is the noise  17  which may be introduced at multiples of the transmit signal, i.e., at frequency multiples of the lower frequency band  15 . This typically occurs as the transmit signal is processed by several components. As will be discussed later, amplification of the transmit signal is often the main cause of this error. As one can see, the noise  17  falls into the receive signal frequency band  16 . When the two frequency bands become isolated by a hybrid network, the noise  17  that is in the receive signal does not get eliminated. It is this error that causes deterioration of the receive signal and thus must be corrected. 
       FIG. 3  is a block diagram of a communication system in which the present echo canceling system may be provided. Specifically,  FIG. 3  illustrates communication between a central office  20  and a customer premise  22  by way of a local loop  24 . While the customer premise  22  may be a single dwelling residence, a small business, or other entity, it is generally characterized as having POTS equipment, such as a telephone  26 , PSTN modem  27 , fax machine (not shown), etc. The customer premise  22  may also include an xDSL communication device, such as an xDSL modem  28 , comprising an ADSL interface card  100 A for handling ADSL services. When an xDSL service is provided, such as, but not limited to, ADSL, a POTS filter  30  is interposed between the POTS equipment  26  and the local loop  24 . As is known, the POTS filter  30  includes a low-pass filter having a cut-off frequency of approximately 4 kilohertz to approximately 10 kilohertz, in order to filter high frequency transmissions from the xDSL communication device  28  and protect the POTS equipment. 
     It should be noted that although the present disclosure is made with reference to ADSL technology, one skilled in the art will appreciate that other communication, specifically xDSL, technologies requiring the mitigation of echo effects may also be provided for by the present technique. 
     Additional circuitry is provided at the central office  20 . Generally, a line card  40  containing line interface circuitry is provided for electrical connection to the local loop  24 . In fact, multiple line cards may be provided  40 ,  42  to serve as a plurality of local loops  24 . In the same way, additional circuit cards are typically provided at the central office  20  to handle different types of services. For example, an integrated services digital network (ISDN) interface card  44 , a digital loop carrier line card  46 , and other circuit cards, for supporting similar and other communication services, may be provided. Particular to the present echo canceling system, an ADSL interface card  100 A may also be provided at the customer premise  22 , also for handling ADSL services, as is further illustrated by  FIG. 5 . It should be noted that the ADSL interface card  100 A may alternatively be located exclusively at the central office  20 , or exclusively at the customer premise  22 . 
     A digital switch  50  is also provided at the central office  20  and is disposed for communication with each of the various line cards  40 ,  42 ,  44 ,  46 ,  100 B. On the outgoing side of the central office  20  (i.e., the side opposite the various local loops), a plurality of trunk cards  52 ,  54 ,  56  are typically provided. For example, an analog trunk card  52 , a digital trunk card  54 , and an optical trunk card  56  are all illustrated in  FIG. 3 . Typically, these cards have outgoing lines that support numerous multiplexed transmissions and are typically destined for other central offices or long distance toll offices. 
     The preferred embodiment of the invention uses DMT line coding techniques, which provide multiple sub-channels for the transmission of information. ADSL uses multiple independent sub-channels for the transmission of information. As known by one skilled in the art, each sub-channel is modulated using quadrature amplitude modulation (QAM) and carries a number of bits per sub-channel. These bits are transmitted and received in groups, or symbols. Generally, 256 complex QAM symbols, which are associated with 256 independent sub-channels, are then converted using an Inverse Fast Fourier Transform (IFFT) yielding a 512 sample DMT symbol. In other words, IFFT maps each QAM symbol into orthogonal frequency bins producing the DMT symbol. 
     A cyclic prefix, comprising 32 samples, is further appended to the 512 samples of each DMT symbol. Briefly stated, the cyclic prefix is a guard space in the time domain that is located between neighboring transmit DMT symbols in order to preserve independence between the 256 sub-channels, thereby protecting against inter-symbol interference (ISI). Each DMT symbol is made of 544 digital samples (512 samples+32 cyclic prefix samples), which are then converted to an analog signal by an analog front end. 
       FIG. 4  is a block diagram further illustrating a connection between the ADSL interface card  100 B of the central office  20  and the ADSL interface card  100 A of the customer premise  22  ( FIG. 3 ), wherein software would be provided within each ADSL interface card  100 A,  100 B for purposes of addressing the aforementioned echo problem. As shown by  FIG. 4 , with regard to the present illustration, transmission of data may be directed from the customer premise  22  to the central office  20 , from the central office  20  to the customer premise (CP)  22 , or in both directions at the same time. The ADSL interface card  100 B located within the central office (CO)  20  comprises a CO DSP  102 , which receives information from a data source (not shown) and sends information to a CO analog front end (AFE)  104 . The CO AFE  104  interfaces between the local loop  24  and the CO DSP  102  and functions to convert digital data, from the CO DSP  102 , into a continuous time analog signal. 
     The analog signal is delivered, via a CO line driver  106 , in accordance with the amount of power required to drive the amplified analog signal through the local loop  24  and to the CP  22 . A CP hybrid  122 , located in the CP  22 , is then used to de-couple the received signal from the transmitted signal, by subtracting the transmitted signal from the sum of the transmitted and received signals. A CP AFE  124 , located in the CP  22 , then converts the received analog signal into a digital signal, which is then transmitted to a CP DSP  126  located in the CP  22 . The CP AFE  124  receives an error signal output from the CP line driver  128 . The analog error signal is then converted from analog to digital by the CP AFE  124  and sent on to the CP DSP  126  for processing. The generation and processing of the error signal will further be discussed in  FIG. 5 . After residual echo cancellation is performed by the CP DSP  126 , as is further discussed hereinbelow, the digital information is transmitted to the data source specified to receive the information. 
     If however, an analog signal is delivered from the CP  22  to the CO  20 , a CP line driver  128  will deliver the signal in accordance with the amount of power required to drive the amplified analog signal through the local loop  24  and to the CO  20 . A CO hybrid  108 , located in the CO  20 , is then used to de-couple the received signal from the transmitted signal, by subtracting the transmitted signal from the sum of the transmitted and received signal. The CO AFE  104 , located in the CO  20 , then converts the received analog signal into a digital signal, which is then transmitted to the CO DSP  102  located in the CO  20 . The Co AFE  104  receives an error signal output from the CO line driver  106 . The analog error signal is then converted from analog to digital by the CO AFE  104  and sent on to the CO DSP  102  for processing. Finally, after residual echo cancellation, the digital information is transmitted to the data source specified to receive the information. 
       FIG. 5  is a block diagram further illustrating the customer premise ADSL interface card  100 A of  FIG. 4 . Again the DSP  126  receives information from a data source (not shown) that needs to be processed for communication. A digital transmit signal  131  is sent to the AFE  124 , wherein a processing block  125  converts the digital transmit signal  131  to analog. The processing block  125  may also contain a plurality of filters used to eliminate any out of band noise that may have been generated by the DSP  126  or the digital to analog conversion. An analog transmit signal  132  is then sent to the line driver  128 . The line driver  128 , as mentioned above, amplifies the analog transmit signal  132  to the required power level based upon the characteristics of the communication network and the application being used. The line driver  128  produces an amplified analog transmit signal  133  that is passed on to the hybrid network  122 . The amplification of the transmit signal generates much error in the form of transmit distortion, manifesting itself as noise  17  in the receive band (see  FIG. 2 ) at multiples of the frequency band of the transmit signal. An error signal  140  can be generated by the line driver  128  that contains the error information generated by the line driver. This transmit error is one of the components of the transmit echo. The transmit error includes non-linear and linear components. 
     As previously discussed, the hybrid network  122  de-couples the transmit signal from the receive signal by subtracting the transmit signal from the combination of the two. Unfortunately, the very nature of the hybrid network  122  allows the noise  17  carried on the amplified transmit signal  132  that falls within the receive signal frequency band  16  ( FIG. 2 ) to be passed through as a component of the receive signal  136 . The receive signal  136 , as mentioned above, is sent to the DSP  126  via the AFE  124 . The AFE may contain some gain stages as well as filters to further process the analog receive signal  136 . The receive signal processing block  127  houses these filters as well as an analog to digital converter. 
     The error signal  140  generated by the line driver  128  is passed to the AFE  124  where it is converted from analog to digital. The preferred embodiment contains a relatively low resolution A-D converter  150  although an A-D converter with higher resolution would suffice. The error signal  140  is generally quite small relative to the transmit and receive signals and the DSP  126  does not require an extremely accurate digital error signal  141 , thus the low resolution A-D converter  150 , which is relatively small and low in cost. The digital error signal  141  is received by the DSP  126 . 
     The DSP  126  can now perform echo cancellation on the receive signal  137 . As is known to one skilled in the art, linear error echo cancellation can be performed without an input error signal  141 . The DSP  126  recognizes what it sent as the transmit signal  131  and what it receives as the receive signal  137 . The system already calculates the transfer function from the DSP  126  to the receive port and so can easily cancel the linear echo. This level of echo cancellation still may retain a receive signal with some of the noise crossed over from the transmit signal caused by non-linear error. The transmit error signal  141  contains such information. The transmit error signal  141  helps compensate for errors in the receive signal  137 . Essentially, the error signal  141  contains all the noise information that must be subtracted from the receive signal  137  to produce an accurate reproduction of the receive signal without any non-linear error originating from the transmit signal. Thus linear and non-linear error is eliminated, completing the echo cancellation. It should be noted that a wide array of algorithms can be applied to mathematically combine the transmit error signal  141  with the receive signal  137  to generate an accurate reproduction of the receive signal. 
     That being said, the DSP  126  can be either configured through hardware, or programmed through software or firmware, or any combination herein, to perform the echo cancellation. In the preferred embodiment of the invention, which is intended to be a non-limiting example, a portion of the system is implemented in software that is executed by the DSP. 
     The software based portion of the echo canceling system, which comprises an ordered listing of executable instructions for implementing logical functions, can be embodied in any computer-readable medium for use by, or in connection with, an instruction execution system, apparatus, or device such as a computer-based system processor containing system, or other system that can fetch the instructions from the instruction execution system, apparatus, or device and execute the instructions. In the context of this document, a “computer-readable medium” can be any means that can contain, store, communicate, propagate or transport the program for use by or in connection with the instruction execution system, apparatus or device. 
     The computer-readable medium can be, for example, but not limited to, an electronic, magnetic, optical, electromagnetic, infrared, or semiconductor system, apparatus, device, or propagation medium. More specific examples (a non-exhaustive list) of the computer-readable medium would include the following: an electrical connection (electronic) having one or more wires, a portable computer diskette (magnetic), a random access memory (RAM) (magnetic), a read-only memory (ROM) (magnetic), an erasable programmable read-only memory (EPROM or Flash memory) (magnetic), an optical fiber (optical), and a portable compact disk read-only memory (CD ROM) (optical). Note that the computer-readable medium could even be paper or another suitable medium upon which the program is printed, as the program can be electronically captured, via for instance, optical scanning of the paper or other medium, then compiled, interpreted or otherwise processed in a suitable manner, if necessary, and then stored in a computer memory. 
     Turning now to  FIG. 6 , an amplifier circuit of the line driver  128  of the preferred embodiment is shown. An inverting differential unity gain amplifier  250  is displayed to more easily show the process of generating an error signal through amplification. It should be noted that other amplifiers could be used to produce the same results of amplifying the transmit signal  132  and producing an error signal  140 . An ideal operational amplifier (op-amp)  210  takes an input, amplifies the input V in  by a gain and produces an output V out =AV in . An inverting amplifier will produce an output V out =−AV in  and a differential amplifier will produce an output based upon the difference between two inputs V out =A(V+−V−). A unity gain amplifier will produce an output that is equivalent in magnitude as the input (A=1), therefore V out =V in . So the inverting differential unity gain amplifier  250  will produce an output V out =−(V + −V − ). In the case of the preferred embodiment, the input signals  132  coming from the AFE  124  are common mode, meaning like in magnitude, therefore the output of the amplifier V out =−V in . When feedback is present in the amplifier circuit and no current is flowing into the + and − terminals of the op-amp  210  it is said that a virtual ground  200  is formed. For an ideal amplifier, the virtual ground  200  means that the voltages across the input terminals are tied together and in this case V in   +  is equal but opposite to V in   − . 
     Unfortunately, amplifiers are non-ideal and they produce errors. These errors, as discussed earlier are carried on the amplified transmit signal  133  and introduced into the receive signal later on in the system. So the non-ideal inverting differential unity gain amplifier  250  will produce an output V out =−(V in )+V err , assuming V in  is common mode, as is the case in the preferred embodiment. If any error, V err , is produced by the amplifier  250 , it can be pulled from the virtual ground  200 . This can be seen by following the output signal back to the input side through the feedback. This error signal  140  is then fed from the virtual ground  200 , out of the line driver  128 , and processed by the low-resolution ADC  150  in the AFE  124  ( FIG. 5 ). 
       FIG. 7  is a flowchart further illustrating the functionality of the present system. A transmit signal  310  is passed to an amplify stage  300 . The transmit signal  310  is amplified to a specific power level based upon the transmission network. A transmit error signal  315  is produced by the amplify stage  300  that relates to the error produced by the amplification. In the preferred embodiment the amplify stage  300  is incorporated within the line driver. The amplified transmit signal  320  is passed to an isolation stage  400 . A receive signal is received from an external transmission line  325 . The external transmission line also carries the transmit signal. The isolation stage  400  attempts to isolate the transmit signal from the receive signal by de-coupling the receive signal from the combination of the two. In the preferred embodiment the isolation stage  400  is incorporated within the hybrid network. The receive signal  330  is passed on to a error compensation stage  500 . 
     The error compensation stage  500  receives both the receive signal  330  and the transmit error signal  315 . By one or a combination of several possible mathematical means the receive signal  330  is compensated. The error information of the transmit error signal  315  is “subtracted” from the receive signal  330  that contains the same error information. The compensation stage  500  produces an error eliminated receive signal  340 . The echo caused by the communication system is thus eliminated. 
     It should be emphasized that the above described embodiments of the present invention, particularly, any “preferred” embodiments, are merely possible examples of implementations, merely set forth for a clear understanding of the principles of the invention. Many variations and modifications may be made to the above-described embodiment(s) of the invention without departing substantially from the spirit and principles of the invention. All such modifications and variations are intended to be included herein within the scope of this disclosure and the present invention and protected by the following claims.
A system for performing echo cancellation via use of a transceiver interface circuit. In a simplified embodiment, a digital signal processor (DSP), an analog front end (AFE), a line driver, and a hybrid network are located within the circuit. The DSP is configured to process a transmit, receive, and a transmit error signal. Mathematical operations of the DSP eliminate error from the receive signal with the help of the transmit error signal. The AFE modifies the transmit, receive, and transmit error signal from analog to digital or vice-versa. The line driver amplifies the transmit signal to a power level compatible with a transmission network. The line driver further produces the transmit error signal which is created by the amplification of the transmit signal. The hybrid network receives the amplified transmit signal from the AFE and a receive signal from the transmission network, and isolates the transmit signal from the receive signal. The receive signal, which has become infected with error from the hybrid network is passed, via the AFE, to the DSP for error compensation.